CN115224944A - Control method of variable topology resonant converter with smooth switching function - Google Patents
Control method of variable topology resonant converter with smooth switching function Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/01—Resonant DC/DC converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0038—Circuits or arrangements for suppressing, e.g. by masking incorrect turn-on or turn-off signals, e.g. due to current spikes in current mode control
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33573—Full-bridge at primary side of an isolation transformer
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The invention discloses a control method of a variable topology resonant converter with a smooth switching function, and belongs to the field of power electronics. According to the method, on the basis of establishing a half-bridge/full-bridge LLC resonant converter model containing parasitic parameters and a state track model of the LLC resonant converter, accurate modeling of the LLC resonant converter is realized, and the optimal track control precision is improved. According to the invention, by analyzing the voltage state tracks of the resonant current and the resonant capacitor and analyzing the influence of the input voltage on the circle center position of the arc-shaped track, the control and regulation relation of the cycle time, the duty ratio to the resonant current and the resonant capacitor voltage is established, and the resonant current-resonant capacitor voltage state tracks are accurately guided to a target steady-state working point and enter a stable linear control state; the invention changes the voltage gain of the LLC resonant converter in the transition process of topology conversion, reduces the resonant current overshoot and the output voltage fluctuation caused by the topology conversion, and accurately inhibits the fluctuation of the output voltage in the transition process of the topology conversion.
Description
Technical Field
The invention relates to a control method of a variable topology resonant converter with a smooth switching function, and belongs to the isolation high-frequency power conversion direction in the field of power electronics.
Background
The LLC resonant converter topology is the most commonly used scheme for high-voltage input, low-voltage, large-current DC-DC converters in the industry at present, and achieves zero-voltage turn-off (ZVS) of the transformer primary side switching device and zero-current turn-off (ZCS) of the transformer secondary side rectifying device in the full load range, thereby obtaining extremely high power conversion efficiency. In many applications, resonant converters are required to operate in a wide output regime. The conventional half-bridge/full-bridge LLC resonant converter controls the output voltage range by changing the operating frequency of the power switching tube, namely changing the gain of the resonant converter, thereby providing a wide range of stable output voltage for power application. However, such a design does not take into account the rapid change of the input voltage during the topology transition, and when a sudden gain change across the half-bridge/full-bridge gain range is required, the output voltage will fluctuate greatly.
Also, in the conventional method, an accurate model of the circuit is not considered, which may cause an error in the determination of the switching frequency after the topology change, thereby causing output fluctuation at the time of topology switching.
Disclosure of Invention
In order to optimize a half-bridge/full-bridge LLC resonant converter control strategy, the fluctuation of output voltage in the transition of topology conversion is inhibited; the invention mainly aims to provide a variable topology resonant converter control method with a smooth switching function, which can change gain in the transition process of topology conversion, reduce resonant current overshoot and output voltage fluctuation caused by topology conversion and inhibit the fluctuation of output voltage in the transition process of topology conversion by utilizing optimal trajectory control based on accurate circuit modeling.
The invention is realized by the following technical scheme.
The invention discloses a control method of a variable topology resonant converter with a smooth switching function, wherein the variable topology resonant converter is a half-bridge/full-bridge LLC resonant converter. The converter mainly comprises a main circuit and a control circuit, and the topology of the main circuit is consistent with that of a full-bridge LLC converter. The main circuit topology comprises a primary side inverter circuit, a transformer and a secondary side rectifying circuit. The primary inverter circuit is composed of a full-bridge circuit, and is operated in a full-bridge state when the input voltage is low, and is controlled to be S when the input voltage is high 3 Off, S 4 Conducting to operate in a half bridge state. And the optimal trajectory control is adopted to limit the resonance current overshoot and the output voltage fluctuation in the topology transformation transition process. The control circuit also comprises a digital control circuit, a sampling circuit and a driving circuit. The sampling circuit is used for samplingInput voltage V in And an output current I o And voltage V o 。
The invention discloses a control method of a variable topology resonant converter with a smooth switching function, which comprises the following steps:
measuring parameters and parasitic parameters of each device of the circuit, obtaining parasitic inductance by using a digital bridge, obtaining turn-to-turn capacitance of a transformer by electromagnetic simulation, obtaining parasitic capacitance of a semiconductor device by a data manual, building a half-bridge/full-bridge LLC resonant converter model containing the parasitic parameters in simulation software, and scanning input voltage under each load to obtain switching frequency-gain-output current f s -G-I o Three-dimensional curved surface and track circle radius-gain-output current rho-G-I o Wherein G = V o /V in . And establishing a state track model of the LLC resonant converter by using the resonant capacitor voltage and the resonant inductor current of the LLC resonant converter as state variables.
An original part of an accurate model of a full-bridge LLC resonant converter comprises a primary side switch tube Q 1 -Q 4 Resonant inductor L r Resonant capacitor C r Transformer excitation inductance L m Transformer with n:1 turn ratio, primary side leakage inductance L of transformer kp Secondary leakage inductance L of transformer ks Equivalent turn-to-turn capacitance C of transformer TR Rectifier diode D 1 -D 4 Parasitic capacitance C of rectifier diode jc . The input voltage is scanned under each load through simulation software to obtain switching frequency-gain-output current f s -G-I o Three-dimensional curved surface and track circle radius-gain-output current rho-G-I o Wherein G = V o /V in 。
For all voltage variables according to the output voltage V of LLC resonant converter o Performing per unit to obtain all current variables according to V o /Z 0 Per unit, where Z 0 Characteristic impedance for two elements:
resonant inductor current i of state variable Lr And resonant capacitor voltage v Cr The per-unit value is i LrN And v CrN Establishing a phase plane model of the LLC resonant converter; the converter works in a boosting state below a resonance frequency, and in a half-bridge mode, a state track of the converter is divided into four sections, wherein the two sections are arcs shown in (2) and (3):
the other two sections are horizontal straight lines formed by linearly charging the resonant capacitor by exciting currents, and the exciting current values are as follows:
in the full-bridge mode, the state locus is divided into four sections, wherein one section of the arc has the same expression as (2), and the other section of the arc is shown as (5):
the other two sections are horizontal straight lines formed by linearly charging the resonant capacitor by the excitation current, and the excitation current is the same as that in the step (4).
The simulation software comprises PSIM and MATLAB which are used as preselection, and PSIM software is selected as the simulation software.
And step two, after the LLC resonant converter is started, detecting the input voltage and the load current of the LLC resonant converter, and judging the voltage gain change condition of the LLC resonant converter.
And step three, if cross-region jumping does not occur in the voltage gain of the LLC resonant converter detected in the step two, the LLC resonant converter enters a linear control mode.
And step four, if the LLC resonant converter voltage gain detected in the step two causes the full bridge to jump to the cross region of the half bridge, the LLC resonant converter obtains the track radius of the state before jumping, the track radius of the state after jumping and the switching frequency according to the load current and the input voltage, and calculates a control variable corresponding to the optimal state track mode I under the cross-region jumping condition, wherein the mode I control variable comprises the control pulse period time length and the duty ratio. And adjusting the time length and the duty ratio of a control pulse period according to the mode-one control variable, accurately guiding a voltage state track of the resonant current-resonant capacitor to a target steady-state working point, further changing the voltage gain of the LLC resonant converter in the transition process of topology conversion, reducing the resonant current overshoot and the output voltage fluctuation caused by the topology conversion, and inhibiting the fluctuation of the output voltage in the transition process of the topology conversion.
The transition from full bridge to half bridge has t 0 -t 4 Five time nodes with input voltage V before transition in1 After jump is V in2 . Wherein t is 0 -t 1 Is obtained according to equation (6):
t 1 -t 0 ＝T r /2 (6)
according to the geometric relationship, get t 0 Resonance voltage:
where ρ is 1 And searching by a three-dimensional plane. Further obtaining the state circle radius of the transition state:
thus t 1 ，t 2 Resonance voltage at time:
where ρ is 2 And searching by a three-dimensional plane. Linear charging of resonant capacitor according to excitation current to obtain t 1 -t 2 Time:
t 2 -t 1 ＝(C r (v CrN (t 2 )-v CrN (t 1 ))nV o )/I Lm (11)
the above formulas (6), (7), (8), (9), (10) and (11) are combined to obtain the total positive pulse time length of the transition period, namely the pulse period time length multiplied by the duty ratio:
switching frequency f after hopping according to three-dimensional plane search Vin2 Obtaining the total length of the transition period time and the duty ratio:
T tran ＝t total +0.5/f Vin2 (13)
D tran ＝t total /(t total +0.5/f Vin2 ) (14)
in the transition from full bridge to half bridge, the period time length of the control pulse is adjusted according to a formula (13), the duty ratio of the control pulse is adjusted according to a formula (14), namely the period time length and the duty ratio of the control pulse are adjusted according to a mode-control variable, a driving signal of a switching tube of the LLC resonant converter is given, and t is enabled to be t 0 -t 1 T of 0 And (4) when the voltage suddenly increases and exceeds the lower limit of the gain provided by the full bridge, finishing linear control and giving the control right to the optimal trajectory control. The voltage applied to the resonant tank suddenly increases, and the state circle radius increases. At t 1 The point locus naturally enters a linear charging stage of the resonant capacitor and is represented as a horizontal straight line. At t 2 At the end of the positive pulse, the track enters the circular track of the latter half period, at t 3 Enter a linear charging phase att 4 And when the optimal trajectory control is finished, handing over the control right to linear control, searching the initial switching frequency by a two-dimensional table, and entering a stable linear control state, namely, changing the voltage gain of the LLC resonant converter in the transition process of topology conversion, reducing the resonant current overshoot and the output voltage fluctuation caused by the topology conversion, and inhibiting the fluctuation of the output voltage in the transition process of the topology conversion.
And step five, if the cross-region jump of the half bridge to the full bridge occurs to the LLC resonant converter voltage gain detected in the step two, the LLC resonant converter obtains the track radius of the state before the jump, the track radius of the state after the jump and the switching frequency according to the load current and the input voltage, and calculates the control variable corresponding to the optimal state track mode two under the cross-region jump condition, wherein the mode two control variable comprises the control pulse period time length and the duty ratio. And adjusting the time length and the duty ratio of the control pulse period according to the mode two control variables, accurately guiding the voltage state track of the resonant current-resonant capacitor to a target steady-state working point, further changing the voltage gain of the LLC resonant converter in the transition process of topology conversion, reducing the resonant current overshoot and the output voltage fluctuation caused by the topology conversion, and inhibiting the fluctuation of the output voltage in the transition process of the topology conversion.
The transition from half-bridge to full-bridge has t 0 -t 4 Five time nodes with input voltage V before jump in1 After jump is V in2 . Wherein t is 0 -t 1 Is obtained according to equation (15):
t 1 -t 0 ＝T r /2 (15)
according to the geometric relationship, get t 0 Resonance voltage:
where ρ is 1 And searching by a three-dimensional plane. Further obtaining the state circle radius of the transition state:
thus t 1 ，t 2 Resonance voltage at time:
where ρ is 2 And searching by a three-dimensional plane. Linearly charging the resonant capacitor according to the excitation current to obtain t 1 -t 2 Time:
t 2 -t 1 ＝(C r (v CrN (t 2 )-v CrN (t 1 ))nV o )/I Lm (20)
the above equations (15), (16), (17), (18), (19) and (20) are combined to obtain the total positive pulse time length of the transition period, namely the pulse period time length multiplied by the duty ratio:
switching frequency f after jump according to three-dimensional plane search Vin2 Obtaining the total length of the transition period time and the duty ratio:
T tran ＝t total +0.5/f Vin2 (22)
D tran ＝t total /(t total +0.5/f Vin2 ) (23)
in the transition from the half bridge to the full bridge, the period time length of the control pulse is adjusted according to a formula (22), the duty ratio of the control pulse is adjusted according to a formula (23), namely the period time length and the duty ratio of the control pulse are adjusted according to a mode-control variable, a driving signal of a switching tube of the LLC resonant converter is given, and t is enabled to be t 0 -t 1 T of 0 The voltage suddenly increases and exceeds the upper limit of the gain provided by the half bridge, the linear control is finished, and the control right is handed to the optimumAnd (4) controlling the track. The voltage applied to the resonant tank suddenly drops, and the state circle radius is reduced. At t 1 The point locus naturally enters a linear charging stage of the resonant capacitor and is represented as a horizontal straight line. At t 2 At the end of the positive pulse, the track enters the circular track of the latter half period, at t 3 Entering a linear charging phase at t 4 And when the optimal trajectory control is finished, handing over the control right to linear control, searching the initial switching frequency by a two-dimensional table, and entering a stable linear control state, namely, changing the voltage gain of the LLC resonant converter in the transition process of topology conversion, reducing the resonant current overshoot and the output voltage fluctuation caused by the topology conversion, and inhibiting the fluctuation of the output voltage in the transition process of the topology conversion.
And step six, if a shutdown instruction or a protection instruction is received, the LLC resonant converter shuts down or seals waves and enters a protection state, if the LLC resonant converter returns to the step two to the step six, a new round of control circulation is entered, when the voltage gain does not cross the gain limit provided by the current mode, linear control is performed according to the step three, when the voltage gain crosses the gain limit provided by the current mode, optimal trajectory control is performed according to the step four and the step five, the voltage gain of the LLC resonant converter is changed in the transition process of topology conversion, resonance current overshoot and output voltage fluctuation caused by topology conversion are reduced, and fluctuation of output voltage in the transition process of topology conversion is suppressed.
Has the beneficial effects that:
1. in the prior art, influence of circuit parasitic parameters on switching frequency is not considered, the invention discloses a variable topology resonant converter control method with a smooth switching function s -G-I o Three-dimensional curved surface and track circle radius-gain-output current rho-G-I o The three-dimensional curved surface of (2). And uses LLC resonant converterThe resonant capacitor voltage and the resonant inductor current are used as state variables to establish a state track model of the LLC resonant converter. On the basis of establishing a half-bridge/full-bridge LLC resonant converter model containing parasitic parameters and a state track model of the LLC resonant converter, accurate modeling of the LLC resonant converter is realized, and the optimal track control precision of the variable topology resonant converter is improved.
2. The invention discloses a variable topology resonant converter control method with a smooth switching function, which is characterized in that on the basis of accurate modeling of a variable topology resonant converter, a resonant capacitor voltage and a resonant inductor current of an LLC resonant converter are used as state variables, a resonant current and a resonant capacitor voltage state track are analyzed, the influence of input voltage on the position of the circle center of an arc section track is analyzed, a cycle time and duty ratio control regulation relation between the resonant current and the resonant capacitor voltage is established, the cycle time and the duty ratio are determined to be used as control variables of a corresponding mode I, the resonant current-resonant capacitor voltage state track is accurately guided to a target steady-state working point according to the cycle time and duty ratio control regulation relation between the resonant current and the resonant capacitor voltage, a stable linear control state is entered, namely the cycle time length and the duty ratio of a control pulse are regulated according to the mode I control variable, the voltage gain of the LLC resonant converter is changed in the transition process of topology conversion, the overshoot of the resonant current and the output voltage fluctuation caused by the topology conversion are reduced, the fluctuation of the output voltage in the transition process of the topology conversion is inhibited, and the overshoot of the resonant current and the output voltage fluctuation caused in the topology conversion is inhibited.
3. In the prior art, the gain and the frequency of a topology conversion switching point are fixed, and the rapid change of an input voltage cannot be coped with. The invention discloses a variable topology resonant converter control method with smooth switching function, which is characterized in that on the basis of beneficial effect 2, when the regulation relation of cycle time, duty ratio to resonant current and resonant capacitor voltage control is established, the influence of the circle center position on a transition state track is considered, namely the change of input voltage influences the circle center position of a state circle in optimal track control, new input voltage is substituted into the circle center after the input voltage is changed during track optimization, the time length and the duty ratio are obtained by calculating the intersection point of the new track and a steady-state working state, the rapid change of the input voltage is coped with, namely the voltage gain of an LLC resonant converter is changed in the transition process of topology conversion, the resonant current overshoot and the output voltage fluctuation caused by the topology conversion are reduced, and the fluctuation of the output voltage in the transition process of the topology conversion is accurately restrained.
Drawings
FIG. 1 is a flowchart of a method for controlling a variable topology resonant converter with smooth switching function according to the present invention;
FIG. 2 is a topology containing parasitic elements used for modeling;
fig. 3 shows a process of dc gain transition in a control method of a variable topology resonant converter with smooth switching function according to the present invention;
FIG. 4 is a DC gain graph of the system operation, wherein FIG. 4 (a) is the switching frequency-gain-output current f in full-bridge mode s -G-I o Fig. 4 (b) shows switching frequency-gain-output current f in half-bridge mode s -G-I o The three-dimensional curved surface of (2);
FIG. 5 shows switching frequency-gain-output current f s -G-I o The three-dimensional curved surface of (1), wherein FIG. 5 (a) is a graph showing the trajectory radius-gain-output current ρ -G-I in the full-bridge mode o Fig. 5 (b) shows the radius of the trajectory in the half-bridge mode-gain-output current ρ -G-I o The three-dimensional curved surface of (2);
FIG. 6 is a state diagram of a transition, wherein FIG. 6 (a) is a transition from full-bridge mode to half-bridge mode, and FIG. 6 (b) is a transition from half-bridge mode to full-bridge mode;
FIG. 7 is a key waveform diagram from full bridge mode to half bridge mode;
fig. 8 is a key waveform diagram from half-bridge mode to full-bridge mode.
Detailed Description
The invention is further illustrated by the following figures and examples.
Fig. 1 shows a control flow chart of the present invention. Before programming, the parameters and parasitic parameters of each device of the circuit are measured and set up in simulation softwareA half-bridge/full-bridge LLC resonant converter model containing parasitic parameters scans input voltage under each load to obtain switching frequency-gain-output current f s -G-I o Three-dimensional curved surface and track circle radius-gain-output current rho-G-I o Wherein G = V o /V in . These surfaces are written to the program in the form of a two-dimensional table. When the converter operates, detecting input voltage and output current at the beginning of each interruption, if voltage gain appears when the full bridge jumps to a cross region of a half bridge, the LLC resonant converter obtains a track radius of a state before jumping, a track radius of a state after jumping and a switching frequency according to load current and input voltage, and calculates a control variable corresponding to an optimal state track mode I under the condition of cross region jumping, wherein the mode I control variable comprises control pulse cycle time length and a duty ratio. And adjusting the time length and the duty ratio of a control pulse period according to the mode-one control variable, accurately guiding a voltage state track of the resonant current-resonant capacitor to a target steady-state working point, further changing the voltage gain of the LLC resonant converter in the transition process of topology conversion, reducing the resonant current overshoot and the output voltage fluctuation caused by the topology conversion, and inhibiting the fluctuation of the output voltage in the transition process of the topology conversion. If the voltage gain jumps to the cross-region of the full bridge from the half bridge, the LLC resonant converter obtains the track radius of the state before jumping, the track radius of the state after jumping and the switching frequency according to the load current and the input voltage, and calculates control variables corresponding to a second optimal state track mode under the cross-region jumping condition, wherein the control variables of the second mode include the control pulse cycle time length and the duty ratio. And adjusting the time length and the duty ratio of the control pulse period according to the mode two control variables, accurately guiding the voltage state track of the resonant current-resonant capacitor to a target steady-state working point, further changing the voltage gain of the LLC resonant converter in the transition process of topology conversion, reducing the resonant current overshoot and the output voltage fluctuation caused by the topology conversion, and inhibiting the fluctuation of the output voltage in the transition process of the topology conversion. And if the voltage gain does not generate cross-region jump, the LLC resonant converter enters a linear control mode. Finally, if a shutdown instruction or a protection instruction is received, the LLC resonatesAnd (4) shutting down the converter or sealing the wave and entering a protection state, and if the interruption is not finished, entering a new round of control circulation.
FIG. 2 shows that the elements of the full-bridge LLC resonant converter comprise a primary side switch tube Q 1 -Q 4 Resonant inductor L r Resonant capacitor C r Transformer excitation inductance L m Transformer with turn ratio n:1, primary side leakage inductance L of transformer kp Secondary side leakage inductance L of transformer ks Equivalent turn-to-turn capacitance C of transformer TR Rectifier diode D 1 -D 4 Parasitic capacitance C of rectifier diode jc 。
Fig. 3 shows the process of the dc gain transition in a dc gain diagram. The trace transition is depicted as a black double-arrow curve, which is a dynamic process for dealing with sudden changes in the input voltage. The output voltage oscillation caused by topology deformation is reduced to the minimum, and the stabilization time of the system is shortened. This trajectory is not fixed and is represented in the figure as trajectory 1 to trajectory n. For example, if the desired output voltage is fixed, it depends on the instantaneous value of the input voltage. The exact value of the gain curve depends on the instantaneous value of the input voltage during the conversion. The whole transition process is smoother and more stable through accurate calculation and variable transition tracks.
FIGS. 4 (a) and 4 (b) are switching frequency-gain-output current f in full-bridge and half-bridge, respectively s -G-I o The three-dimensional curved surface searches the switching frequency in the full-bridge mode and the half-bridge mode according to the output current and the input voltage through the two-dimensional tables. Since the converter operates below the resonant frequency, the look-up table range is in the red box range.
FIGS. 5 (a) and 5 (b) are respectively the full-bridge and half-bridge lower track radii-gain-output current ρ -G-I o The three-dimensional curved surface of (2). The radius of the trajectory circles in the half-bridge mode and the full-bridge mode are looked up by the two-dimensional tables according to the output current and the input voltage. Since the converter operates below the resonant frequency, the look-up table range is in the red-box range.
FIG. 6 shows the transition from full bridge to half bridge and half bridge to full bridgeAnd (4) state tracks. FIG. 6 (a) shows the transition from full bridge to half bridge, t 0 -t 1 T of (a) 0 And (4) when the voltage suddenly increases and exceeds the lower limit of the gain provided by the full bridge, finishing linear control and giving the control right to the optimal trajectory control. The voltage applied to the resonant tank suddenly increases, and the state circle radius increases. At t 1 The point locus naturally enters a linear charging stage of the resonant capacitor and is represented as a horizontal straight line. At t 2 At the end of the positive pulse, the track enters the circular track of the latter half period, at t 3 Entering a linear charging phase at t 4 And when the optimal track control is finished, the control right is handed to linear control, the initial switching frequency is searched by a two-dimensional table, and the stable linear control state is entered.
FIG. 6 (b) shows the half-bridge to full-bridge transition, t 0 -t 1 T of 0 And when the voltage suddenly drops and exceeds the upper limit of the gain provided by the half bridge, the linear control is finished, and the control right is handed to the optimal track control. The voltage applied to the resonant tank drops suddenly and the state circle radius decreases. At t 1 The point locus naturally enters a resonant capacitor linear charging stage and is represented as a horizontal straight line. At t 2 At the end of the positive pulse, the track enters the circular track of the latter half period, at t 3 Entering a linear charging phase at t 4 And when the optimal track control is finished, the control right is handed to linear control, the initial switching frequency is searched by a two-dimensional table, and the stable linear control state is entered.
Fig. 7 shows the time domain key waveforms from full bridge to half bridge. The transition period in the drive signal is an asymmetric square waveform, the transition time and duty cycle are given by the above calculation, and the steady-state switching frequency after the transition is determined by a look-up table. In the transition from full bridge to half bridge, the period time length of the control pulse is adjusted according to a formula (13), the duty ratio of the control pulse is adjusted according to a formula (14), namely the period time length and the duty ratio of the control pulse are adjusted according to a mode-control variable, a driving signal of a switching tube of the LLC resonant converter is given, and t is enabled to be t 0 -t 1 T of 0 And (4) when the voltage suddenly increases and exceeds the lower limit of the gain provided by the full bridge, finishing the linear control and giving the control right to the optimal trajectory control. The resonance tank is charged with electricityThe pressure suddenly increases, and the state circle radius increases. At t 1 The point locus naturally enters a resonant capacitor linear charging stage and is represented as a horizontal straight line. At t 2 At the end of the positive pulse, the track enters the circular track of the latter half period, at t 3 Entering a linear charging phase at t 4 And when the optimal trajectory control is finished, the control right is handed to linear control, the initial switching frequency is searched by a two-dimensional table and enters a stable linear control state, namely, the voltage gain of the LLC resonant converter is changed in the transition process of topology conversion, the resonant current overshoot and the output voltage fluctuation caused by the topology conversion are reduced, and the fluctuation of the output voltage in the transition process of the topology conversion is restrained.
Fig. 8 shows the time domain key waveforms from half-bridge to full-bridge. The transition period in the drive signal is an asymmetric square waveform, the transition time and duty cycle are given by the above calculation, and the steady-state switching frequency after the transition is determined by a look-up table. In the transition from the half bridge to the full bridge, the period time length of the control pulse is adjusted according to a formula (22), the duty ratio of the control pulse is adjusted according to a formula (23), namely the period time length and the duty ratio of the control pulse are adjusted according to a mode-control variable, a driving signal of a switching tube of the LLC resonant converter is given, and t is enabled to be t 0 -t 1 T of 0 And (4) when the voltage suddenly increases and exceeds the upper limit of the gain which can be provided by the half bridge, the linear control is finished, and the control right is handed to the optimal track control. The voltage applied to the resonant tank drops suddenly and the state circle radius decreases. At t 1 The point locus naturally enters a resonant capacitor linear charging stage and is represented as a horizontal straight line. At t 2 At the moment the positive pulse is over, the track enters the circular track of the latter half period, at t 3 Entering a linear charging phase at t 4 And when the optimal trajectory control is finished, handing over the control right to linear control, searching the initial switching frequency by a two-dimensional table, and entering a stable linear control state, namely, changing the voltage gain of the LLC resonant converter in the transition process of topology conversion, reducing the resonant current overshoot and the output voltage fluctuation caused by the topology conversion, and inhibiting the fluctuation of the output voltage in the transition process of the topology conversion.
The above detailed description is intended to illustrate the objects, aspects and advantages of the present invention, and it should be understood that the above detailed description is only exemplary of the present invention and is not intended to limit the scope of the present invention, and any modifications, equivalents, improvements and the like made within the spirit and principle of the present invention should be included in the scope of the present invention.
Claims (5)
1. A control method of a variable topology resonant converter with smooth switching function is disclosed, wherein the variable topology resonant converter is a half-bridge/full-bridge LLC resonant converter; the converter mainly comprises a main circuit and a control circuit, and the topology of the main circuit is consistent with that of a full-bridge LLC converter; the main circuit topology comprises a primary side inverter circuit, a transformer and a secondary side rectifying circuit; the primary inverter circuit is composed of a full-bridge circuit, and is operated in a full-bridge state when the input voltage is low, and is controlled to be S when the input voltage is high 3 Off, S 4 Conducting to work in a half-bridge state; the optimal track control is adopted to limit the resonance current overshoot and the output voltage fluctuation in the topology transformation transition process; the control circuit also comprises a digital control circuit, a sampling circuit and a driving circuit; the sampling circuit is used for sampling the input voltage V in And an output current I o And voltage V o ；
The method is characterized in that: comprises the following steps of (a) carrying out,
measuring parameters and parasitic parameters of each device of the circuit, obtaining parasitic inductance by using a digital bridge, obtaining turn-to-turn capacitance of a transformer by electromagnetic simulation, obtaining parasitic capacitance of a semiconductor device by a data manual, building a half-bridge/full-bridge LLC resonant converter model containing the parasitic parameters in simulation software, and scanning input voltage under each load to obtain switching frequency-gain-output current f s -G-I o Three-dimensional curved surface and track circle radius-gain-output current rho-G-I o Wherein G = V o /V in (ii) a Establishing a state track model of the LLC resonant converter by taking the resonant capacitor voltage and the resonant inductor current of the LLC resonant converter as state variables;
step two, after the LLC resonant converter is started, detecting input voltage and load current of the LLC resonant converter, and judging the voltage gain change condition of the LLC resonant converter;
step three, if cross-region jumping does not occur in the voltage gain of the LLC resonant converter detected in the step two, the LLC resonant converter enters a linear control mode;
step four, if the LLC resonant converter voltage gain detected in the step two causes cross-region jump from the full bridge to the half bridge, the LLC resonant converter obtains the track radius of the state before the jump and the track radius and the switching frequency of the state after the jump according to the load current and the input voltage, and calculates a control variable corresponding to an optimal state track mode I under the cross-region jump condition, wherein the mode I control variable comprises the control pulse cycle time length and the duty ratio; adjusting the time length and the duty ratio of a control pulse cycle according to the mode-one control variable, accurately guiding a voltage state track of the resonant current-resonant capacitor to a target steady-state working point, further changing the voltage gain of the LLC resonant converter in the transition process of topology conversion, reducing resonant current overshoot and output voltage fluctuation caused by topology conversion, and inhibiting the fluctuation of the output voltage in the transition process of topology conversion;
step five, if the cross-region jump of the half bridge to the full bridge occurs to the LLC resonant converter voltage gain detected in the step two, the LLC resonant converter obtains the track radius of the state before the jump, the track radius of the state after the jump and the switching frequency according to the load current and the input voltage, and calculates the control variable corresponding to the optimal state track mode two under the cross-region jump condition, wherein the mode two control variable comprises the control pulse cycle time length and the duty ratio; adjusting the time length and the duty ratio of a control pulse cycle according to the mode two control variables, accurately guiding a voltage state track of the resonant current-resonant capacitor to a target steady-state working point, further changing the voltage gain of the LLC resonant converter in the transition process of topology conversion, reducing resonant current overshoot and output voltage fluctuation caused by topology conversion, and inhibiting the fluctuation of the output voltage in the transition process of topology conversion;
and step six, if a shutdown instruction or a protection instruction is received, the LLC resonant converter is shut down or wave-sealed and enters a protection state, if the LLC resonant converter returns to the step two to the step six, a new round of control circulation is entered, when the voltage gain does not cross the gain limit provided by the current mode, linear control is performed according to the step three, when the voltage gain crosses the gain limit provided by the current mode, optimal trajectory control is performed according to the step four and the step five, the voltage gain of the LLC resonant converter is changed in the transition process of topology conversion, the resonant current overshoot and the output voltage fluctuation caused by the topology conversion are reduced, and the fluctuation of the output voltage in the transition process of the topology conversion is restrained.
2. The method for controlling the variable topology resonant converter with the smooth switching function according to claim 1, wherein: the first implementation method comprises the following steps of,
an original part of an accurate model of a full-bridge LLC resonant converter comprises a primary side switch tube Q 1 -Q 4 Resonant inductor L r Resonant capacitor C r Transformer excitation inductance L m Transformer with turn ratio n:1, primary side leakage inductance L of transformer kp Secondary leakage inductance L of transformer ks Equivalent turn-to-turn capacitance C of transformer TR Rectifier diode D 1 -D 4 Parasitic capacitance C of rectifier diode jc (ii) a The input voltage is scanned under each load through simulation software to obtain switching frequency-gain-output current f s -G-I o Three-dimensional curved surface and track circle radius-gain-output current rho-G-I o Wherein G = V o /V in ；
For all voltage variables according to the output voltage V of LLC resonant converter o Performing per unit to obtain all current variables according to V o /Z 0 Per unit, wherein Z 0 Characteristic impedance for two elements:
resonant inductor current i of state variable Lr And resonant capacitor voltagev Cr The per unit value is i LrN And v CrN Establishing a phase plane model of the LLC resonant converter; the converter works in a boosting state below a resonance frequency, and in a half-bridge mode, the state track of the converter is divided into four sections, wherein the two sections are arcs shown in (2) and (3):
the other two sections are horizontal straight lines formed by linearly charging the resonant capacitor by exciting current, and the exciting current value is as follows:
in the full-bridge mode, the state locus is divided into four sections, wherein one section of the arc has the same expression as (2), and the other section of the arc is shown as (5):
the other two sections are horizontal straight lines formed by linearly charging the resonant capacitor by the exciting current, and the exciting current is the same as that in the step (4).
3. The method according to claim 2, wherein the method comprises: the implementation method of the fourth step is that,
the transition from full bridge to half bridge has t 0 -t 4 Five time nodes with input voltage V before transition in1 After jump is V in2 (ii) a Wherein t is 0 -t 1 Is obtained according to equation (6):
t 1 -t 0 ＝T r /2 (6)
according to the geometric relationship, get t 0 Resonance voltage:
where ρ is 1 Searching by a three-dimensional plane; and further obtaining the state circle radius of the transition state:
thus t 1 ，t 2 Resonance voltage at time:
where ρ is 2 Searching by a three-dimensional plane; linear charging of resonant capacitor according to excitation current to obtain t 1 -t 2 Time:
t 2 -t 1 ＝(C r (v CrN (t 2 )-v CrN (t 1 ))nV o )/I Lm (11)
the above formulas (6), (7), (8), (9), (10) and (11) are combined to obtain the total positive pulse time length of the transition period, namely the pulse period time length multiplied by the duty ratio:
switching frequency f after hopping according to three-dimensional plane search Vin2 Obtaining the total length of the transition period time and the duty ratio:
T tran ＝t total +0.5/f Vin2 (13)
D tran ＝t total /(t total +0.5/f Vin2 ) (14)
in the transition from full bridge to half bridge, the period time length of the control pulse is adjusted according to a formula (13), the duty ratio of the control pulse is adjusted according to a formula (14), namely the period time length and the duty ratio of the control pulse are adjusted according to a mode-control variable, a driving signal of a switching tube of the LLC resonant converter is given, and t is enabled to be t 0 -t 1 T of 0 The time voltage suddenly increases and exceeds the lower limit of gain provided by the full bridge, the linear control is finished, and the control right is handed to the optimal track control; the voltage applied to the resonant tank is suddenly increased, and the state circle radius is increased; at t 1 The point track naturally enters a resonant capacitor linear charging stage and is represented as a horizontal straight line; at t 2 At the moment the positive pulse is over, the track enters the circular track of the latter half period, at t 3 Entering a linear charging phase at t 4 And when the optimal trajectory control is finished, handing over the control right to linear control, searching the initial switching frequency by a two-dimensional table, and entering a stable linear control state, namely, changing the voltage gain of the LLC resonant converter in the transition process of topology conversion, reducing the resonant current overshoot and the output voltage fluctuation caused by the topology conversion, and inhibiting the fluctuation of the output voltage in the transition process of the topology conversion.
4. The method according to claim 3, wherein the method comprises: the method is implemented by the steps of,
the transition from half-bridge to full-bridge has t 0 -t 4 Five time nodes with input voltage V before transition in1 After jump is V in2 (ii) a Wherein t is 0 -t 1 Is obtained according to equation (15):
t 1 -t 0 ＝T r /2 (15)
according to the geometric relationship, get t 0 Resonance voltage:
where ρ is 1 Searching by a three-dimensional plane; further obtaining the state circle radius of the transition state:
thus t 1 ，t 2 Resonance voltage at time:
where ρ is 2 Searching by a three-dimensional plane; linear charging of resonant capacitor according to excitation current to obtain t 1 -t 2 Time:
t 2 -t 1 ＝(C r (v CrN (t 2 )-v CrN (t 1 ))nV o )/I Lm (20)
the above formulas (15), (16), (17), (18), (19) and (20) are combined to obtain the total positive pulse time length of the transition period, namely the pulse period time length multiplied by the duty ratio:
switching frequency f after jump according to three-dimensional plane search Vin2 Obtaining the total time length of the transition period and the duty ratio:
T tran ＝t total +0.5/f Vin2 (22)
D tran ＝t total /(t total +0.5/f Vin2 ) (23)
in the transition from half-bridge to full-bridgeAdjusting the time length of the control pulse period according to a formula (22), adjusting the duty ratio of the control pulse according to a formula (23), namely adjusting the time length of the control pulse period and the duty ratio according to a mode-control variable, giving a driving signal of a switching tube of the LLC resonant converter, and enabling t to be t 0 -t 1 T of 0 The time voltage suddenly increases and exceeds the upper limit of the gain provided by the half bridge, the linear control is finished, and the control right is handed to the optimal track control; the voltage applied to the resonant tank drops suddenly, and the state circle radius is reduced; at t 1 The point track naturally enters a resonant capacitor linear charging stage and is represented as a horizontal straight line; at t 2 At the moment the positive pulse is over, the track enters the circular track of the latter half period, at t 3 Entering a linear charging phase at t 4 And when the optimal trajectory control is finished, handing over the control right to linear control, searching the initial switching frequency by a two-dimensional table, and entering a stable linear control state, namely, changing the voltage gain of the LLC resonant converter in the transition process of topology conversion, reducing the resonant current overshoot and the output voltage fluctuation caused by the topology conversion, and inhibiting the fluctuation of the output voltage in the transition process of the topology conversion.
5. The method for controlling a variable topology resonant converter with smooth switching function according to claim 2, 3 or 4, characterized in that: the simulation software adopts PSIM software.
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