CN114142236B - Narrow-edge waveguide slot antenna - Google Patents
Narrow-edge waveguide slot antenna Download PDFInfo
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- CN114142236B CN114142236B CN202210105461.XA CN202210105461A CN114142236B CN 114142236 B CN114142236 B CN 114142236B CN 202210105461 A CN202210105461 A CN 202210105461A CN 114142236 B CN114142236 B CN 114142236B
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
- H01Q13/10—Resonant slot antennas
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/12—Supports; Mounting means
- H01Q1/22—Supports; Mounting means by structural association with other equipment or articles
- H01Q1/24—Supports; Mounting means by structural association with other equipment or articles with receiving set
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
- H01Q13/20—Non-resonant leaky-waveguide or transmission-line antennas; Equivalent structures causing radiation along the transmission path of a guided wave
- H01Q13/22—Longitudinal slot in boundary wall of waveguide or transmission line
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q21/00—Antenna arrays or systems
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q21/00—Antenna arrays or systems
- H01Q21/0006—Particular feeding systems
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Abstract
The invention discloses a narrow-edge waveguide slot antenna, which comprises: the first radiation waveguide and the second radiation waveguide are arranged along the same straight line; a plurality of inclined radiation slots are formed in one side of each narrow edge of the first radiation waveguide and one side of each narrow edge of the second radiation waveguide, one end of the first radiation waveguide is connected with one end of a first feed waveguide, and the other end of the first feed waveguide is connected with one port of the sum-difference beam network; one end of the second radiation waveguide is connected with one end of a second feed waveguide, and the other end of the second feed waveguide is connected with the other port of the sum-difference beam network; the invention divides a single radiation waveguide into two parts to be respectively designed, meets the feed condition of sum and difference beams through the design of a sum and difference beam network and a feed waveguide, realizes sum and difference beams in the narrow beam direction, and improves the angle measurement precision of a radar system.
Description
Technical Field
The invention relates to the field of microwave radio frequency, in particular to a sum-difference system low-side lobe narrow-side waveguide slot antenna.
Background
The waveguide slot antenna has excellent structural performance, stable and reliable electrical performance and wide application in radar systems. With the development of radar systems, the requirements for waveguide slot antennas are also higher and higher, and functions of low sidelobe, broadband, and difference beam, phase scanning support and the like are required. The radar mostly adopts a single-beam working mode, and only distance and direction information of a target can be obtained. To achieve accurate tracking of the target, a monopulse antenna system may be employed. The monopulse antenna system generates sum beams and difference beams through the antenna, and completes the space angle of a detection target and a measurement target by utilizing the comparison of received signals of the sum beams and the difference beams. The conventional narrow-side waveguide slot antenna with the sum and difference beam function is arranged by a plurality of waveguides, the sum and difference beams are realized in the wide beam direction, and the capability of forming the sum and difference beams in the narrow beam direction is not provided.
Disclosure of Invention
To solve the above problems, the present invention provides an antenna that realizes sum and difference beams in a narrow beam direction and has low sidelobes.
In order to achieve the purpose, the invention provides the technical scheme that: a narrow-sided waveguide slot antenna, comprising: the radiation device comprises a first radiation waveguide and a second radiation waveguide, wherein the first radiation waveguide and the second radiation waveguide are arranged along the same straight line, and a gap is arranged between the first radiation waveguide and the second radiation waveguide; a plurality of inclined radiation gaps are formed in one side of the narrow sides of the first radiation waveguide and the second radiation waveguide, the included angle between each radiation gap and the extension direction of the first radiation waveguide and the extension direction of the second radiation waveguide are greater than or equal to 45 degrees, and two adjacent radiation gaps on the same radiation waveguide are not parallel; one end of the first radiation waveguide is connected with one end of a first feed waveguide, and the other end of the first feed waveguide is connected with one port of the sum-difference beam network; one end of the second radiation waveguide is connected with one end of a second feed waveguide, and the other end of the second feed waveguide is connected with the other port of the sum-difference beam network.
Preferably, the distance between the center points of two adjacent radiation slits is 0.448 times the wavelength of the waveguide.
Preferably, a reserved space is provided between the first radiation waveguide and the second feed waveguide.
As a preferable technical solution, one end of the first radiation waveguide far from the first feed waveguide is connected with a first load, and the first load is disposed in the reserved space.
Preferably, a second load is connected to an end of the second radiation waveguide away from the second feed waveguide.
Preferably, the lengths of the first feed waveguide and the second feed waveguide are different, and the desired phase difference is achieved by adjusting the lengths of the first feed waveguide and the second feed waveguide.
As a preferred technical solution, a first transition section is disposed between the first radiation waveguide and the first feed waveguide, and the first transition section is U-shaped.
As a preferred technical solution, a second transition section is disposed between the second radiation waveguide and the second feed waveguide, and the second transition section is Z-shaped.
As a preferred technical solution, the sum and difference beam network is a four-port waveguide magic T.
Preferably, the amplitude weighted distribution of the radiation waveguide is determined by the following method:
step 1, determining an optimized variable array
The side lobe level requires R, and the number of sampling points is M;
step 2, constructing a limit array L (M) according to the side lobe level requirement R and the number M of sampling points;
and 5, optimizing and calculating the values of the N variables to minimize the cost function value and output the optimal assignment.
Compared with the prior art, the invention has the beneficial effects that:
(1) a single radiation waveguide is divided into two parts to be respectively designed, the feed conditions of sum and difference beams are met through the design of a sum and difference beam network and a feed waveguide, the sum and difference beams are realized in the narrow beam direction, and the angle measurement precision of the radar system is improved.
(2) Through the design of reasonably selecting the non-standard waveguide size and the miniaturized load, the distance between the radiation waveguides is reduced as much as possible, the side lobe level deterioration caused by the increase of the distance between the two radiation waveguides is reduced, and the difficulty in realizing the low side lobe level is reduced.
(3) Amplitude weighting distribution of the slot antenna array is improved by adopting an amplitude optimization algorithm, and the amplitude weighting distribution is completed by adjusting the combination of the inclination angle and the cutting depth of the radiation slot, so that the low side lobe design is realized, and the anti-interference capability of the radar system is improved.
Drawings
Fig. 1 is an overall structural diagram of a narrow-side waveguide slot antenna according to an embodiment of the present invention;
fig. 2 is a structural diagram of a four-port waveguide magic T according to an embodiment of the present invention;
FIG. 3 is a schematic diagram of a miniaturized load according to an embodiment of the present invention;
FIG. 4 is a 1GHz sum difference beam pattern provided by an embodiment of the invention;
fig. 5 is a diagram of 4GHz sum and difference beam patterns provided by an embodiment of the present invention.
Detailed Description
The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
As used in this application and the appended claims, the terms "a," "an," "the," and/or "the" are not intended to be inclusive in the singular, but rather are intended to be inclusive in the plural unless the context clearly dictates otherwise. In general, the terms "comprises" and "comprising" merely indicate that steps and elements are included which are explicitly identified, that the steps and elements do not form an exclusive list, and that a method or apparatus may include other steps or elements.
The relative arrangement of the components and steps, the numerical expressions, and numerical values set forth in these embodiments do not limit the scope of the present application unless specifically stated otherwise. Meanwhile, it should be understood that the sizes of the respective portions shown in the drawings are not drawn in an actual proportional relationship for the convenience of description. Techniques, methods, and apparatus known to one of ordinary skill in the relevant art may not be discussed in detail but are intended to be part of the specification where appropriate. In all examples shown and discussed herein, any particular value should be construed as merely illustrative, and not limiting. Thus, other examples of the exemplary embodiments may have different values. It should be noted that: like reference numbers and letters refer to like items in the following figures, and thus, once an item is defined in one figure, it need not be discussed further in subsequent figures.
It should be noted that the terms "first", "second", and the like are used to define the components, and are only used for convenience of distinguishing the corresponding components, and the terms have no special meanings unless otherwise stated, and therefore, the scope of protection of the present application is not to be construed as being limited. Further, although the terms used in the present application are selected from publicly known and used terms, some of the terms mentioned in the specification of the present application may be selected by the applicant at his or her discretion, the detailed meanings of which are described in relevant parts of the description herein. Further, it is required that the present application is understood not only by the actual terms used but also by the meaning of each term lying within.
Referring to fig. 1, the present embodiment provides a narrow-side waveguide slot antenna, including a first radiation waveguide 1 and a second radiation waveguide 2, where the first radiation waveguide 1 and the second radiation waveguide 2 are disposed along a same straight line, and a gap is formed between the first radiation waveguide 1 and the second radiation waveguide 2, where the gap may affect a side lobe level, and as a ratio increases, the side lobe level is raised significantly. In order to reduce the degree of side lobe level degradation, in this embodiment, a reasonable non-standard waveguide size is selected, so that the waveguide wavelength is as large as possible.
Furthermore, a plurality of inclined radiation gaps 11 and radiation gaps 21 are respectively arranged on one side of the narrow sides of the first radiation waveguide 1 and the second radiation waveguide 2 to form a gap array, the included angle between the radiation gap 11 and the radiation gap 21 and the extension direction of the first radiation waveguide 1 and the extension direction of the second radiation waveguide 2 are greater than or equal to 45 degrees, and two adjacent radiation gaps on the same radiation waveguide are not parallel; in addition, the distance between the center points of two adjacent radiation slits is 0.448 times the wavelength of the waveguide, which can effectively reduce the degree of deterioration of the side lobe level.
Regarding to the size of the radiation gap, the size parameters of the gap are obtained through the combined simulation of numerical calculation software and electromagnetic simulation software and fast iterative calculation, and the inclination angle and the cut-in depth are determined by the target field distribution.
The amplitude weighting distribution for the radiation guide is calculated by:
step 1, determining an optimized variable array
The side lobe level requirement R and the number of sampling points M;
step 2, constructing a limit array L (M) according to the side lobe level requirement R and the number M of sampling points;
and 5, optimizing and calculating the values of the N variables to minimize the cost function value and output the optimal assignment.
In the traditional method, N variable values are needed to be optimized, because the amplitude weighting distribution is basically a monotonous curve, the curve segments can be regarded as being composed of straight line segments with different slopes, the slopes of the adjacent straight lines are kept consistent, the improved variable values in the optimization algorithm in the embodiment can change the length of the straight line segments according to the needs, and the combination of various slopes can be adopted, so that the calculation accuracy is improved, the quantity of the variables needing to be optimized can be greatly reduced, and the calculation speed and the convergence speed of the optimization algorithm are improved.
The distribution of the radiation energy of the antenna aperture surface is determined by the inclination angle combination of the radiation gaps, the inclination angle combination of the radiation gaps can be obtained by reverse deduction of the amplitude weighted distribution obtained by the calculation, and the combination of the inclination angle and the cutting depth of the radiation gaps ensures that the size of each radiation gap is close to the resonance length.
Further, referring to fig. 1, one end of a first radiation waveguide 1 is connected to one end of a first feed waveguide 3, and the other end of the first feed waveguide 3 is connected to one port of a sum and difference beam network 4; one end of the second radiation waveguide 2 is connected to one end of a second feed waveguide 5, and the other end of the second feed waveguide 5 is connected to the other port of the sum and difference beam network 4.
In this embodiment, the difference beam network is a four-port waveguide magic T, a structure diagram of which is shown in fig. 2, a round-table and cylindrical tuning and matching structure is adopted inside the network, so that a good broadband characteristic and port isolation are obtained, a first port 41 and a second port 42 of the difference beam network are respectively connected with the first feed waveguide 3 and the second feed waveguide 5, and/or a difference beam port is connected with the radar transceiving component, wherein a third port 43 is a sum beam port, and a fourth port 44 is a difference beam port.
In this embodiment, the lengths of the first feeding waveguide 3 and the second feeding waveguide 5 are not the same, and the desired phase difference is achieved by adjusting the lengths of the first feeding waveguide 3 and the second feeding waveguide 5, specifically, since the phase characteristic of the waveguide is also a curve varying with frequency, and the slope of the curve varies with the variation of the waveguide length, the desired phase difference can be obtained at two ports by feeding through two waveguides with different lengths by using this characteristic of the waveguide.
In the present embodiment, a first transition section 6 is disposed between the first radiation waveguide 1 and the first feed waveguide 3, and the first transition section 6 has a U shape. Similarly, a second transition section 7 is arranged between the second radiation guide 2 and the second feed guide 5, and the second transition section 7 is Z-shaped.
Further, a reserved space is provided between the first radiation waveguide 1 and the second feed waveguide 5, and the reserved space is used for placing a load, in this embodiment, a first load 8 is connected to one end of the first radiation waveguide 1 far away from the first feed waveguide 3, and the first load 8 is arranged in the reserved space. In addition, a second load 9 is connected to an end of the second radiation waveguide 2 remote from the second feed waveguide 5.
In order to introduce the beneficial effects of the invention more fully, the following experiments verify the effects of the invention, the working frequency band of the experiment is 9.1-9.4GHz, the waveguide adopts a non-standard size, the wide side size is 19mm, the narrow side size is 9mm, the wall thickness is 1.3mm, and the whole length of the antenna is 3834 mm. Each radiation waveguide comprises 70 radiation slots, the slot spacing is 26.8mm, and the slot width is 2 mm. The distance between the two radiation waveguides is 40mm, and is about 1.5 times the distance between the radiation gaps.
In addition, referring to fig. 3, fig. 3 is a schematic diagram of a miniaturized load local amplification adopted in the experiment, and the microwave absorbing material is hydroxyl iron, which has the characteristics of wide frequency band and good wave absorbing performance. To achieve the miniaturization of the load, a cylindrical shape is selected as the shape of the absorber of the load. The cylindrical wave-absorbing material is inserted from a narrow side opening of the feed waveguide, so that the wave-absorbing material is positioned on a narrow side central line of the feed waveguide and is positioned at a proper position away from a short-circuit surface of the feed waveguide. In order to ensure the absorption effect of the load, the size D and the position D of the wave-absorbing material and the depth h of the wave-absorbing material inserted into the waveguide need to be adjusted during design. In this embodiment, the diameter D of the cylindrical wave-absorbing material is 7mm, the distance D from the short-circuit surface is 10.4mm, and the height h of the wave-absorbing material penetrating into the waveguide is 6 mm.
The experimental results are shown in fig. 4 and fig. 5, where fig. 4 is a 1GHz sum-difference beam pattern, fig. 5 is a 4GHz sum-difference beam pattern, the abscissa in the figure represents an angle, the ordinate represents an amplitude value, the solid line represents a sum pattern, and the dotted line represents a difference pattern, and it can be seen from the figure that the narrow-edge waveguide slot antenna provided by the embodiment realizes sum-difference beams and a-25 dB side lobe level in the range of 9GHz to 9.4 GHz.
The above description is only an embodiment of the present invention, and is not intended to limit the scope of the present invention, and all equivalent structures or equivalent processes performed by the present specification and the attached drawings, or directly or indirectly applied to other related technical fields, are included in the scope of the present invention.
Claims (8)
1. A narrow-sided waveguide slot antenna, comprising: the radiation device comprises a first radiation waveguide and a second radiation waveguide, wherein the first radiation waveguide and the second radiation waveguide are arranged along the same straight line, and a gap is arranged between the first radiation waveguide and the second radiation waveguide; a plurality of inclined radiation gaps are formed in one side of the narrow sides of the first radiation waveguide and the second radiation waveguide, the included angle between each radiation gap and the extension direction of the first radiation waveguide and the extension direction of the second radiation waveguide are greater than or equal to 45 degrees, and two adjacent radiation gaps on the same radiation waveguide are not parallel;
one end of the first radiation waveguide is connected with one end of a first feed waveguide, and the other end of the first feed waveguide is connected with one port of the sum-difference beam network; one end of the second radiation waveguide is connected with one end of a second feed waveguide, and the other end of the second feed waveguide is connected with the other port of the sum-difference beam network;
a reserved space is arranged between the first radiation waveguide and the second feed waveguide; one end, far away from the first feed waveguide, of the first radiation waveguide is connected with a first load, and the first load is arranged in the reserved space.
2. The narrow-sided waveguide slot antenna of claim 1, wherein: the distance between the center points of two adjacent radiation slits is 0.448 times the wavelength of the waveguide.
3. The slot antenna of claim 1, wherein: and one end of the second radiation waveguide far away from the second feed waveguide is connected with a second load.
4. The slot antenna of claim 1, wherein: the lengths of the first feed waveguide and the second feed waveguide are different, and the expected phase difference is achieved by adjusting the lengths of the first feed waveguide and the second feed waveguide.
5. The narrow-sided waveguide slot antenna of claim 1 or 4, wherein: a first transition section is arranged between the first radiation waveguide and the first feed waveguide, and the first transition section is U-shaped.
6. The narrow-sided waveguide slot antenna of claim 1 or 4, wherein: and a second transition section is arranged between the second radiation waveguide and the second feed waveguide and is Z-shaped.
7. The slot antenna of claim 1, wherein: the sum and difference beam network is a four-port waveguide magic T.
8. The slot antenna of claim 1, wherein: the amplitude weighted distribution of the radiation guide is determined by:
step 1, determining an optimized variable array
The side lobe level requirement R and the number of sampling points M;
step 2, constructing a limit array L (M) according to the side lobe level requirement R and the number M of sampling points;
step 3, for N variables
Randomly assigning values according to 0-1, and calculating to obtain a directional diagram array f (M);
step 4, calculating cost function value
In which only the calculation is carried out
Point (2), otherwise, is 0;
and 5, optimizing and calculating the values of the N variables to minimize the cost function value and output the optimal assignment.
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| CN202210105461.XA CN114142236B (en) | 2022-01-28 | 2022-01-28 | Narrow-edge waveguide slot antenna |
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| CN202210105461.XA CN114142236B (en) | 2022-01-28 | 2022-01-28 | Narrow-edge waveguide slot antenna |
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Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101150224A (en) * | 2007-10-31 | 2008-03-26 | 中国电子科技集团公司第三十八研究所 | Broadband dual L wave guide narrow edge gap antenna array |
| CN201549575U (en) * | 2009-05-30 | 2010-08-11 | 四川九洲电器集团有限责任公司 | Electric bridge for millimeter wave double-channel plate antenna |
| CN108631054A (en) * | 2018-03-29 | 2018-10-09 | 西安电子工程研究所 | Mix the slot array antenna of feed |
| CN111864377A (en) * | 2020-07-29 | 2020-10-30 | 中国电子科技集团公司第十四研究所 | Broadband collinear seam waveguide slot antenna |
Family Cites Families (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP3565059B1 (en) * | 2018-04-30 | 2021-04-07 | NXP USA, Inc. | Antenna with switchable beam pattern |
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- 2022-01-28 CN CN202210105461.XA patent/CN114142236B/en active Active
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101150224A (en) * | 2007-10-31 | 2008-03-26 | 中国电子科技集团公司第三十八研究所 | Broadband dual L wave guide narrow edge gap antenna array |
| CN201549575U (en) * | 2009-05-30 | 2010-08-11 | 四川九洲电器集团有限责任公司 | Electric bridge for millimeter wave double-channel plate antenna |
| CN108631054A (en) * | 2018-03-29 | 2018-10-09 | 西安电子工程研究所 | Mix the slot array antenna of feed |
| CN111864377A (en) * | 2020-07-29 | 2020-10-30 | 中国电子科技集团公司第十四研究所 | Broadband collinear seam waveguide slot antenna |
Non-Patent Citations (1)
| Title |
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| 基片集成波导单脉冲缝隙天线阵列;王思捷等;《无线通信技术》;20200915(第03期);第26-30页 * |
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