CN113965139A - Thyristor and IGBT mixed three-phase motor two-phase frequency conversion control circuit and method thereof - Google Patents

Thyristor and IGBT mixed three-phase motor two-phase frequency conversion control circuit and method thereof Download PDF

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Publication number
CN113965139A
CN113965139A CN202111293021.3A CN202111293021A CN113965139A CN 113965139 A CN113965139 A CN 113965139A CN 202111293021 A CN202111293021 A CN 202111293021A CN 113965139 A CN113965139 A CN 113965139A
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phase
thyristor
circuit
diode
motor
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谢仕宏
梁荣茂
梁力
杨智浩
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Shaanxi University of Science and Technology
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Shaanxi University of Science and Technology
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
    • H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
    • H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
    • H02M5/443—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a thyratron or thyristor type requiring extinguishing means
    • H02M5/45—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
    • H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
    • H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
    • H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/505—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means
    • H02M7/515—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P1/00—Arrangements for starting electric motors or dynamo-electric converters
    • H02P1/16—Arrangements for starting electric motors or dynamo-electric converters for starting dynamo-electric motors or dynamo-electric converters
    • H02P1/26—Arrangements for starting electric motors or dynamo-electric converters for starting dynamo-electric motors or dynamo-electric converters for starting an individual polyphase induction motor
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/16—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the circuit arrangement or by the kind of wiring
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P2207/00—Indexing scheme relating to controlling arrangements characterised by the type of motor
    • H02P2207/01—Asynchronous machines

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Ac Motors In General (AREA)
  • Inverter Devices (AREA)

Abstract

The invention belongs to the technical field of AC-DC-AC frequency converters, and particularly relates to a thyristor and IGBT mixed three-phase motor two-phase frequency conversion control circuit and a control method thereof. The existing three-phase six-switch frequency converter has more switch power devices, the three-phase four-switch inverter has fewer switch power devices, the motor has larger torque pulsation and lower loading capacity. The invention provides a thyristor and IGBT mixed three-phase motor two-phase frequency conversion control circuit, which comprises a single chip microcomputer, a driving circuit, a rectifying circuit, a pumping voltage limiting circuit, a filter circuit, a voltage sampling circuit and an inverter circuit, wherein the two-phase frequency conversion control motor is adopted, sine modulation waves with the phase difference of 60 degrees are used for pulse width modulation, and thyristors and IGBTs are mixed in the frequency conversion circuit, so that power switching devices are reduced, fewer element faults exist, the production cost and the maintenance cost are greatly reduced, and the normal frequency conversion speed regulation of a motor under the two-phase control is realized.

Description

Thyristor and IGBT mixed three-phase motor two-phase frequency conversion control circuit and method thereof
Technical Field
The invention belongs to the technical field of AC-DC-AC frequency converters, and particularly relates to a thyristor and IGBT mixed two-phase frequency conversion control circuit of a three-phase motor and a control method thereof.
Background
At present, the traditional voltage source type AC-DC-AC three-phase six-switch frequency converter is widely applied to the speed regulation process of a three-phase asynchronous motor, and the traditional topological structure can meet the speed regulation requirement under most conditions by utilizing the characteristics of an IGBT. Based on the classical topological structure, a three-phase four-switch topological structure for reducing the use number of the IGBTs is further derived. Because the voltage source type inversion is still used as a basic structure, the three-phase four-switch speed regulation method can be improved by a conventional control strategy. The V/F control is used in the speed regulating system of the AC motor, namely, the rotating speed of the motor is regulated by changing the frequency of the variable voltage, and the basic idea is that the motor steady-state equation is used as the basis, the amplitude and the frequency of the power supply voltage of the motor are regulated in the same proportion to realize the control that the voltage-frequency ratio is a constant value based on the constant air gap flux, the voltage and the frequency of the inversion output are changed by changing the modulation wave in the pulse width modulation technology, and the method is easy to realize, has high reliability and is still applicable to the two-phase four-switch control of the three-phase motor.
When one phase of a load is connected to the midpoint of a bus power supply to form a topology structure of four-switch inversion, the bus power supply voltage is reduced by half, different control methods are greatly influenced, and the four-switch inversion is also the main reason mainly used as a fault-tolerant and short-time coping strategy. The reduction of the voltage of the direct current power supply in the process of sinusoidal pulse width modulation enables the effective value of the output alternating current to be reduced to 1/2; in the space voltage vector pulse width modulation process: (1) because the number of the switching tubes is reduced, the three-phase four-switch inverter can only output four basic voltage vectors with phases sequentially different by 90 degrees, compared with the traditional six-switch operation mode, the number of space voltage vector sectors is reduced from six to four, zero voltage vectors are lacked, the amplitude of the voltage vectors is asymmetric, the switching of the voltage vectors is not smooth enough in the inversion process, the inverted output is not as fine as that of six switches, and the torque pulsation of a motor is larger; 2) the amplitude of the output voltage vector is reduced to 1/2, which causes the output torque of the motor to be reduced sharply and the load capacity to be reduced, therefore, the performance of four-switch speed regulation is reduced greatly compared with the traditional frequency converter. Therefore, the traditional four-switch inversion control can effectively reduce the use of full-control devices, but can only be used as a coping method when six-switch inversion fails.
Disclosure of Invention
The invention aims to solve the problems in the prior art and provides a thyristor and IGBT mixed three-phase motor two-phase frequency conversion control circuit and a control method thereof.
In order to achieve the purpose, the invention adopts the following technical scheme to realize the purpose:
a thyristor and IGBT mixed two-phase frequency conversion control circuit of a three-phase motor comprises a single chip microcomputer, a driving circuit, a rectifying circuit, a pumping voltage limiting circuit, a filter circuit, a voltage sampling circuit and an inverter circuit, wherein the rectifying circuit, the pumping voltage limiting circuit and the filter circuit are sequentially connected, the output end of the filter circuit is respectively connected with the input end of the inverter circuit and the W of the motor, the output end of the inverter circuit is connected with U, V two phases of the motor,
the output end of the single chip microcomputer is connected with the input end of the driving circuit and used for controlling the driving circuit, the driving circuit is respectively connected with the input end of the pumping voltage limiting circuit and the input end of the inverter circuit, the output end of the voltage sampling circuit is connected with the single chip microcomputer, and the input end of the voltage sampling circuit is connected with the output end of the rectifying circuit.
In the above scheme, the voltage sampling circuit includes a resistor R2, a resistor R3, and a VSM025 isolation type hall voltage sensor, an input end of the VSM025 isolation type hall voltage sensor is connected to two ends of the resistor R3, and an output end of the VSM025 isolation type hall voltage sensor is connected to the single chip microcomputer.
In the above scheme, the pump-up voltage limiting circuit includes an IGBT1, a resistor R1, and a diode D1, wherein a collector of the IGBT1 is connected to a cathode of the diode D1, a gate of the IGBT1 is connected to an output terminal of the driving circuit, and an emitter of the IGBT1 is connected to an anode of the diode D1 and the resistor R1, respectively.
In the above scheme, the filter circuit includes a capacitor C1 and a capacitor C2, the capacitors C1 and C2 are connected in series, a midpoint E between the capacitor C1 and the capacitor C2 is connected to a W of the motor, and U, V two-phase voltages output by the inverter circuit have a phase difference of 60 °.
In the above scheme, the inverter circuit comprises a U-phase inverter circuit and a V-phase inverter circuit,
the U-phase inverter circuit comprises a thyristor VT1, a thyristor VT2, an IGBT2, a diode D2, a diode D3, a diode D4, a diode D5 and a capacitor C3, wherein the gate electrode of the IGBT2 is connected with the output end of the drive circuit,
the cathode of the thyristor VT1 is respectively connected with the collector of the IGBT2 and the anode of the diode D2, the gate of the thyristor VT1 is connected with the output end of the driving circuit, the anode of the thyristor VT1 is connected with the cathode of the diode D2,
the anode of the thyristor VT2 is connected with the emitter of the IGBT2 and the cathode of the diode D5, the gate of the thyristor VT2 is connected with the output end of the driving circuit, the cathode of the thyristor VT2 is connected with the anode of the diode D5,
a capacitor C3 is connected in parallel between the collector and the emitter of the IGBT2, and the U of the motor is connected between diodes D3 and D4;
the V-phase inverter circuit comprises a thyristor VT3, a thyristor VT4, an IGBT3, a diode D6, a diode D7, a diode D8, a diode D9 and a capacitor C4, wherein the gate of the IGBT3 is connected with the output end of the drive circuit,
the cathode of the thyristor VT3 is respectively connected with the collector of the IGBT3 and the anode of the diode D6, the gate of the thyristor VT3 is connected with the output end of the driving circuit, the anode of the thyristor VT3 is connected with the cathode of the diode D6,
the anode of the thyristor VT4 is connected with the emitter of the IGBT3 and the cathode of the diode D9, the gate of the thyristor VT4 is connected with the output end of the driving circuit, the cathode of the thyristor VT4 is connected with the anode of the diode D9,
a capacitor C4 is connected in parallel between the collector and the emitter of the IGBT3, and the V phase of the motor is connected between diodes D7 and D8.
In another aspect of the present invention, a method for controlling a four-leg frequency conversion soft starter based on forced commutation is provided, where the method includes: the voltage of the W phase of the motor is taken as a reference potential point, an open-loop constant-voltage frequency ratio control method is adopted, sine modulation waves with the phase difference of 60 degrees are used for pulse width modulation, the single chip microcomputer controls the drive circuit to generate 7 paths of PWM waves, PWM1 is used for controlling the pump generation voltage limiting circuit by using the IGBT1, PWM2-PWM7 is used for carrying out two-phase inversion on the IGBT2, the thyristor VT1, the thyristor VT2, the thyristor VT4, the IGBT3 and the thyristor VT3 by using an inverter circuit U, V, the amplitude and the frequency of two phases are adjustable, and the alternating voltage with the phase difference of 60 degrees is output by taking the reference phase W as reference.
The method further comprises the step that when the voltage measured by the VSM025 isolation type Hall voltage sensor is larger than the set safety voltage, the driving circuit generates PWM1 to perform energy consumption braking to prevent the direct current bus overvoltage, the PWM3 and the PWM4 are complementary pulses, the respective dead time of the PWM3 and the PWM4 is larger than the turn-off time of the IGBT2, the PWM3 and the PWM4 perform OR logic operation to generate PWM2, the sine modulation wave generating the PWM7 lags to generate the sine modulation wave of the PWM3 by 60 degrees in electrical angle, the PWM5 and the PWM7 are complementary pulses, the respective dead time of the PWM5 and the PWM7 is larger than the turn-off time of the IGBT3, and the PWM5 and the PWM7 perform OR logic operation to generate PWM 6.
The method also comprises the following control process of the U phase of the inverter circuit: in the positive half cycle of the current flowing in the motor U phase, when the thyristors VT1 and the IGBT2 are switched on, the thyristor VT2 is switched off, the current flows into the motor U phase through the thyristor VT1 → the IGBT2 → the diode D4, the voltage at the two ends of the capacitor C3 is approximately zero, when the IGBT2 is switched off, the thyristor VT1 charges the capacitor C3, the current flows to the thyristor VT1 → the capacitor C3 → the diode D4 to flow into the motor U phase, when the voltage of the capacitor C3 rises to the voltage of a direct current bus, the current of the thyristor VT1 drops to zero and is switched off, the diodes D5 and D4 are switched on in follow current, and the current of the U phase flows to the diode D5 → the diode D4 to flow into the motor U phase; in the negative half cycle of the motor U-phase current flowing out, when the IGBT2 and the thyristor VT2 are switched on, the voltage at two ends of the capacitor C3 is approximately zero, the current direction is the motor U phase → the diode D3 → the IGBT2 → the thyristor VT2, when the IGBT2 is switched off, the motor U-phase current is charged to the capacitor C3, the current flows to the motor U phase → the diode D3 → the capacitor C3 → the thyristor VT2, when the voltage of the capacitor C3 rises to the direct-current bus voltage, the current of the thyristor VT2 drops to zero and is switched off, the follow currents of the diodes D3 and D2 are switched on, and the U-phase current flows to the motor U phase → the diode D3 → the diode D2; the control process of the inverter circuit V phase is the same as the principle of the inverter circuit U phase.
Compared with the prior art, the invention has the following beneficial effects:
the invention provides a thyristor and IGBT mixed three-phase motor two-phase frequency conversion control circuit and a control method thereof.A two-phase frequency conversion control motor is adopted, sine modulation waves with the phase difference of 60 degrees are used for pulse width modulation, and thyristors and IGBTs are mixed in the frequency conversion circuit, thereby reducing the switching devices of the traditional AC-DC-AC three-phase frequency conversion technology, simplifying the circuit structure, having fewer element faults in the two-phase frequency conversion circuit, greatly reducing the production cost and the maintenance cost, realizing the normal frequency conversion speed regulation of a motor under the two-phase control and increasing the working stability of the motor.
Drawings
FIG. 1 is a topological diagram of a thyristor and IGBT mixed three-phase motor two-phase frequency conversion control circuit of the invention;
FIG. 2 is a voltage waveform of the rectified DC bus of the present invention;
in fig. 3, (a) and (b) are the rotation speed waveform and the current waveform of the three-phase motor of the present invention, respectively.
Detailed Description
The invention is described in further detail below with reference to the accompanying drawings:
the two-phase frequency conversion control circuit of the three-phase motor with the thyristor and the IGBT mixed provided by the embodiment of the invention comprises a single chip microcomputer, a driving circuit, a rectifying circuit, a pumping voltage limiting circuit, a filter circuit, a voltage sampling circuit and an inverter circuit, wherein the rectifying circuit, the pumping voltage limiting circuit and the filter circuit are sequentially connected, the output end of the filter circuit is respectively connected with the input end of the inverter circuit and the W of the motor, the output end of the inverter circuit is connected with U, V two phases of the motor,
the output end of the single chip microcomputer is connected with the input end of the driving circuit and used for controlling the driving circuit, the driving circuit is respectively connected with the input end of the pumping voltage limiting circuit and the input end of the inverter circuit, the output end of the voltage sampling circuit is connected with the single chip microcomputer, and the input end of the voltage sampling circuit is connected with the output end of the rectifying circuit.
The voltage sampling circuit comprises a resistor R2, a resistor R3 and a VSM025 isolation type Hall voltage sensor, the input end of the VSM025 isolation type Hall voltage sensor is connected with the two ends of a resistor R3, the output end of the VSM025 isolation type Hall voltage sensor is connected with a single chip microcomputer, the voltage waveform of a rectified direct current bus is shown in figure 2, the voltage sampling circuit is used for collecting the voltage of the rectified direct current bus and sending data to the single chip microcomputer, and when the voltage exceeds a limit value, the single chip microcomputer controls a driving circuit to send a PWM signal to control an IGBT1, so that the limitation of pumping voltage is realized.
The pumping voltage limiting circuit comprises an IGBT1, a resistor R1 and a diode D1, wherein a collector of the IGBT1 is connected with a cathode of the diode D1, a gate of the IGBT1 is connected with an output end of the driving circuit, and an emitter of the IGBT1 is respectively connected with an anode of the diode D1 and the resistor R1.
The filter circuit comprises a capacitor C1 and a capacitor C2, the capacitors C1 and C2 are connected in series, the capacitor C1 and the capacitor C2 filter the voltage output by the rectifier circuit, the midpoint E of the capacitor C1 and the capacitor C2 is connected with the W of the motor to form a practical two-phase integral power supply and load, and the two-phase voltages output by the inverter circuit U, V are different in phase by 60 degrees.
The inverter circuit comprises a U-phase inverter circuit and a V-phase inverter circuit,
the U-phase inverter circuit comprises a thyristor VT1, a thyristor VT2, an IGBT2, a diode D2, a diode D3, a diode D4, a diode D5 and a capacitor C3, wherein the gate electrode of the IGBT2 is connected with the output end of the drive circuit,
the cathode of the thyristor VT1 is respectively connected with the collector of the IGBT2 and the anode of the diode D2, the gate of the thyristor VT1 is connected with the output end of the driving circuit, the anode of the thyristor VT1 is connected with the cathode of the diode D2,
the anode of the thyristor VT2 is connected with the emitter of the IGBT2 and the cathode of the diode D5, the gate of the thyristor VT2 is connected with the output end of the driving circuit, the cathode of the thyristor VT2 is connected with the anode of the diode D5,
a capacitor C3 is connected in parallel between the collector and the emitter of the IGBT2, and the U of the motor is connected between diodes D3 and D4;
the V-phase inverter circuit comprises a thyristor VT3, a thyristor VT4, an IGBT3, a diode D6, a diode D7, a diode D8, a diode D9 and a capacitor C4, wherein the gate of the IGBT3 is connected with the output end of the drive circuit,
the cathode of the thyristor VT3 is respectively connected with the collector of the IGBT3 and the anode of the diode D6, the gate of the thyristor VT3 is connected with the output end of the driving circuit, the anode of the thyristor VT3 is connected with the cathode of the diode D6,
the anode of the thyristor VT4 is connected with the emitter of the IGBT3 and the cathode of the diode D9, respectively, the cathode of the thyristor VT4 is connected with the anode of the diode D9, the gate of the thyristor VT4 is connected with the output end of the driving circuit,
a capacitor C4 is connected in parallel between the collector and the emitter of the IGBT3, and the V phase of the motor is connected between diodes D7 and D8.
The turn-off of the thyristors VT1, VT2, VT3 and VT4 is controlled by the switch of the IGBT, the signals of the IGBT1, the IGBT2 and the IGBT3 are controlled by a single chip microcomputer,
the embodiment of the invention also provides a control method of a thyristor and IGBT mixed three-phase motor two-phase frequency conversion control circuit, referring to fig. 3, the voltage of the motor W phase is taken as a reference potential point, the signal of each IGBT is controlled by a single chip microcomputer, an open-loop constant voltage frequency ratio control method with wider application is adopted, sine modulation waves with the phase difference of 60 degrees are used for pulse width modulation, the single chip microcomputer controls a drive circuit to generate 7 paths of PWM waves, the sine modulation waves with the phase difference of 60 degrees are used for pulse width modulation, PWM1 is used for controlling a pump generation voltage limiting circuit by IGBT1, PWM2-PWM7 are used for carrying out inversion of two phases on an IGBT2, a thyristor VT1, a VT2, a thyristor VT4, an IGBT3 and a thyristor VT3, the two-phase inversion circuit U, V is used for outputting two-phase amplitude values and frequency adjustment, and the reference phase W is taken as an alternating voltage with the quasi-phase difference of 60 degrees.
When the voltage measured by the VSM025 isolation type Hall voltage sensor is greater than a set safety voltage, a driving circuit generates PWM1 to perform energy consumption braking to prevent direct-current bus overvoltage, the PWM3 and the PWM4 are complementary pulses and have a certain dead time, and the PWM2 generation method comprises the following steps: PWM2 is the logical operation result of or of PWM3 and PWM4, note that thyristors VT1, VT2 are half-controlled devices, the dead time of PWM3 and PWM4 should be greater than the turn-off time of IGBT2, the sine modulation wave generated by PWM7 should lag the 60 ° electrical angle of the sine modulation wave generated by PWM3, PWM5 and PWM7 are complementary pulses and both must have a certain dead time, the method for generating PWM 6: the PWM6 is the or logical operation result of PWM5 and PWM7, and it is noted that the thyristors VT3, VT4 are half-controlled devices, and the dead time of PWM5 and PWM7 should be greater than the turn-off time of the IGBT 3.
The control process of the inverter circuit V phase is the same as the principle of the U phase, and the U phase is taken as an example for analysis as follows:
in the positive half cycle of the current flowing in the motor U phase, when the thyristors VT1 and the IGBT2 are switched on, the thyristor VT2 is switched off, the current flows into the motor U phase through the thyristor VT1 → the IGBT2 → the diode D4, the voltage at the two ends of the capacitor C3 is approximately zero, when the IGBT2 is switched off, the thyristor VT1 charges the capacitor C3, the current flows to the thyristor VT1 → the capacitor C3 → the diode D4 to flow into the motor U phase, when the voltage of the capacitor C3 rises to the voltage of a direct current bus, the current of the thyristor VT1 drops to zero and is switched off, the diodes D5 and D4 are switched on in follow current, and the current of the U phase flows to the diode D5 → the diode D4 to flow into the motor U phase; in the negative half cycle of the motor U-phase current flowing out, when the IGBT2 and the thyristor VT2 are switched on, the voltage at two ends of the capacitor C3 is approximately zero, the current direction is the motor U phase → the diode D3 → the IGBT2 → the thyristor VT2, when the IGBT2 is switched off, the motor U-phase current is charged to the capacitor C3, the current flows to the motor U phase → the diode D3 → the capacitor C3 → the thyristor VT2, when the voltage of the capacitor C3 rises to the direct-current bus voltage, the current of the thyristor VT2 drops to zero and is switched off, the follow currents of the diodes D3 and D2 are switched on, and the U-phase current flows to the motor U phase → the diode D3 → the diode D2; the control process of the inverter circuit V phase is the same as the principle of the inverter circuit U phase.
The above is only a preferred embodiment of the present invention, and is not intended to limit the present invention, and various modifications and changes will occur to those skilled in the art. Any modification, equivalent replacement, or improvement made within the spirit and principle of the present invention should be included in the protection scope of the present invention.

Claims (8)

1. A thyristor and IGBT mixed three-phase motor two-phase frequency conversion control circuit is characterized by comprising a single chip microcomputer, a driving circuit, a rectifying circuit, a pumping voltage limiting circuit, a filter circuit, a voltage sampling circuit and an inverter circuit, wherein the rectifying circuit, the pumping voltage limiting circuit and the filter circuit are sequentially connected, the output end of the filter circuit is respectively connected with the input end of the inverter circuit and the W of a motor, the output end of the inverter circuit is connected with U, V two phases of the motor,
the output end of the single chip microcomputer is connected with the input end of the driving circuit and used for controlling the driving circuit, the driving circuit is respectively connected with the input end of the pumping voltage limiting circuit and the input end of the inverter circuit, the output end of the voltage sampling circuit is connected with the single chip microcomputer, and the input end of the voltage sampling circuit is connected with the output end of the rectifying circuit.
2. The thyristor and IGBT mixed three-phase motor two-phase frequency conversion control circuit according to claim 1, wherein the voltage sampling circuit comprises a resistor R2, a resistor R3 and a VSM025 isolation type Hall voltage sensor, the input end of the VSM025 isolation type Hall voltage sensor is connected with two ends of a resistor R3, and the output end of the VSM025 isolation type Hall voltage sensor is connected with the single chip microcomputer.
3. The two-phase inverter control circuit of a thyristor and IGBT hybrid three-phase motor according to claim 1, wherein the pump-up voltage limiting circuit comprises an IGBT1, a resistor R1 and a diode D1, wherein a collector of the IGBT1 is connected with a cathode of the diode D1, a gate of the IGBT1 is connected with an output end of the driving circuit, and an emitter of the IGBT1 is respectively connected with an anode of the diode D1 and the resistor R1.
4. The thyristor and IGBT combined three-phase motor two-phase frequency conversion control circuit of claim 1, wherein the filter circuit comprises a capacitor C1 and a capacitor C2, the capacitors C1 and C2 are connected in series, a midpoint E of the capacitors C1 and C2 is connected with W of a motor, and two-phase output voltages of the inverter circuit U, V are different from each other in phase by 60 °.
5. The thyristor and IGBT hybrid three-phase motor two-phase frequency conversion control circuit according to claim 3, wherein the inverter circuit comprises a U-phase inverter circuit and a V-phase inverter circuit,
the U-phase inverter circuit comprises a thyristor VT1, a thyristor VT2, an IGBT2, a diode D2, a diode D3, a diode D4, a diode D5 and a capacitor C3, wherein the gate electrode of the IGBT2 is connected with the output end of the drive circuit,
the cathode of the thyristor VT1 is respectively connected with the collector of the IGBT2 and the anode of the diode D2, the gate of the thyristor VT1 is connected with the output end of the driving circuit, the anode of the thyristor VT1 is connected with the cathode of the diode D2,
the anode of the thyristor VT2 is connected with the emitter of the IGBT2 and the cathode of the diode D5, the gate of the thyristor VT2 is connected with the output end of the driving circuit, the cathode of the thyristor VT2 is connected with the anode of the diode D5,
a capacitor C3 is connected in parallel between the collector and the emitter of the IGBT2, the U of the motor is connected between diodes D3 and D4,
the V-phase inverter circuit comprises a thyristor VT3, a thyristor VT4, an IGBT3, a diode D6, a diode D7, a diode D8, a diode D9 and a capacitor C4, wherein the gate of the IGBT3 is connected with the output end of the drive circuit,
the cathode of the thyristor VT3 is respectively connected with the collector of the IGBT3 and the anode of the diode D6, the gate of the thyristor VT3 is connected with the output end of the driving circuit, the anode of the thyristor VT3 is connected with the cathode of the diode D6,
the anode of the thyristor VT4 is connected with the emitter of the IGBT3 and the cathode of the diode D9, the gate of the thyristor VT4 is connected with the output end of the driving circuit, the cathode of the thyristor VT4 is connected with the anode of the diode D9,
a capacitor C4 is connected in parallel between the collector and the emitter of the IGBT3, and the V phase of the motor is connected between diodes D7 and D8.
6. A control method of a thyristor and IGBT mixed three-phase motor two-phase frequency conversion control circuit according to claim 5, characterized in that the method comprises: the voltage of the W phase of the motor is used as a reference potential point, an open-loop constant-voltage frequency ratio control method is adopted, sine modulation waves with the phase difference of 60 degrees are used for pulse width modulation, the single chip microcomputer controls the driving circuit to generate 7 paths of PWM waves, PWM1 is used for acting on the IGBT1 to control the pump generation voltage limiting circuit, PWM2-PWM7 is used for acting on the IGBT2, the thyristor VT1, the thyristor VT2, the thyristor VT4, the IGBT3 and the thyristor VT3 to carry out two-phase inversion of the inverter circuit U, V, the amplitude and the frequency of two phases are adjustable, and the reference phase W is used as an alternating voltage with the quasi-phase difference of 60 degrees.
7. The method as claimed in claim 6, further comprising the step of generating PWM1 for dynamic braking to prevent dc bus overvoltage when the voltage measured by the VSM025 isolated hall voltage sensor is greater than the set safety voltage, wherein PWM3 and PWM4 are complementary pulses and their respective dead time is greater than the off time of IGBT2, PWM3 and PWM4 are or-logic operated to generate PWM2, the sinusoidal modulation wave generated PWM7 lags behind the sinusoidal modulation wave generated PWM3 by 60 ° electrical angle, PWM5 and PWM7 are complementary pulses and their respective dead time is greater than the off time of IGBT3, and PWM5 and PWM7 are or-logic operated to generate PWM 6.
8. The method for controlling the two-phase variable frequency control circuit of the three-phase motor with the thyristor and the IGBT mixed according to claim 7, characterized in that the method further comprises the following control process of the U phase of the inverter circuit: in the positive half cycle of the current flowing in the motor U phase, when the thyristors VT1 and the IGBT2 are switched on, the thyristor VT2 is switched off, the current flows into the motor U phase through the thyristor VT1 → the IGBT2 → the diode D4, the voltage at the two ends of the capacitor C3 is approximately zero, when the IGBT2 is switched off, the thyristor VT1 charges the capacitor C3, the current flows to the thyristor VT1 → the capacitor C3 → the diode D4 to flow into the motor U phase, when the voltage of the capacitor C3 rises to the voltage of a direct current bus, the current of the thyristor VT1 drops to zero and is switched off, the diodes D5 and D4 are switched on in follow current, and the current of the U phase flows to the diode D5 → the diode D4 to flow into the motor U phase; in the negative half cycle of the motor U-phase current flowing out, when the IGBT2 and the thyristor VT2 are switched on, the voltage at two ends of the capacitor C3 is approximately zero, the current direction is the motor U phase → the diode D3 → the IGBT2 → the thyristor VT2, when the IGBT2 is switched off, the motor U-phase current is charged to the capacitor C3, the current flows to the motor U phase → the diode D3 → the capacitor C3 → the thyristor VT2, when the voltage of the capacitor C3 rises to the direct-current bus voltage, the current of the thyristor VT2 drops to zero and is switched off, the follow currents of the diodes D3 and D2 are switched on, and the U-phase current flows to the motor U phase → the diode D3 → the diode D2; the control process of the inverter circuit V phase is the same as the principle of the inverter circuit U phase.
CN202111293021.3A 2021-11-03 2021-11-03 Thyristor and IGBT mixed three-phase motor two-phase frequency conversion control circuit and method thereof Pending CN113965139A (en)

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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20220247339A1 (en) * 2018-11-30 2022-08-04 Lenze Se Method for Monitoring the Operation of a Frequency Converter, and Frequency Converter

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20220247339A1 (en) * 2018-11-30 2022-08-04 Lenze Se Method for Monitoring the Operation of a Frequency Converter, and Frequency Converter

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