CN113791392A - Deception method for omnidirectional amplitude comparison monopulse direction finding system based on frequency control array - Google Patents

Deception method for omnidirectional amplitude comparison monopulse direction finding system based on frequency control array Download PDF

Info

Publication number
CN113791392A
CN113791392A CN202110905518.XA CN202110905518A CN113791392A CN 113791392 A CN113791392 A CN 113791392A CN 202110905518 A CN202110905518 A CN 202110905518A CN 113791392 A CN113791392 A CN 113791392A
Authority
CN
China
Prior art keywords
array
antenna
finding system
frequency control
deception
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
CN202110905518.XA
Other languages
Chinese (zh)
Other versions
CN113791392B (en
Inventor
陈楚舒
盛川
谢军伟
邵雷
张浩为
王博
李正杰
葛佳昂
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Air Force Engineering University of PLA
Original Assignee
Air Force Engineering University of PLA
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Air Force Engineering University of PLA filed Critical Air Force Engineering University of PLA
Priority to CN202110905518.XA priority Critical patent/CN113791392B/en
Publication of CN113791392A publication Critical patent/CN113791392A/en
Application granted granted Critical
Publication of CN113791392B publication Critical patent/CN113791392B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Classifications

    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/38—Jamming means, e.g. producing false echoes

Landscapes

  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Remote Sensing (AREA)
  • Radar Systems Or Details Thereof (AREA)

Abstract

The invention discloses a method for positioning and cheating an omnidirectional amplitude-comparison monopulse direction-finding system based on a frequency control array, which is different from a phased array in controlling the beam direction through the phase difference between array elements. The energy domain is that the main lobe energy of the space beam is bent due to the interference effect of the field intensity to form a virtual radiation source, so that angle deception is formed on the nABD direction of the reconnaissance receiver. Experiments show that the deception method can improve the detection precision of the radar of the party and enhance the deception effect on the interference machine of the enemy.

Description

Deception method for omnidirectional amplitude comparison monopulse direction finding system based on frequency control array
Technical Field
The invention relates to the field of electronic countermeasure, in particular to a deception method for an omnidirectional amplitude comparison monopulse direction finding system based on a frequency control array.
Background
Electronic countermeasure is a special combat means in modern war, and mainly comprises the basic contents of electronic countermeasure reconnaissance, electronic attack, electronic defense and the like. The direction finding in electronic pair scout is essentially determining or estimating the direction of arrival (DOA) or angle of arrival (AOA) of an incoming wave from a radiation source in space, and is therefore also called passive or passive goniometry. In electronic countermeasure, the jammer of our party releases interference to the target radar of the enemy party, and meanwhile, the radiation signal of the jammer of our party is captured by the passive detection radar of the enemy party so as to accurately position the jammer of our party, which seriously threatens the safety of the jammer of our party. Therefore, a new system radar needs to be developed to shield an interference machine by reducing interception probability, and the traditional phased array radar changes the phase between adjacent array elements through a shifter to realize the scanning of a wave beam in space.
The Frequency Diversity Array (FDA) can synthesize a beam with time-distance-angle three-dimensional correlation by introducing a tiny frequency offset between array elements, so that after a radiation signal of an interference machine based on the FDA reaches a signal receiver of a target radar direction-finding system, a 'virtual radiation source' can be formed due to the time-distance-angle correlation characteristic of the FDA emitted beam, and positioning of an enemy radar is misled, thereby ensuring that the interference machine of our party effectively carries out a shield task.
Disclosure of Invention
Aiming at the existing problems, the invention aims to provide a deception method of a full-antenna amplitude comparison direction-finding system based on a frequency control array, and the deception effect of an enemy jammer is enhanced while the detection precision of the radar of the own party is improved by using the method.
In order to achieve the purpose, the technical scheme adopted by the invention is as follows:
a deception method for an all-antenna amplitude comparison direction-finding system based on a frequency control array is characterized by comprising the following steps:
step 1: constructing a frequency control array radar system;
step 2: establishing a deception model of the frequency control array radar system to a full-antenna amplitude comparison direction-finding system;
and step 3: obtaining a distance expression between the frequency control array elements and the array elements of the direction-finding system array antenna and an expression of signals received by the direction-finding system;
and 4, step 4: and obtaining a DOA estimation angle of the direction-finding system based on a deception model of the full-antenna amplitude-comparison direction-finding system, calculating an angle deviation and a position deviation of the direction-finding system for positioning the radiation source, and evaluating a positioning deception effect according to the obtained angle deviation and position deviation.
Further, the specific steps of step 1 are:
suppose a uniform linear array frequency-controlled array radar composed of N array elements, as shown in fig. 1, where the number of the frequency-controlled array elements is N, c is the speed of light, the frequency increment between two adjacent array elements is Δ f, and the initial carrier frequency f0The frequency of the n-th array element is fn＝f0+ delta f, array element spacing d, and distance between the target and the frequency control array R; the pointing angle from the array signal to the far field is theta, and the radiation signals of array elements n in the frequency control array radiation source are assumed as follows:
sn(t)＝exp(j2πfnt),n＝0,1,...,N-1 (1)，
the signal emitted by the nth array element at a far-field observation point (R, θ) is represented as:
Figure BDA0003198875230000021
the resultant field strength at the far field observation point (R, θ) is:
Figure BDA0003198875230000031
let γ be Δ ft + (f)0dsin θ)/c- Δ fR/c due to f0> N.DELTA.f, then:
Figure BDA0003198875230000032
taking the array factor as:
Figure BDA0003198875230000033
taking a phase direction diagram as follows:
Figure BDA0003198875230000034
further, the specific steps of step 2 are:
step 21: an antenna directional pattern function F (theta) of the four-antenna omnidirectional amplitude monopulse direction-finding system is expanded into a Fourier series, namely:
Figure BDA0003198875230000035
Figure BDA0003198875230000036
Figure BDA0003198875230000037
wherein N is the number of antennas of the receiving system, Fi(theta) is the directional diagram function of the ith antenna, akFor Fourier series coefficients, k is 0 and all positive integers, θsThe included angle between adjacent antennas is 2 pi/N;
step 22: using the weight cos (i θ)s),sin(iθs) The weighted sum of the output signals of each antenna is equivalent to the sum of the projections of the incoming wave signals received by each antenna to two orthogonal directions,then there are:
Figure BDA0003198875230000038
Figure BDA0003198875230000039
the expansion is as follows:
Figure BDA0003198875230000041
Figure BDA0003198875230000042
wherein L represents an antenna of the same pattern F (θ);
when the antenna mapping function is fourier expanded, the coefficients of the higher order terms decrease very fast with increasing order, so when the number of antennas is large, an approximation is taken:
Figure BDA0003198875230000043
Figure BDA0003198875230000044
step 23: and calculating the incoming wave azimuth angle based on the obtained C (theta) and S (theta), wherein the calculation formula is as follows:
Figure BDA0003198875230000045
step 24: and establishing a positioning deception model based on the incoming wave azimuth angle obtained in the step 23, wherein a receiving antenna of a full-antenna amplitude-comparison direction-finding system in the positioning deception model is an array antenna comprising M array elements, and the distance between adjacent array elements in the array antenna of the omnidirectional amplitude-comparison single-pulse direction-finding system is d 1.
Further, the specific steps of step 3 are:
step 31: according to the geometric position relation, calculating the distance R' between a frequency control array element n and an array antenna element m of the omnidirectional amplitude comparison monopulse direction-finding system, and calculating a formula:
R'＝R-(n-1)dsinθ+(m-1)d1sin(θ-iθs) (12)；
step 32: the expression of the signal received by the direction finding system is:
assuming that the gain of each transmitting array element radiation signal and the gain of each receiving array element signal are both equal to 1, the signal received by the antenna i is:
Figure BDA0003198875230000046
Figure BDA0003198875230000051
further, the specific steps of step 4 are:
step 41: when Δ fnWhen the frequency control array is degraded to a phased array at 0, the signal received by the antenna i is changed from equation (13):
Figure BDA0003198875230000052
the phase direction diagram is:
φ1＝2πf0(t-[R-(N-1)dsinθ/2+(M-1)d1sin(θ-iθs)/2]/c) (16)；
step 42: assuming that each receive channel performs sub-envelope sampling after threshold detection, equation (11) can be expressed as:
Figure BDA0003198875230000053
wherein，
Figure BDA0003198875230000054
Step 43: processing signals in the full-antenna amplitude-comparison direction-finding system according to a phased array system, wherein the form of the received signals is as shown in the formula (15), the actually received signals are frequency control array signals, and angle estimation values are obtained in MATLAB by using a solve function
Figure BDA0003198875230000055
Figure BDA0003198875230000056
Step 44: calculating the angle deviation and the position deviation of the full-antenna amplitude-comparison direction-finding system for positioning the radiation source, wherein the calculation formula is as follows:
angular deviation:
Figure BDA0003198875230000061
position deviation:
Figure BDA0003198875230000062
the invention has the beneficial effects that:
according to the method, on the basis of the deception principle of the FDA on the direction finding system, a deception model of the FDA on the full antenna amplitude comparison (nABD) direction finding system is established, and finally, the DOA positioning deception effect of the FDA on the nABD direction finding under a non-noise environment and a Gaussian white noise environment is verified through simulation analysis, and the experiment effect shows that the deception model has a good deception effect.
Drawings
Fig. 1 is a schematic diagram of a basic FDA array structure;
FIG. 2 is a four-antenna omnidirectional amplitude monopulse direction-finding schematic;
FIG. 3 is a position relationship between an nABD direction finding system and a frequency control array radar jammer;
fig. 4 is a comparison of the emission patterns of four FDA arrays;
FIG. 5 illustrates the impact of frequency offset increments on the positioning spoofing effect of different arrays;
FIG. 6 is a graph of the effects of time on location spoofing for different arrays;
FIG. 7 is a graph of the effect of signal-to-noise ratio on positioning estimation;
FIG. 8 is a graph of the effect of time on location estimation RMSE under noisy conditions;
FIG. 9 is a graph of the effect of a frequency offset increment on a location estimate RMSE under noisy conditions.
Detailed Description
In order to make those skilled in the art better understand the technical solution of the present invention, the following further describes the technical solution of the present invention with reference to the drawings and the embodiments.
To further illustrate the spoofing method proposed by the present invention, a brief description of the FDA and nABD direction finding system principles will be given first.
1. FDA signal model
As shown in the FDA array structure of FIG. 1, the number of array elements is N, and the carrier frequency is f0And then the frequency of the radiation signal of the nth array element is:
fn＝f0+Δfn＝f0+xnΔf,n＝0,1,2,...,N-1 (1)，
wherein x isnRepresenting the coding coefficient, and delta f is the increment of frequency deviation between adjacent array elements, delta fnIndicating the increment of frequency offset between the nth array element and the initial array element.
As can be seen from equation (1), if the coding coefficient x is changednObtaining FDA arrays with different frequency control functions when x isnWhen n, is a uniform linear fda (ulfda), when xnSin (n), sin-FDA, when x isnLog (n +1) is log FDA (log-FDA).
Assuming that the distance between two adjacent array elements is d, the pointing angle from the array signal to the far field is theta, the light velocity is c, and assuming that the radiation signals of the array elements n in the frequency control array radiation source are:
sn(t)＝exp(j2πfnt),n＝0,1,...,N-1 (2)，
at a far-field observation point (R, θ):
Figure BDA0003198875230000071
wherein R is the distance from the reference array element to the target point, RnThe combined field strength at a far-field observation point (R, θ) is:
Figure BDA0003198875230000072
the following analyses were performed using the example of ULFDA:
the resultant field strength at the far field point (R, θ) is:
Figure BDA0003198875230000081
let γ be Δ ft + (f)0dsin θ)/c- Δ fR/c due to f0> N.DELTA.f, the above formula can be simplified as:
Figure BDA0003198875230000082
and taking the array factor as:
Figure BDA0003198875230000083
taking a phase direction diagram as follows:
Figure BDA0003198875230000084
2. nABD direction finding system principle
Amplitude of omnidirectionalThe schematic diagram of the monopulse direction finding system is shown in fig. 2, and the monopulse direction finding system comprises L antennas with the same directional diagram F (theta), which are uniformly distributed in a range of 360 degrees to form a circular array, and the field angles of the adjacent antennas are as follows: thetasThe system performs doa (direction of arrival) estimation based on amplitude information of signals received by each antenna:
the azimuth direction of each antenna is as follows:
Fi(θ)＝F(θ-iθs),i＝0,1,2…L-1 (9)，
suppose that the amplitude gain of each channel is kiThen, the logarithmic output of the signal received by each antenna through the receiving channel is:
si(t,θ)＝10lg[kiF(θ-iθs)A(t)](dB),i＝0,1,…L-1 (10)，
a (t) in the formula (10) is a function of the amplitude of the radiation signal;
the nABD direction-finding system utilizes the amplitude information of the signals received by the n antennas to carry out unified processing, thereby carrying out DOA estimation. The antenna pattern function F (θ) can be expanded as a fourier series, i.e.:
Figure BDA0003198875230000091
therein
Figure BDA0003198875230000092
Figure BDA0003198875230000093
Using the weight cos (i θ)s),sin(iθs) The weighted sum of the output signals of each antenna is equivalent to the sum of the projections of the incoming wave signals received by each antenna to two orthogonal directions, and then:
Figure BDA0003198875230000094
Figure BDA0003198875230000095
the respective formulas (12-1) and (12-2) are developed to obtain:
Figure BDA0003198875230000096
Figure BDA0003198875230000097
in general, when the antenna pattern function is subjected to fourier expansion, the coefficients of higher-order terms decrease rapidly with increasing order, so when the number of antennas is large, the approximation is obtained:
Figure BDA0003198875230000098
Figure BDA0003198875230000099
obtaining the azimuth angle of the incoming wave as follows:
Figure BDA00031988752300000910
in engineering practice, a signal in one pulse envelope is sampled and then statistical averaging is carried out, so that the effect of a virtual antenna can be achieved. By performing the direction finding processing in this way, the direction estimation accuracy can be improved. Assuming that each receive channel performs m envelope samples after threshold detection, equation (15) can be expressed as:
Figure BDA0003198875230000101
wherein,
Figure BDA0003198875230000102
generally, in the nABD direction finding system, n antennas with the same antenna pattern function are uniformly arranged on a circle, omnidirectional direction finding is performed, all received signals are projected to two orthogonal directions, summation is performed, and arctangent of a ratio is obtained, so that DOA estimation can be performed. Compared with the traditional amplitude comparison method which is difficult to have an ideal antenna directional diagram function and easy to influence the direction finding precision, the nABD direction comparison method directly processes the amplitude information of signals received by n antennas in one circle, constructs a virtual ideal antenna and greatly improves the direction finding precision. The transmitting directional diagram of the frequency control array has distance dependency, the beam direction changes along with the change of the distance, and the beam direction shows bending characteristics on an energy domain, and the nABD direction-finding system carries out positioning cheating on the nABD direction-finding system due to the fact that the DOA estimation is carried out according to the amplitude of a received signal, and therefore the virtual radiation source characteristics of the frequency control array can carry out positioning cheating on the nABD direction-finding system.
3. FDA-based fraud model
The receiving antenna of the omnidirectional amplitude-comparison monopulse direction-finding system is assumed to be an array antenna comprising M array elements. The positional relationship between the nABD direction-finding system and the frequency control array in the space is shown in figure 3. Assuming that the distance between adjacent array elements in the array antenna of the nABD direction-finding system is d1, and the distance between a frequency control array element n and a receiving antenna array element m is R':
R'＝R-(n-1)dsinθ+(m-1)d1sin(θ-iθs) (17)，
assuming that the gain of each transmitting array element radiation signal and receiving array element signal is equal to 1, the signal received by the antenna i is:
Figure BDA0003198875230000111
Figure BDA0003198875230000112
when Δ fnWhen 0, the frequency control array is degraded to a phased array:
Figure BDA0003198875230000113
φ1＝2πf0(t-[R-(N-1)dsinθ/2+(M-1)d1sin(θ-iθs)/2]/c) (21)，
Figure BDA0003198875230000114
the angular deviation of the orientation system from the positioning of the radiation source is then:
Figure BDA0003198875230000115
Figure BDA0003198875230000116
examples
In order to verify the feasibility and the effect of the deception model provided by the invention, the following simulation experiment is carried out.
Positioning errors are generally used as a measure of positioning accuracy, and in the present invention, a larger positioning error indicates a better spoofing effect. In order to verify the deception effect of the model, the invention analyzes the angular deviation, the distance deviation and the Root Mean Square Error (RMSE) of the DOA positioning of the nABD direction-finding system based on the radiation signals of ULFDA, log-FDA, sin-FDA and FDA.
1. Simulation experiment
(1) Four array emission pattern comparisons
Let the coordinates of the far-field object be (60km,30 °), Δ f 6kHz, d 0.15m, f0The number of array elements is 30 at 1GHz, and the signal-to-noise ratio and the drying ratio are both 10. FIG. 4 shows PA array, ULFDA array, log-FDA arrayColumn, emission pattern of sin-FDA array; from fig. 4, it can be verified that the FDA proposed in the present invention can perform positioning spoofing on an nABD direction finding system that performs DOA estimation using the amplitude response of a radiation signal, compared to the beam bending characteristics of PA in the energy domain. Fig. 4(c) - (d) enable the formation of energy-concentrated "spot-like" beams, eliminating the ULFDA distance-angle coupling;
(2) location spoofing with different FDA arrays under noiseless conditions
Taking the total number N of array elements of FDA as 10, d as 0.15m, and carrier frequency f01GHz, the number L of receiving antennas of the nABD direction finding system is 72, and the included angle between adjacent antennas is thetasThe receiving array element number of each array antenna is M10, and the distance between adjacent array elements is d1 0.15M. The FDA jammer is 50km away from the direction-finding system, and the true incident angle of a radiation signal is 50 degrees. Due to the introduction of the tiny frequency offset increment, a distance-time dependent beam generated by the frequency control array has a positioning spoofing effect on a direction finding system, so that the influence of two parameters, namely the frequency offset increment and the time, on the spoofing effect is mainly simulated in the simulation experiment, fig. 5(a) - (d) show the influence of different frequency offset increments on the positioning spoofing effect when t is 40 μ s, and fig. 6(a) - (d) show the influence of different starting times at Δ f being 1kHz on the positioning spoofing effect. As can be seen from the attached figures 5 and 6, the signals radiated by the traditional phased array radar have no deception effect and are easy to be intercepted by a direction-finding system. The signals radiated by the FDA array have a deceptive effect on the direction-finding system, wherein the deceptive effect of the ULFDA array is better than that of the other two non-linear frequency control functions. And the optimal deception effect can be achieved at a specific frequency offset and a specific time.
(3) Location spoofing with different FDA arrays in the case of white Gaussian noise
The basic parameters of the FDA transmit array element and the nABD direction finding system in the experiment are the same as those in the simulation experiment described above. In an actual electromagnetic environment, internal and external noise is ubiquitous, and the noise is assumed to be white gaussian noise in the example. The root mean square error can effectively measure the statistical mean value of the deviation between the estimator and the true value, and the root mean square error is used for describing DOA estimation and positioning errors in the experiment and measuring the quality of positioning deception effect. To ensure randomness of the results, the RMSE of the angle estimation error and the distance estimation error was calculated using 1000 monte carlo experiments. Fig. 7(a) shows the effect of the signal-to-noise ratio on the root mean square error of the angle estimation, and fig. 7(b) shows the effect of the signal-to-noise ratio on the root mean square error of the position estimation. Fig. 8(a) shows the effect of time on the root mean square error of the angle estimation under noisy conditions, and fig. 8(b) shows the effect of time on the root mean square error of the position estimation under noisy conditions. Fig. 9(a) shows the influence of the frequency offset increment on the root mean square error of the angle estimation under the noise condition, and fig. 9(b) shows the influence of the frequency offset increment on the root mean square error of the position estimation under the noise condition. From simulation results, in a noise environment, the frequency control array still has a deception effect on the nABD direction finding system, and the positioning estimation deviation is influenced by the signal-to-noise ratio, the frequency offset increment and the starting time. As can be seen from fig. 8 and 9, among the four arrays, the ul fda spoofing effect is the best, and the spoofing effect is the better when the signal-to-noise ratio is small, while in most practical scenarios, the signal-to-noise ratio of the signal received by the direction-finding system is low, so the frequency control array can exert good spoofing effect.
The foregoing has described the general principles, principal features, and advantages of the invention. It will be understood by those skilled in the art that the present invention is not limited to the embodiments described above, which are described in the specification and illustrated only to illustrate the principle of the present invention, but that various changes and modifications may be made therein without departing from the spirit and scope of the present invention, which fall within the scope of the invention as claimed. The scope of the invention is defined by the appended claims and equivalents thereof.

Claims (5)

1. A deception method for an all-antenna amplitude comparison direction-finding system based on a frequency control array is characterized by comprising the following steps:
step 1: constructing a frequency control array radar system;
step 2: establishing a deception model of the frequency control array radar system to a full-antenna amplitude comparison direction-finding system;
and step 3: obtaining a distance expression between the frequency control array elements and the array elements of the direction-finding system array antenna and an expression of signals received by the direction-finding system;
and 4, step 4: and obtaining a DOA estimation angle of the direction-finding system based on a deception model of the full-antenna amplitude-comparison direction-finding system, calculating an angle deviation and a position deviation of the direction-finding system for positioning the radiation source, and evaluating a positioning deception effect according to the obtained angle deviation and position deviation.
2. The deception method of the full-antenna amplitude comparison direction-finding system based on the frequency control array according to claim 1, wherein the specific steps of the step 1 are as follows:
suppose a uniform linear array frequency-controlled array radar composed of N array elements, as shown in fig. 1, where the number of the frequency-controlled array elements is N, c is the speed of light, the frequency increment between two adjacent array elements is Δ f, and the initial carrier frequency f0The frequency of the n-th array element is fn＝f0+ delta f, array element spacing d, and distance between the target and the frequency control array R; the pointing angle from the array signal to the far field is theta, and the radiation signals of array elements n in the frequency control array radiation source are assumed as follows:
sn(t)＝exp(j2πfnt),n＝0,1,...,N-1 (1)，
the signal emitted by the nth array element at a far-field observation point (R, θ) is represented as:
Figure FDA0003198875220000011
the resultant field strength at the far field observation point (R, θ) is:
Figure FDA0003198875220000021
let γ be Δ ft + (f)0dsin θ)/c- Δ fR/c due to f0> N.DELTA.f, then:
Figure FDA0003198875220000022
taking the array factor as:
Figure FDA0003198875220000023
taking a phase direction diagram as follows:
Figure FDA0003198875220000024
3. the deception method of the full-antenna amplitude comparison direction-finding system based on the frequency control array as claimed in claim 1, wherein the specific steps of the step 2 are as follows:
step 21: an antenna directional pattern function F (theta) of the four-antenna omnidirectional amplitude monopulse direction-finding system is expanded into a Fourier series, namely:
Figure FDA0003198875220000025
Figure FDA0003198875220000026
Figure FDA0003198875220000027
wherein N is the number of antennas of the receiving system, Fi(theta) is the directional diagram function of the ith antenna, akFor Fourier series coefficients, k is 0 and all positive integers, θsThe included angle between adjacent antennas is 2 pi/N;
step 22: using the weight cos (i θ)s),sin(iθs) The weighted sum of the output signals of each antenna is equivalent to the sum of the projections of the incoming wave signals received by each antenna to two orthogonal directions, and then:
Figure FDA0003198875220000031
Figure FDA0003198875220000032
the expansion is as follows:
Figure FDA0003198875220000033
Figure FDA0003198875220000034
wherein L represents an antenna of the same pattern F (θ);
when the antenna mapping function is fourier expanded, the coefficients of the higher order terms decrease very fast with increasing order, so when the number of antennas is large, an approximation is taken:
Figure FDA0003198875220000035
Figure FDA0003198875220000036
step 23: and calculating the incoming wave azimuth angle based on the obtained C (theta) and S (theta), wherein the calculation formula is as follows:
Figure FDA0003198875220000037
step 24: and establishing a positioning deception model based on the incoming wave azimuth angle obtained in the step 23, wherein a receiving antenna of a full-antenna amplitude-comparison direction-finding system in the positioning deception model is an array antenna comprising M array elements, and the distance between adjacent array elements in the array antenna of the omnidirectional amplitude-comparison single-pulse direction-finding system is d 1.
4. The deception method of the full-antenna amplitude comparison direction-finding system based on the frequency control array as claimed in claim 1, wherein the specific steps of the step 3 are as follows:
step 31: according to the geometric position relation, calculating the distance R' between a frequency control array element n and an array antenna element m of the omnidirectional amplitude comparison monopulse direction-finding system, and calculating a formula:
R'＝R-(n-1)d sinθ+(m-1)d1sin(θ-iθs) (12)；
step 32: the expression of the signal received by the direction finding system is:
assuming that the gain of each transmitting array element radiation signal and the gain of each receiving array element signal are both equal to 1, the signal received by the antenna i is:
Figure FDA0003198875220000041
Figure FDA0003198875220000042
5. the deception method of the full-antenna amplitude comparison direction-finding system based on the frequency control array as claimed in claim 1, wherein the specific steps of the step 4 are as follows:
step 41: when Δ fnWhen the frequency control array is degraded to a phased array at 0, the signal received by the antenna i is changed from equation (13):
Figure FDA0003198875220000043
the phase direction diagram is:
φ1＝2πf0(t-[R-(N-1)d sinθ/2+(M-1)d1sin(θ-iθs)/2]/c)
(16)；
step 42: assuming that each receive channel performs sub-envelope sampling after threshold detection, equation (11) can be expressed as:
Figure FDA0003198875220000051
wherein,
Figure FDA0003198875220000052
step 43: processing signals in the full-antenna amplitude-comparison direction-finding system according to a phased array system, wherein the form of the received signals is as shown in the formula (15), the actually received signals are frequency control array signals, and angle estimation values are obtained in MATLAB by using a solve function
Figure FDA0003198875220000053
Figure FDA0003198875220000054
Step 44: calculating the angle deviation and the position deviation of the full-antenna amplitude-comparison direction-finding system for positioning the radiation source, wherein the calculation formula is as follows:
angular deviation:
Figure FDA0003198875220000055
position deviation:
Figure FDA0003198875220000056
CN202110905518.XA 2021-08-05 2021-08-05 Spoofing method based on frequency control array to omnidirectional amplitude comparison single pulse direction finding system Active CN113791392B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN202110905518.XA CN113791392B (en) 2021-08-05 2021-08-05 Spoofing method based on frequency control array to omnidirectional amplitude comparison single pulse direction finding system

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN202110905518.XA CN113791392B (en) 2021-08-05 2021-08-05 Spoofing method based on frequency control array to omnidirectional amplitude comparison single pulse direction finding system

Publications (2)

Publication Number Publication Date
CN113791392A true CN113791392A (en) 2021-12-14
CN113791392B CN113791392B (en) 2023-11-07

Family

ID=79181523

Family Applications (1)

Application Number Title Priority Date Filing Date
CN202110905518.XA Active CN113791392B (en) 2021-08-05 2021-08-05 Spoofing method based on frequency control array to omnidirectional amplitude comparison single pulse direction finding system

Country Status (1)

Country Link
CN (1) CN113791392B (en)

Citations (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20040267127A1 (en) * 1999-05-28 2004-12-30 Vuesonix Sensors, Inc. Transmitter patterns for multi beam reception
US20110309981A1 (en) * 2008-10-30 2011-12-22 Nederlandse Organisatie Voor Toegepast- Natuurwetenschappelijk Onderzoek Tno Combined direction finder and radar system, method and computer program product
CN107037410A (en) * 2017-04-17 2017-08-11 电子科技大学 A kind of method disturbed radar, device and frequency control battle array jammer
CN109324309A (en) * 2018-09-10 2019-02-12 中国航天科工集团八五研究所 A kind of rotation single antenna angle-measuring equipment and its measurement method
CN110109117A (en) * 2019-05-30 2019-08-09 电子科技大学 The satellite-borne synthetic aperture radar Convolution Modulation interference method of battle array is controlled based on frequency
US20190265353A1 (en) * 2018-02-28 2019-08-29 Goverment of the United States, as represented by the Secretary of the Air Force Radio or Sonic Wave Detector, Transmitter, Receiver and Method Thereof
CN110346764A (en) * 2019-08-21 2019-10-18 上海无线电设备研究所 A kind of MIMO radar target range angle decoupling method
EP3690483A1 (en) * 2019-02-04 2020-08-05 Fraunhofer-Gesellschaft zur Förderung der angewandten Forschung e.V. A method for synthesis of antenna array layouts or selection of waveform in a set of mutually incoherent apertures for radar and radio-frequency applications
CN112612019A (en) * 2020-11-30 2021-04-06 中国人民解放军空军工程大学 Active anti-interference method based on frequency control array phase center

Patent Citations (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20040267127A1 (en) * 1999-05-28 2004-12-30 Vuesonix Sensors, Inc. Transmitter patterns for multi beam reception
US20110309981A1 (en) * 2008-10-30 2011-12-22 Nederlandse Organisatie Voor Toegepast- Natuurwetenschappelijk Onderzoek Tno Combined direction finder and radar system, method and computer program product
CN107037410A (en) * 2017-04-17 2017-08-11 电子科技大学 A kind of method disturbed radar, device and frequency control battle array jammer
US20190265353A1 (en) * 2018-02-28 2019-08-29 Goverment of the United States, as represented by the Secretary of the Air Force Radio or Sonic Wave Detector, Transmitter, Receiver and Method Thereof
CN109324309A (en) * 2018-09-10 2019-02-12 中国航天科工集团八五研究所 A kind of rotation single antenna angle-measuring equipment and its measurement method
EP3690483A1 (en) * 2019-02-04 2020-08-05 Fraunhofer-Gesellschaft zur Förderung der angewandten Forschung e.V. A method for synthesis of antenna array layouts or selection of waveform in a set of mutually incoherent apertures for radar and radio-frequency applications
CN110109117A (en) * 2019-05-30 2019-08-09 电子科技大学 The satellite-borne synthetic aperture radar Convolution Modulation interference method of battle array is controlled based on frequency
CN110346764A (en) * 2019-08-21 2019-10-18 上海无线电设备研究所 A kind of MIMO radar target range angle decoupling method
CN112612019A (en) * 2020-11-30 2021-04-06 中国人民解放军空军工程大学 Active anti-interference method based on frequency control array phase center

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
王博;谢军伟;葛佳昂;张晶;: "FDA对比幅法单脉冲测向的角度欺骗", 北京航空航天大学学报, vol. 46, no. 3 *
解志斌;谭冠南;田雨波;陈锦富;王旭;: "一种用于频率可重构超宽带天线的改进的nABD测向算法", 宇航学报, no. 02 *

Also Published As

Publication number Publication date
CN113791392B (en) 2023-11-07

Similar Documents

Publication Publication Date Title
CN109946665B (en) Method for acquiring real target based on array radar
CN106066473B (en) The multi-beam joint angle measurement of MIMO radar target and Contact fusion method under orthogonal waveforms
CN104297734B (en) Deceiving interference suppressing method based on the MIMO radar of frequency diversity array
CN102156279B (en) Method for detecting moving target on ground by utilizing bistatic radar based on MIMO (Multiple Input Multiple Output)
CN103235292B (en) Full-dimension and difference angle measurement method for zero setting conformal calibration of a planar phased array
CN112949100B (en) Main lobe interference resisting method for airborne radar
US6404379B1 (en) Matrix monopulse ratio radar processor for two target azimuth and elevation angle determination
CN111239677B (en) Multi-beam passive monopulse angle measurement method based on digital array
CN112834980B (en) Vortex electromagnetic wave super-resolution direction finding method based on propagation operator
CN109765529B (en) Millimeter wave radar anti-interference method and system based on digital beam forming
CN109283497B (en) Bistatic FDA-MIMO radar range deception jamming identification method
CN112068119B (en) Identification method of passive radar seeker for radar and decoy interference
EP1423725A2 (en) Digital beamforming for passive detection of target using reflected jamming echoes
CN105974390B (en) Ji Sao metre wave radars mass centre angle-measuring method based on doppler information
CN113314832A (en) Millimeter wave vehicle-mounted MIMO radar antenna array device and design method
CN107907860A (en) A kind of Location fraud method that the anti-time difference measurement of battle array technology is controlled using frequency
CN109884337B (en) Method for detecting sea surface wind direction by using high-frequency ground wave radar
Liu et al. Discrimination of mainlobe deceptive target with meter-wave FDA-MIMO radar
CN114935738A (en) Radar sum and difference angle measurement method based on sample identification under time domain discrete main lobe interference
Yang et al. Fast generation of deceptive jamming signal against space-borne SAR
CN111830495B (en) Airborne radar self-adaptive beam forming algorithm based on convex optimization learning
CN117518095A (en) Method and system for calculating failure area of spoofing jammer of bistatic SAR system
CN113791392B (en) Spoofing method based on frequency control array to omnidirectional amplitude comparison single pulse direction finding system
CN115201821B (en) Small target detection method based on strong target imaging cancellation
CN112415469B (en) Rapid interference direction finding method for two-dimensional digital array radar

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant