CN113452250A - Single-power-supply-driven multi-level double-inverter topological structure and control method thereof - Google Patents

Single-power-supply-driven multi-level double-inverter topological structure and control method thereof Download PDF

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CN113452250A
CN113452250A CN202110748408.7A CN202110748408A CN113452250A CN 113452250 A CN113452250 A CN 113452250A CN 202110748408 A CN202110748408 A CN 202110748408A CN 113452250 A CN113452250 A CN 113452250A
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converter
voltage source
isolated
source converter
voltage
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CN113452250B (en
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雷家兴
全相军
冯双
赵剑锋
陈武
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Southeast University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels

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Abstract

The invention discloses a single power supply driven multi-level double-inverter topological structure, which comprises a first voltage source converter, a second voltage source converter, a non-isolated DC-DC converter and a high-frequency common mode filter, wherein the circuit connection mode of the topological structure is as follows: the input power supply is connected to a direct current bus of the first voltage source converter, the input power supply is connected to the input of the non-isolated DC-DC converter, the output of the non-isolated DC-DC converter is connected to a direct current bus of the second voltage source converter, and the alternating current output of the first voltage source converter and the alternating current output of the second voltage source converter supply power for the neutral-point-free three-phase load together. The topological structure of the invention can realize the same control performance as the independent power supply double inverter only by the non-isolated DC-DC converter, thereby reducing the number and the loss of power devices, reducing the system cost and improving the operation efficiency; the method has high technical competitiveness and high practical value, and can promote the application and development of the double-inverter multi-level converter.

Description

Single-power-supply-driven multi-level double-inverter topological structure and control method thereof
Technical Field
The invention relates to a double inverter, in particular to a single-power-driven multi-level double inverter topological structure and a control method thereof.
Background
Compared with the traditional flying capacitor type, midpoint clamping type and other multi-level inverter topologies, the double-inverter topology can generate three-level, four-level, five-level and other multi-level output voltages only by changing the voltage ratio of the direct-current bus, the required devices are few, the redundancy is stronger, and the double-inverter topology has wide attention in the fields of motor driving and new energy grid-connected power generation. The traditional double-inverter system requires two independent direct current power supplies, otherwise zero sequence current is generated due to the existence of a zero sequence loop in the system, and further load current distortion and system loss increase are caused.
However, practical systems are typically configured with only a single power supply in view of reducing the complexity of the system's power distribution. The actual dual inverter therefore has to generate a second independent DC power source on its own, which is generally achieved by an isolated DC-DC converter. The isolated DC-DC converter can obtain the optimal control performance of the double-inverter system, but the required devices are large in quantity, high in cost, large in loss and low in efficiency. For this reason, the researchers have proposed a hybrid power source double inverter scheme with a floating capacitor, i.e., the dc bus of the second inverter is supported only by a large-capacity energy storage capacitor. According to the scheme, a separate second direct current bus power supply is not needed, the cost is low, and the efficiency is high. However, the direct-current bus capacitor of the second inverter needs to keep charge/discharge balance, the second inverter can only control the reactive component at the alternating-current side, the active supporting capacity is limited, and the running performance of the double inverters is reduced.
Disclosure of Invention
The invention aims to provide a single-power-supply-driven multi-level double-inverter topological structure and a control method thereof, which reduce the number of required devices and loss, reduce the system cost and improve the operation efficiency on the basis of keeping the control performance of an independent power supply double-inverter.
The purpose of the invention can be realized by the following technical scheme:
a single power supply driven multilevel double-inverter topological structure comprises a first voltage source converter, a second voltage source converter, a non-isolated DC-DC converter and a high-frequency common mode filter, and the circuit connection mode of the topological structure is as follows: an input power supply is connected to a direct current bus of the first voltage source converter, the input power supply is connected to the input of the non-isolated DC-DC converter, the output of the non-isolated DC-DC converter is connected to a direct current bus of the second voltage source converter, and the alternating current output of the first voltage source converter and the alternating current output of the second voltage source converter supply power for a neutral-point-free three-phase load;
the topological structure is controlled to satisfy the following constraint relation:
Figure BDA0003141338890000021
further, the number of effective switch states of the non-isolated DC-DC converter in the topology is three or more.
Further, the first voltage source converter and the second voltage source converter are typical two-level, three-level and five-level voltage source converters.
Further, the high-frequency common mode filter is located on a direct current bus side of the first voltage source converter, a direct current bus side of the second voltage source converter, an alternating current output side of the first voltage source converter, an alternating current output side of the second voltage source converter, and an input side or an output side of the non-isolated DC-DC converter.
Further, the
Figure BDA0003141338890000022
For the three-phase ac output of the first voltage source converter to output a low frequency component of the common mode voltage with respect to the negative terminal of the dc bus of the first voltage source converter,
Figure BDA0003141338890000023
for the three-phase ac output of the second voltage source converter to output a low frequency component of the common mode voltage with respect to the negative terminal of the dc bus of the second voltage source converter,
Figure BDA0003141338890000024
and outputting a low-frequency component of the voltage of the negative end relative to the input negative end for the non-isolated DC-DC converter.
A control method of a single power supply driven multi-level double-inverter topological structure comprises the following steps:
s1, setting the DC bus voltage reference value of the second voltage source converter to be Udc2 *；
S2 determining generation of non-isolated DC-DC converter
Figure BDA0003141338890000031
In the range of [ v ]min,vmax]；
S3 determining the reference voltage u required by the loado *；
Determining the first and second voltage source converters for generating u S4o *All the switch state combinations and their corresponding switch state duty cycles;
s5, calculating the low-frequency component of the common-mode voltage generated by the first voltage source converter and the second voltage source converter under each switch state combination
Figure BDA0003141338890000032
And
Figure BDA0003141338890000033
s6, selecting an optimal switch state combination and applying the optimal switch state combination to the first voltage source converter and the second voltage source converter;
s7, mixing
Figure BDA0003141338890000034
As non-isolated DC-DC converters
Figure BDA0003141338890000035
Reference value
Figure BDA0003141338890000036
S8 according to Udc2 *And
Figure BDA0003141338890000037
the switching state of the non-isolated DC-DC converter and its duty cycle are determined.
Further, the selection principle of the optimal switch state combination in S6 is as follows: produced by a combination of switching states
Figure BDA0003141338890000038
Is located at [ v ]min,vmax]In range and the switching state combinations produce minimal switching losses.
Further, the specific method for determining the switching state and the duty cycle of the non-isolated DC-DC converter in S6 includes:
s81 output voltage U to non-isolated DC-DC converterdc2And the output current is subjected to double closed-loop control to generate a reference value V of the output voltage of the bridge armL *；
S82 according to
Figure BDA0003141338890000039
And VL *And calculating the duty ratio of each switching state, and only adopting three switching states at any time to obtain all duty ratio values because the number of unknown variables is greater than the equation number.
The invention has the beneficial effects that:
1. the topological structure of the invention can realize the same control performance as the independent power supply double inverter only by the non-isolated DC-DC converter, thereby reducing the number and the loss of power devices, reducing the system cost and improving the operation efficiency;
2. the topological structure has higher technical competitiveness and higher practical value, and can promote the application and development of the double-inverter multi-level converter.
Drawings
The invention will be further described with reference to the accompanying drawings.
FIG. 1 is a diagram of a dual inverter topology of the present invention;
FIG. 2 is a block diagram of a non-isolated DC-DC converter topology of the present invention;
FIG. 3 is a block diagram of a non-isolated DC-DC converter topology of the present invention;
FIG. 4 is a block diagram of a non-isolated DC-DC converter topology of the present invention;
FIG. 5 is a block diagram of a non-isolated DC-DC converter topology of the present invention;
FIG. 6 is a simulation of the load line voltage (phase A) of the present invention;
FIG. 7 is a simulation result of the load phase current (phase A) of the present invention without the high frequency common mode filter;
FIG. 8 is a simulation result of the load phase current (phase A) of the present invention added to a high frequency common mode filter;
FIG. 9 is a graph of v generated by a non-isolated DC-DC converter of the present inventioncmcAnd reference value thereof
Figure BDA0003141338890000041
Schematic representation.
Detailed Description
The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
A single power driven multilevel double inverter topology comprises a first voltage source converter VSC1, a second voltage source converter VSC2, a non-isolated DC-DC converter and a high frequency common mode filter, wherein alternating current output sides of the VSC1 and the VSC2 jointly supply three-phase loads without neutral points as shown in figure 1. A typical three-phase load is an open-winding machine. Input power supply Udc1Connected to the DC bus of VSC1, and input power Udc1Generating a DC bus voltage U of VSC2 by a non-isolated DC-DC converterdc2. In the figure, the high-frequency common mode filter is located on the input side of the non-isolated DC-DC converter, but may also be located on the DC bus side of the VSC1, the DC bus side of the VSC2, the ac output side of the VSC1, the ac output side of the VSC2 or the output side of the non-isolated DC-DC converter. Both VSC1 and VSC2 may be typical two-level or three-level, five-level, etc. multilevel voltage source converters.
The working principle of the proposed topology of the present invention is further explained below. To achieve excellent dual inverter output control performance, the VSC1 and VSC2 can be modulated like independent source dual inverters. For example, the output voltage vector may be decomposed into two separate voltage vectors and assigned to each of VSC1 and VSC2 for modulation. The vectors generated by the VSC1 and the VSC2 can also be modulated as a whole. According to the principle of the voltage source converter modulation algorithm, the ac output thereof generates a common mode voltage. In this specification, the common mode voltage reference points generated by the VSCs 1 and 2 are set as the respective dc bus voltage negative terminals. Defining the common mode voltage transient of the VSC1 as vcm1The common mode voltage transient of the VSC2 is vcm2The corresponding low frequency components are respectively
Figure BDA0003141338890000051
And
Figure BDA0003141338890000052
if the VSC1 and the dc bus negative terminal of the VSC2 are directly connected, a common mode voltage v will be generated across the loadcm1-vcm2Low frequency component thereof
Figure BDA0003141338890000053
Obvious low-frequency zero-sequence current can be generated, and the load operation performance is deteriorated. To this end, the present invention employs a non-isolated DC-DC converter to counteract
Figure BDA0003141338890000054
Typical non-isolated DC-DC converter topologies suitable for use in the present invention are shown in fig. 2, 3, 4, 5. In the figure, 4 converters are all in a full-bridge structure and are provided with 4 switchesOff S1、S2、S3And S4And (4) forming. In FIGS. 2 and 3, Udc1To Udc2For step-up conversion, adapted to Udc2＞Udc1The dual inverter system of (1); in FIGS. 4 and 5, Udc1To Udc2Is a step-down transformation, and is suitable for Udc2<Udc1The dual inverter system of (1). Non-isolated DC-DC converter cancellation is further described below with reference to FIG. 5
Figure BDA0003141338890000055
The principle of (1). Table 1 shows the switching state of the converter, where VLFor full-bridge converter leg output voltage, for converter to generate Udc2Control of (2); v. ofcmFor the converter output Udc2With respect to the input Udc1Voltage of negative terminal used for compensation in the present invention
Figure BDA0003141338890000056
And (4) controlling. According to the principle of pulse width modulation, the duty ratios of 4 switching states are respectively set as d1、d2、d3And d4Then in order to generate the desired VL *And
Figure BDA0003141338890000057
it should satisfy:
Figure BDA0003141338890000061
at VL *And
Figure BDA0003141338890000062
in the known case, the system of equations has 3 equations, but 4 unknown variables d1、d2、d3And d4. Thus, as long as VL *And
Figure BDA0003141338890000063
satisfy a certain constraint relation, can pass throughThe converter generating the desired VL *And
Figure BDA0003141338890000064
from the equation, it can also be seen that the general characteristics of a non-isolated DC-DC converter suitable for use in the present invention are: the converter has at least 3 active switching states.
In steady state conditions, the voltage drop across the inductor is negligible in FIG. 5, where V isL *Can be approximately considered as being equal to Udc2Are equal. According to each duty ratio, the duty ratios are all [0,1 ]]The requirements of the range can be solved
Figure BDA0003141338890000065
In the range of [0, Udc1-Udc2]. This range is what the non-isolated converter can produce
Figure BDA0003141338890000066
The range of (1).
TABLE 1 switching states of the converter in FIG. 5
State sequence number S1 S2 S3 S4 VL vcm
I 1 0 1 0 0 Udc1
II 1 0 0 1 Udc1 0
III 0 1 1 0 -Udc1 Udc1
IV 0 1 0 1 0 0
Based on the above description of the operating principle, the following description will proceed with fig. 5 as an example to describe the control method of the topology according to the present invention, and the control method includes the following steps:
s1, setting the direct current bus of the VSC2 according to the requirements of the double-inverter systemVoltage reference value of Udc2 *For a 2:1 DC bus voltage dual inverter system, Udc2 *Is 0.5Udc1；
S2 determining what the non-isolated converter of FIG. 5 can produce
Figure BDA0003141338890000067
In the range of [0, Udc1-Udc2]I.e., [0,0.5Udc1]；
S3, carrying out closed-loop control on the voltage and the current of the load to generate a reference voltage u required by the loado *；
S4, determining available u generation of VSC1 and VSC2 according to the principle of the modulation algorithm of the double inverterso *Wherein the VSC1 and the VSC2 can adopt independent modulation or centralized modulation;
s5, calculating the low-frequency components of the common-mode voltage generated by the VSC1 and the VSC2 under each switch state combination
Figure BDA0003141338890000068
And
Figure BDA0003141338890000071
s6, selecting an optimal switch state combination and applying the optimal switch state combination to VSC1 and VSC2, wherein the selection principle of the optimal switch state combination is as follows: produced by a combination of switching states
Figure BDA0003141338890000072
In the range [0,0.5U ] generated by S2dc1]And the switching loss generated by the combination of the switching states is minimum;
s7, mixing
Figure BDA0003141338890000073
As non-isolated DC-DC converters
Figure BDA0003141338890000074
Reference value
Figure BDA0003141338890000075
S8 according to Udc2 *And
Figure BDA0003141338890000076
the method for determining the switching state and the duty ratio of the non-isolated DC-DC converter comprises the following steps:
s81 output voltage U to non-isolated DC-DC converterdc2And the output current is subjected to double closed-loop control to generate a reference value V of the output voltage of the bridge armL *；
S82 according to
Figure BDA0003141338890000077
And VL *The duty ratio of each switch state is calculated by the formula, and because the number of unknown variables is greater than the equation number, only three of the switch states can be adopted at any time, and V isL *For > 0, only I, II and IV switch states can be used, i.e. let d30; for VL *<0, the switching states of I, III and IV alone can be used, i.e., let d20. All duty cycle values can thus be solved.
According to the above description of the operating principle and the control method, the non-isolated DC-DC converter can compensate only the low frequency component of the load side common mode voltage, and cannot compensate the high frequency component. V under the action of high-frequency pulse width modulationcm1-vcm2The high frequency component frequency of (2) is up to 10kHz or more. Then v can be filtered out by only needing a high-frequency common mode filter with smaller capacitycm1-vcm2The high frequency component of (2).
A simulation model of the topology provided by the invention is set up in MATLAB/Simulink simulation software, Udc2Is set as Udc1Half of the two inverters exhibit a four-level characteristic. The simulation results are shown in fig. 3-6. As can be seen from fig. 3 and 4, the topology provided by the present invention can achieve the desired four-level output, and the load current has no low-frequency harmonics. Although there are some high frequency harmonics of the load current,this can be filtered out by a high frequency common mode filter. Fig. 5 is a simulation result of the load current after the high-frequency common-mode filter inductor is added, and the result shows that the load current has excellent waveform quality. As can be seen from FIG. 6, the non-isolated DC-DC converter can output the desired output
Figure BDA0003141338890000081
This is a necessary condition for realizing the normal operation of the topology provided by the invention.
In the description herein, references to the description of "one embodiment," "an example," "a specific example" or the like are intended to mean that a particular feature, structure, material, or characteristic described in connection with the embodiment or example is included in at least one embodiment or example of the invention. In this specification, the schematic representations of the terms used above do not necessarily refer to the same embodiment or example. Furthermore, the particular features, structures, materials, or characteristics described may be combined in any suitable manner in any one or more embodiments or examples.
The foregoing shows and describes the general principles, essential features, and advantages of the invention. It will be understood by those skilled in the art that the present invention is not limited to the embodiments described above, which are described in the specification and illustrated only to illustrate the principle of the present invention, but that various changes and modifications may be made therein without departing from the spirit and scope of the present invention, which fall within the scope of the invention as claimed.

Claims (8)

1. A single power supply driven multi-level double-inverter topological structure is characterized by comprising a first voltage source converter, a second voltage source converter, a non-isolated DC-DC converter and a high-frequency common mode filter, wherein the circuit connection mode of the topological structure is as follows: an input power supply is connected to a direct current bus of the first voltage source converter, the input power supply is connected to the input of the non-isolated DC-DC converter, the output of the non-isolated DC-DC converter is connected to a direct current bus of the second voltage source converter, and the alternating current output of the first voltage source converter and the alternating current output of the second voltage source converter supply power for a neutral-point-free three-phase load;
the topological structure is controlled to satisfy the following constraint relation:
Figure FDA0003141338880000011
。
2. the single power driven multilevel double inverter topology of claim 1, wherein the number of active switch states a non-isolated DC-DC converter has in the topology is three or more.
3. The single power driven multilevel double inverter topology of claim 1, wherein the first and second voltage source converters are each a typical two-level, three-level, five-level voltage source converter.
4. The single power driven multilevel double inverter topology of claim 1, wherein the high frequency common mode filter is located on a DC bus side of the first voltage source converter, a DC bus side of the second voltage source converter, an ac output side of the first voltage source converter, an ac output side of the second voltage source converter, an input side or an output side of the non-isolated DC-DC converter.
5. The single power driven multilevel double inverter topology of claim 1, wherein the topology is characterized in that
Figure FDA0003141338880000012
For the three-phase ac output of the first voltage source converter to output a low frequency component of the common mode voltage with respect to the negative terminal of the dc bus of the first voltage source converter,
Figure FDA0003141338880000013
for three-phase AC output of the second voltage source converterThe low frequency component of the common mode voltage with respect to the negative terminal of the dc bus of the second voltage source converter,
Figure FDA0003141338880000014
and outputting a low-frequency component of the voltage of the negative end relative to the input negative end for the non-isolated DC-DC converter.
6. The method for controlling a multilevel double inverter topology according to any of claims 1 to 5, characterized in that the method for controlling a topology comprises the steps of:
s1, setting the DC bus voltage reference value of the second voltage source converter to be Udc2 *；
S2 determining generation of non-isolated DC-DC converter
Figure FDA0003141338880000021
In the range of [ v ]min,vmax]；
S3 determining the reference voltage u required by the loado *；
Determining the first and second voltage source converters for generating u S4o *All the switch state combinations and their corresponding switch state duty cycles;
s5, calculating the low-frequency component of the common-mode voltage generated by the first voltage source converter and the second voltage source converter under each switch state combination
Figure FDA0003141338880000022
And
Figure FDA0003141338880000023
s6, selecting an optimal switch state combination and applying the optimal switch state combination to the first voltage source converter and the second voltage source converter;
s7, mixing
Figure FDA0003141338880000024
As a non-partitionFrom DC-DC converter
Figure FDA0003141338880000025
Reference value
Figure FDA0003141338880000026
S8 according to Udc2 *And
Figure FDA0003141338880000027
the switching state of the non-isolated DC-DC converter and its duty cycle are determined.
7. The control method according to claim 6, wherein the optimal switch state combination in S6 is selected by: produced by a combination of switching states
Figure FDA0003141338880000028
Is located at [ v ]min,vmax]In range and the switching state combinations produce minimal switching losses.
8. The control method according to claim 6, wherein the specific method for determining the switch state and the duty ratio of the non-isolated DC-DC converter in S6 comprises:
s81 output voltage U to non-isolated DC-DC converterdc2And the output current is subjected to double closed-loop control to generate a reference value V of the output voltage of the bridge armL *；
S82 according to
Figure FDA0003141338880000029
And VL *And calculating the duty ratio of each switching state, and only adopting three switching states at any time to obtain all duty ratio values because the number of unknown variables is greater than the equation number.
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