CN113328644A - Passive control method for capacitor voltage fluctuation of modular multilevel converter - Google Patents
Passive control method for capacitor voltage fluctuation of modular multilevel converter Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/483—Converters with outputs that each can have more than two voltages levels
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/12—Arrangements for reducing harmonics from ac input or output
- H02M1/126—Arrangements for reducing harmonics from ac input or output using passive filters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
- H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
- H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
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Abstract
The invention relates to a modularized multi-level capacitor voltage fluctuation passive control method, which comprises the following steps: establishing an MMC fluctuation capacitor voltage state equation based on a PCHD model; based on the established MMC fluctuation capacitor voltage state equation, an MMC capacitor voltage fluctuation passive controller based on a PCHD model is further established to obtain fluctuation capacitor voltage control quantity; processing the voltage control quantity of the fluctuation capacitor by adopting a pulse modulation method to obtain a corresponding trigger pulse signal; and controlling the switching state of the converter of each phase bridge arm submodule of the MMC according to the trigger pulse signal. Compared with the prior art, the passive control method based on the PCHD model is used for suppressing the voltage fluctuation of the MMC capacitor, has the advantages of simple control law form, no singular point and good stability, and can effectively suppress the voltage fluctuation of the MMC capacitor.
Description
Technical Field
The invention relates to the technical field of control of modular multilevel converters, in particular to a passive control method for capacitor voltage fluctuation of a modular multilevel converter.
Background
Modular Multilevel Converters (MMC) have been widely used in the field of large-scale renewable energy grid connection at present due to their advantages of low harmonic content, low switching loss, strong fault ride-through capability, convenience in Modular capacity expansion, and industrial production. However, large-scale renewable energy power generation has the characteristics of intermittence and volatility, so that the interphase energy imbalance of the three-phase MMC is easily caused, and further the imbalance of the sub-module capacitor voltage is caused. The MMC capacitor voltage fluctuation inevitably increases the converter loss, so that the output voltage of the alternating current side has deviation, and the reliable operation of the system is influenced in severe cases.
For this reason, it is necessary to suppress the fluctuation of the MMC capacitor voltage, and the conventional method adopts a vector control method, which is designed for the nonlinear nature of the MMC submodule capacitor voltage fluctuation system, and does not start from an energy perspective, so that when there is an uncertain disturbance situation, the immunity and robustness of the vector controller will face a challenge that is difficult to overcome. Compared with the traditional vector control method, the nonlinear control method is adopted in the prior art, and the controller capable of reflecting the nonlinear essence of the MMC sub-module capacitor voltage fluctuation system is designed from the energy perspective, so that the control performance is improved in the aspects of stability and robustness of a closed-loop control system. Therefore, how to realize the improvement of dynamic and static response performance on the premise that the design of the controller is as simple as possible and ensure the further improvement of the global progressive stability and robustness of the system is a key problem which must be solved by the engineering application of the MMC submodule capacitor voltage fluctuation inhibition.
Disclosure of Invention
The invention aims to overcome the defects of the prior art and provide a passive control method for the capacitance-voltage fluctuation of a modular multilevel converter, so that the MMC capacitance-voltage fluctuation is effectively restrained by a simple-form controller, and the global gradual stability and robustness of a system can be improved.
The purpose of the invention can be realized by the following technical scheme: a modularized multi-level capacitor voltage fluctuation passive control method comprises the following steps:
s1, establishing an MMC fluctuation capacitance voltage state equation based on a PCHD (port-controlled Hamiltonian with dispersion, port controlled dissipation Hamiltonian) model;
s2, further constructing an MMC capacitor voltage fluctuation passive controller based on the PCHD model based on the MMC fluctuation capacitor voltage state equation established in the step S1 to obtain a fluctuation capacitor voltage control quantity;
s3, processing the voltage control quantity of the fluctuation capacitor by adopting a pulse modulation method to obtain a corresponding trigger pulse signal;
and S4, controlling the switching state of the converter of each phase bridge arm submodule of the MMC according to the trigger pulse signal.
Further, in step S1, a state variable, an input variable, and an output variable are respectively defined in a dq rotation coordinate system, where the state variable is a product of a three-phase injected circular current double frequency dq axis component and a bridge arm inductance, the input variable is a three-phase ripple capacitance voltage dq axis component, and the output variable is a three-phase injected circular current double frequency dq axis component.
Further, the MMC fluctuation capacitance voltage state equation is specifically:
x＝[x1 x2]T＝[Lmicird Lmicirq]T
u＝[u1 u2]T＝[ucird ucirq]T
y＝[y1 y2]T＝[icird icirq]T
where x is a state variable, u is an input variable, y is an output variable, LmIs bridge arm inductance icird、icirqThe components u of the d-axis and q-axis of the three-phase injected circulating current frequency doubling are respectivelycird、ucirqD-axis and q-axis components of the three-phase ripple capacitance voltage, J (x) is an interconnection matrix, R (x) is a damping matrix, g (x) is a port matrix, H (x) is an energy function, omega0At fundamental angular frequency, RmIs a resistance of a bridge arm, and is,
is a differential operator.
Further, the step S2 specifically includes the following steps:
s21, setting an expected balance point after the MMC sub-module fluctuation capacitor voltage system injects circulating current;
and S22, obtaining a passive control law based on the PCHD model by taking the difference between the state variable and the expected balance point as a control target and combining an MMC fluctuation capacitor voltage state equation, and obtaining the fluctuation capacitor voltage control quantity.
Further, the desired balance point is specifically:
wherein x is*In order to expect a point of equilibrium,
and
and respectively a three-phase injection circulation frequency doubling d-axis component reference track and a q-axis component reference track.
Further, the step S22 specifically includes the following steps:
s221, according to the control target x-x*Designing a corresponding expected energy function as 0;
s222, obtaining a state equation of the MMC sub-module fluctuation capacitor voltage closed-loop system by combining an MMC fluctuation capacitor voltage state equation based on an expected energy function;
and S223, further obtaining a passive control law based on the PCHD model according to a state equation of the MMC sub-module fluctuation capacitor voltage closed-loop system.
Further, the expected energy function is specifically:
wherein Hd(x) As a function of the desired energy.
Further, the state equation of the MMC submodule fluctuation capacitance voltage closed-loop system specifically is as follows:
wherein, Jd(x) Interconnection matrix desired for the system, Rd(x) A desired damping matrix for the system.
Further, the interconnection matrix desired by the system is specifically:
Jd(x)＝J(x)+Ja(x)
Ja(x)＝0
wherein, Ja(x) Is an injected dissipation matrix;
the desired damping matrix of the system is specifically:
Rd(x)＝R(x)+Ra(x)
wherein R isa(x) For an injected damping matrix, ra1、ra2Is the injected positive damping parameter.
Further, the passive control law based on the PCHD model is specifically:
wherein u iscird、ucirqThe three-phase fluctuation capacitance voltage d-axis and q-axis components are respectively the fluctuation capacitance voltage control quantity.
Compared with the prior art, the method is based on a PCHD model and a passivity theory, based on an established MMC fluctuation capacitor voltage state equation, through energy function shaping, a control target can obtain the minimum value at an expected balance point, and by means of input and output mapping of a PCHD system, the overall gradual stability of the system can be effectively ensured, so that the accuracy of obtaining the subsequent fluctuation capacitor voltage control quantity is ensured, and the reliability of MMC capacitor voltage fluctuation suppression is improved;
in addition, the PCHD model-based MMC capacitor voltage fluctuation passive controller can realize the rapid tracking of the injected circulation reference track while ensuring the overall stability of the system, and has simple control law form, better transient performance and stability.
Drawings
FIG. 1 is a schematic flow diagram of the process of the present invention;
FIG. 2 is a schematic diagram of an embodiment of an application process;
FIG. 3 is a schematic diagram of an MMC three-phase equivalent circuit structure;
FIG. 4 is a schematic diagram of the fluctuation of the capacitance and voltage of the MMC sub-module after the method of the present invention is applied in the embodiment.
Detailed Description
The invention is described in detail below with reference to the figures and specific embodiments.
Examples
As shown in fig. 1, a modular multi-level capacitor voltage fluctuation passive control method includes the following steps:
s1, establishing an MMC fluctuation capacitance-voltage state equation based on a PCHD model, specifically defining a state variable, an input variable and an output variable respectively under a dq rotation coordinate system: the state variable is the product of the three-phase injection circulation double frequency dq axis component and the bridge arm inductance, the input variable is the three-phase fluctuation capacitance voltage dq axis component, and the output variable is the three-phase injection circulation double frequency dq axis component;
the MMC fluctuation capacitor voltage state equation is specifically as follows:
x＝[x1 x2]T＝[Lmicird Lmicirq]T
u＝[u1 u2]T＝[ucird ucirq]T
y＝[y1 y2]T＝[icird icirq]T
where x is a state variable, u is an input variable, y is an output variable, LmIs bridge arm inductance icird、icirqThe components u of the d-axis and q-axis of the three-phase injected circulating current frequency doubling are respectivelycird、ucirqD-axis and q-axis components of the three-phase ripple capacitance voltage, J (x) is an interconnection matrix, R (x) is a damping matrix, g (x) is a port matrix, H (x) is an energy function, omega0At fundamental angular frequency, RmIs a resistance of a bridge arm, and is,
is a differential operator;
s2, further constructing and obtaining an MMC capacitor voltage fluctuation passive controller based on the PCHD model based on the MMC fluctuation capacitor voltage state equation established in the step S1 to obtain a fluctuation capacitor voltage control quantity, specifically:
s21, setting an expected balance point after the MMC sub-module fluctuation capacitor voltage system injects circulating current:
wherein x is*In order to expect a point of equilibrium,
and
respectively injecting circulating current double frequency d-axis and q-axis component reference tracks for three phases;
s22, taking the difference between the state variable and the expected balance point as zero as a control target, combining an MMC fluctuation capacitance voltage state equation, obtaining a passive control law based on a PCHD model, and obtaining a fluctuation capacitance voltage control quantity:
first according to a control target x-x*0, designing the corresponding expected energy function — -
Wherein Hd(x) Is a function of the desired energy;
and then obtaining a state equation of the MMC submodule fluctuation capacitor voltage closed-loop system based on an expected energy function and by combining the MMC fluctuation capacitor voltage state equation
Jd(x)＝J(x)+Ja(x)
Ja(x)＝0
Rd(x)＝R(x)+Ra(x)
Wherein, Jd(x) Interconnection matrix desired for the system, Rd(x) Damping matrix desired for the system, Ja(x) For an implanted dissipative matrix, Ra(x) For an injected damping matrix, ra1、ra2Is the injected positive damping parameter;
s223, further obtaining a passive control law based on the PCHD model according to a state equation of the MMC sub-module fluctuation capacitance voltage closed-loop system:
wherein u iscird、ucirqThe three-phase fluctuation capacitance voltage d-axis and q-axis components are respectively used as the fluctuation capacitance voltage control quantity;
s3, processing the voltage control quantity of the fluctuation capacitor by adopting a pulse modulation method to obtain a corresponding trigger pulse signal;
and S4, controlling the switching state of the converter of each phase bridge arm submodule of the MMC according to the trigger pulse signal.
The present embodiment applies the above method, and the process thereof is shown in fig. 2:
step 1: the three-phase MMC circuit structure and the topological diagram of the sub-modules are shown in FIG. 3, and the MMC fluctuation capacitor voltage dynamic equation under dq rotation coordinate system obtained from FIG. 3 is
Wherein, ω is0At the fundamental angular frequency, LmIs bridge arm inductance, RmIs bridge arm resistance icirdAnd icirqD-and q-axis components, u, for frequency doubling of the three-phase injected circulating currentcirdAnd ucirqThe d-axis and q-axis components of the three-phase ripple capacitance voltage,
t is time, which is a differential operator.
Selecting a state variable x, an input variable u and an output variable y as follows:
in the formula: [. the]TIs the transpose of the matrix.
Designing an orthodefinite quadratic energy function H (x) as
Carrying out equivalent transformation on the MMC fluctuation capacitance voltage dynamic equation (1) to obtain a PCHD model of MMC submodule capacitor voltage fluctuation
Wherein the content of the first and second substances,
interconnection matrix
Damping matrix
Port matrix
In the formula (I), the compound is shown in the specification,
is a differential operator.
The dissipative inequality obtainable from equations (3) and (4)
The left side of the equation (5) is increment of the whole MMC fluctuation capacitor voltage system, the right side is external supply energy, and the passivity theory shows that: mapping u → x is strictly passive in output, and the MMC fluctuation capacitor voltage system has passive characteristics.
Step 2: according to the system control performance target, setting the expected balance point of the MMC submodule capacitor voltage fluctuation system after injection circulation to be
In the formula (I), the compound is shown in the specification,
and
and d-axis and q-axis component reference tracks are frequency-doubled for the three-phase injected circulating current.
According to control target x-x*Designing an expected energy function of the MMC sub-module capacitance voltage fluctuation suppression control system as 0
From the formulas (4) and (7), the state equation of the MMC submodule fluctuation capacitance voltage closed-loop system can be obtained as
In the formula, Jd(x)＝J(x)+Ja(x) Interconnection matrix desired for the system, Rd(x)＝R(x)+Ra(x) Damping matrix desired for the system, Ja(x)＝0、
Respectively an injected dissipation matrix and a damping matrix, ra1、ra2Is the injected positive damping parameter.
The passive control law based on the PCHD model obtained from equation (8) is
The formula (9) can ensure that the closed-loop control system can realize effective inhibition of the capacitance voltage fluctuation of the MMC sub-module on the premise of global gradual stabilization.
A simulation model of an MMC capacitor voltage fluctuation control system is built in MATLAB/Simulink, the effectiveness of the method is verified, and simulation parameters of the embodiment are shown in Table 1.
TABLE 1
| Simulation model parameters and units | Numerical value |
| Number of submodules n/ | 24 |
| Submodule capacitor C/ |
2 |
| Bridge arm inductance L/mH | 5 |
| Bridge arm resistance R/omega | 5 |
| Rated voltage u at AC sidek/V | 220 |
| Frequency f/Hz of AC system | 50 |
| DC side voltage Udc/V | 650 |
| AC side inductor Lg/mH | 1 |
| AC side resistor Rg/mΩ | 100 |
And carrying out simulation test by adopting an MMC capacitor voltage fluctuation passivity control method based on a PCHD model under the steady-state operation of the MMC system. The simulation result of the method for suppressing the capacitance-voltage fluctuation of the promoter module when t is 0.3s is shown in fig. 4. Fig. 4 analyzes and shows that when sub-module capacitance voltage fluctuation suppression is not adopted before t is 0.3s, the MMC sub-module capacitance voltage fluctuation is large, and after the PCHD model-based passive control method is implemented at t is 0.3s, the transient transition time period is fast in dynamic response, so that the effective suppression of the MMC sub-module capacitance voltage fluctuation is realized, and the stability of the system is improved.
Claims (10)
1. A modularized multi-level capacitor voltage fluctuation passive control method is characterized by comprising the following steps:
s1, establishing an MMC fluctuation capacitor voltage state equation based on a PCHD model;
s2, further constructing an MMC capacitor voltage fluctuation passive controller based on the PCHD model based on the MMC fluctuation capacitor voltage state equation established in the step S1 to obtain a fluctuation capacitor voltage control quantity;
s3, processing the voltage control quantity of the fluctuation capacitor by adopting a pulse modulation method to obtain a corresponding trigger pulse signal;
and S4, controlling the switching state of the converter of each phase bridge arm submodule of the MMC according to the trigger pulse signal.
2. The passive control method for voltage fluctuation of modular multilevel capacitors according to claim 1, wherein in step S1, a state variable, an input variable and an output variable are respectively defined in a dq rotation coordinate system, wherein the state variable is a product of a three-phase injection circulating current double frequency dq axis component and a bridge arm inductance, the input variable is a three-phase fluctuation capacitive voltage dq axis component, and the output variable is a three-phase injection circulating current double frequency dq axis component.
3. The modular multi-level capacitor voltage fluctuation passive control method according to claim 2, wherein the MMC fluctuation capacitor voltage state equation is specifically:
x＝[x1 x2]T＝[Lmicird Lmicirq]T
u＝[u1 u2]T＝[ucird ucirq]T
y＝[y1 y2]T＝[icird icirq]T
where x is a state variable, u is an input variable, y is an output variable, LmIs bridge arm inductance icird、icirqIs respectively twice of three-phase injection circulationFrequency d-axis and q-axis components, ucird、ucirqD-axis and q-axis components of the three-phase ripple capacitance voltage, J (x) is an interconnection matrix, R (x) is a damping matrix, g (x) is a port matrix, H (x) is an energy function, omega0At fundamental angular frequency, RmIs a resistance of a bridge arm, and is,
is a differential operator.
4. The modular multi-level capacitor voltage fluctuation passive control method according to claim 3, wherein the step S2 specifically comprises the following steps:
s21, setting an expected balance point after the MMC sub-module fluctuation capacitor voltage system injects circulating current;
and S22, obtaining a passive control law based on the PCHD model by taking the difference between the state variable and the expected balance point as a control target and combining an MMC fluctuation capacitor voltage state equation, and obtaining the fluctuation capacitor voltage control quantity.
5. The modular multilevel capacitor voltage fluctuation passive control method according to claim 4, wherein the desired balance point is specifically:
wherein x is*In order to expect a point of equilibrium,
and
and respectively a three-phase injection circulation frequency doubling d-axis component reference track and a q-axis component reference track.
6. The modular multilevel capacitor voltage fluctuation passive control method according to claim 5, wherein the step S22 specifically comprises the following steps:
s221, according to the control target x-x*Designing a corresponding expected energy function as 0;
s222, obtaining a state equation of the MMC sub-module fluctuation capacitor voltage closed-loop system by combining an MMC fluctuation capacitor voltage state equation based on an expected energy function;
and S223, further obtaining a passive control law based on the PCHD model according to a state equation of the MMC sub-module fluctuation capacitor voltage closed-loop system.
7. The modular multilevel capacitor voltage fluctuation passive control method according to claim 6, wherein the desired energy function is specifically:
wherein Hd(x) As a function of the desired energy.
8. The modular multi-level capacitor voltage fluctuation passive control method according to claim 7, wherein the state equation of the MMC sub-module fluctuation capacitor voltage closed-loop system is specifically as follows:
wherein, Jd(x) Interconnection matrix desired for the system, Rd(x) A desired damping matrix for the system.
9. The method according to claim 8, wherein the interconnection matrix desired by the system is specifically:
Jd(x)＝J(x)+Ja(x)
Ja(x)＝0
wherein, Ja(x) Is an injected dissipation matrix;
the desired damping matrix of the system is specifically:
Rd(x)＝R(x)+Ra(x)
wherein R isa(x) For an injected damping matrix, ra1、ra2Is the injected positive damping parameter.
10. The modular multi-level capacitor voltage fluctuation passive control method according to claim 9, wherein the passive control law based on the PCHD model is specifically:
wherein u iscird、ucirqThe three-phase fluctuation capacitance voltage d-axis and q-axis components are respectively the fluctuation capacitance voltage control quantity.
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| 程启明 等: "准Z 源三电平并网逆变器的无源控制策略", 《电工技术学报》 * |
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