CN113315381A - Novel LCLCL resonant converter and high-efficiency resonant driving method thereof - Google Patents

Novel LCLCL resonant converter and high-efficiency resonant driving method thereof Download PDF

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CN113315381A
CN113315381A CN202110577586.8A CN202110577586A CN113315381A CN 113315381 A CN113315381 A CN 113315381A CN 202110577586 A CN202110577586 A CN 202110577586A CN 113315381 A CN113315381 A CN 113315381A
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capacitor
resonant
converter
circuit
bridge
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杨云龙
林璇
戴明聪
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Jiangsu Jingchuang Advanced Electronic Technology Co Ltd
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Jiangsu Jingchuang Advanced Electronic Technology Co Ltd
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H02M3/33515—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with digital control
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention discloses a novel LCLCLCL resonant converter and a high-efficiency resonant driving method thereof, aiming at solving the defects of the existing high voltage reduction ratio DC/DC converter, a half-bridge LCLCL resonant converter and a switch capacitor converter are combined in series, and the obtained new topological structure has high voltage reduction ratio and high power density and is suitable for high-frequency occasions with high voltage reduction.

Description

Novel LCLCL resonant converter and high-efficiency resonant driving method thereof
Technical Field
The invention belongs to the technical field of resonant converters, and particularly relates to a novel LCLCL resonant converter and a high-efficiency resonant driving method thereof.
Background
The development of the direct-current micro-grid system is rapid day by day, and the corresponding voltage reduction technology from the direct-current bus to the direct-current load is also paid attention, wherein a DC/DC converter with a high voltage reduction ratio becomes a research hotspot. Meanwhile, with the demands for light weight, small size, and high power density of the switching power supply, the switching power supply is also gradually developing to a high frequency. Therefore, the research on the high-voltage reduction ratio DC/DC converter with high efficiency and high power density has important theoretical significance and practical value.
The LCLCL resonant converter can realize ZVS (zero voltage switching) switching-on and low current switching-off of a primary side switching tube in a full load range, can realize ZCS (zero current switching) switching-off of a secondary side diode, and is widely applied to high-efficiency high-frequency converter design. The voltage stress experienced by the primary side switching tube increases significantly as the input voltage increases. Meanwhile, in the occasion of high voltage reduction ratio, the turn ratio of the transformer of the LCLCLCL is increased, the size is larger, and the circuit loss is increased. These disadvantages limit the application of lclclcl resonant converters in high power density, high buck ratio applications.
The switched capacitor circuit does not contain a magnetic element, has small volume and high power density, and is often applied to occasions requiring high power density. However, the switching tube is hard switching, and as the switching frequency increases, the switching loss increases, and the converter efficiency decreases. And the switched capacitor topological structure has a fixed voltage conversion ratio, the realized voltage conversion ratios are all discrete values, and the voltage regulation is lacked. With the increase of the requirement of the voltage conversion ratio, the number of the switched capacitor units is increased, so that the circuit structure is complicated. In addition, in order to ensure the stability of the output power, the switched capacitor needs to have a larger capacitance value, so that the resistance value of the series equivalent resistor (ESR) of the switched capacitor is correspondingly increased, and the efficiency of the circuit is reduced. These disadvantages limit the application of switched capacitor circuits in high frequency, high buck ratio applications.
Disclosure of Invention
The purpose of the invention is as follows: in order to overcome the defects of the existing high voltage reduction ratio DC/DC converter, the invention provides a high voltage reduction converter with a novel topological structure and a high-efficiency resonance driving method thereof.
The technical scheme is as follows: a novel LCLCL resonant converter comprises a half-bridge switch capacitor converter used as a front-stage circuit and used for carrying out n-time voltage reduction and a half-bridge LCLCL resonant converter used as a rear-stage circuit, wherein the half-bridge switch capacitor converter is connected with the half-bridge LCL resonant converter in series; n is an integer.
Further, the half-bridge switched capacitor converter comprises a plurality of input capacitors CnA plurality of flying capacitors CiAnd a plurality of switching tubes Sj(ii) a Wherein n is the number of input capacitors, i is the number of flying capacitors, and j is the number of switching tubes;
the switching tubes are connected in series two by two to form a switching tube pair, each pair of switching tube pairs is connected with an input capacitor in parallel, the connection position of the switching tubes in the switching tube pair is defined as a flying capacitor access point, the flying capacitor access points of two adjacent pairs of switching tube pairs are connected with a flying capacitor, and the voltage of each flying capacitor access point is used as the output voltage of the half-bridge switched capacitor converter;
and the duty ratio of all primary side switching tubes is D-0.5.
Further, the capacitance values of the input capacitor and the flying capacitor are the same.
Further, the half-bridge LCLCLCLCL resonant converter comprises a resonant capacitor CrResonant inductor LrAnd transformer excitation inductance LmSaid resonant capacitor CrIs formed by connecting n identical resonance capacitors in parallel.
Further, the circuit also comprises an output circuit which is a full-wave rectification circuit.
Further, the digital controller comprises an A/D sampling circuit, a compensation circuit and a PWM control circuit; the output voltage of the output circuit enters the compensation circuit after being sampled by the A/D sampling circuit to obtain a control result, and the PWM control circuit adjusts the switching frequency of the primary side switching tube based on the control result.
The invention also discloses a high-efficiency resonance driving method, which comprises the following processes:
the converter is constructed by taking a half-bridge switch capacitor converter as a preceding-stage circuit, taking a half-bridge LCLCLCL resonant converter as a subsequent-stage circuit and taking a full-wave rectification circuit as an output circuit, and connecting the half-bridge switch capacitor converter and the half-bridge LCLCL resonant converter in series:
in the front-stage circuit, according to the switching frequency, the corresponding switching tube is conducted, and n times of voltage reduction and current equalization are carried out on the input high-voltage direct-current voltage; when the voltage with completely same fundamental wave components is input to the rear-stage circuit, third harmonic waves are injected into the rear-stage circuit, the utilization rate of energy is improved, the rectification loss of the rear stage is reduced, and the efficiency is improved; meanwhile, a system obtains a new gain transfer function, has a zero gain point, and can better design an excellent soft start and overcurrent protection scheme;
in a post-stage circuit, filtering higher harmonics to obtain a required working voltage;
in an output circuit, full-wave rectification is carried out on the output voltage of the half-bridge LCLCLCL resonant converter to obtain the final output voltage;
adjusting the switching frequency of a primary side switching tube in the half-bridge switched capacitor converter according to the final output voltage by a digital control method; and applying the adjusted switching frequency to the front-stage circuit.
Further, the half-bridge switched capacitor converter comprises a plurality of input capacitors CnA plurality of flying capacitors CiAnd a plurality of switching tubes Sj(ii) a Wherein n is the number of input capacitors, i is the number of flying capacitors, and j is the number of switching tubes;
the switching tubes are connected in series two by two to form a switching tube pair, each pair of switching tube pairs is connected with an input capacitor in parallel, the connection position of the switching tubes in the switching tube pair is defined as a flying capacitor access point, the flying capacitor access points of two adjacent pairs of switching tube pairs are connected with a flying capacitor, and the voltage of each flying capacitor access point is used as the output voltage of the half-bridge switched capacitor converter; the capacitance values of the input capacitor and the flying capacitor are the same; and the duty ratio of all primary side switching tubes is D-0.5.
Further, the half-bridge LCLCLCLCL resonant converter comprises a resonant capacitor CrResonant inductor LrAnd transformer excitation inductance Lm(ii) a Wherein the resonant capacitor CrIs formed by connecting n identical resonance capacitors in parallel.
Has the advantages that: compared with the prior art, the invention has the following advantages:
(1) compared with an asymptotic horizontal axis approximation type resonance curve of the LLC, the LCLCL converter has better high-frequency resolution, has better adjustment capability on the fluctuation of input voltage and load resistance, and has better robustness;
(2) compared with all other current resonant converters, the gain curve of the LCLCL converter has a unique zero gain point, and a complete soft start and overcurrent protection scheme can be designed according to the zero gain point;
(3) the switch capacitor of the invention provides larger voltage reduction capability, has the capability of providing third harmonic injection for a rear-stage half-bridge LCLCLCL resonant converter, reduces the average value capability of the rectification current, improves the efficiency, and can reduce the average current by 74 percent under the condition of the same effective value of the load current, so the LCLCL resonant topology can improve the efficiency;
(4) compared with the traditional LLC resonant converter, the input voltage of a rear-stage LLC resonant tank of the switched capacitor LLC resonant converter is reduced, and the turn ratio and the volume of a coil of the transformer are reduced; compared with a switched capacitor circuit, the switched capacitor LLC converter has the advantages of no magnetic element in the switched capacitor circuit, high power density, small volume, capability of realizing automatic voltage sharing of input voltage and the like, and can realize soft switching of a switching tube in the switched capacitor circuit by utilizing the resonance effect of the LLC, work in a ZVS (zero voltage switching) on state, reduce switching loss and realize higher efficiency; the invention combines the topological structure of the novel LCLCL and the topological structure of the switch capacitor converter, so that the obtained topological structure has the characteristics of reliable soft switching, high efficiency, high power density and high voltage reduction ratio.
Drawings
Fig. 1 is a schematic structural diagram of a switched capacitor lclclclclcl resonant converter;
FIG. 2 is a simplified circuit and mode diagram of a switched capacitor;
FIG. 3 is a graph of the output voltage waveform of the switched capacitor circuit;
FIG. 4 is a driving waveform diagram;
FIG. 5 is a waveform diagram of output waveforms of three output terminals of the switched capacitor;
fig. 6 shows a graph of the output voltage waveform.
Detailed Description
The invention is further illustrated below with reference to the figures and examples.
Considering that the lclclcl resonant converter and the switched capacitor circuit both have a half-bridge structure and a control strategy with a duty ratio of 0.5, in this embodiment, the half-bridge LCLCL resonant converter and the switched capacitor converter are combined in series, and the obtained new topology structure has a high voltage reduction ratio and a high power density, and simultaneously, the use of an inductance device is saved, so that the high-voltage-reduction high-frequency inverter is suitable for high-voltage-reduction high-frequency occasions.
The switched capacitor lclclcl resonant converter structure of the present embodiment is shown in fig. 1, and in the topology structure, the switched capacitor lcl resonant converter structure includes a front-stage switched capacitor circuit, a rear-stage lclclcl resonant circuit, and an output circuit;
FIG. 2 (a) shows a switched capacitor circuit of the preceding stage, in which V is set to VinFor input of high-voltage direct voltage, Vout1、Vout2、Vout3Is the low-voltage direct-current voltage at the output end. Input capacitance C1、C2、C3Flying capacitor C4、C5And a switching tube S1、S2、S3、S4、S5、S6The pre-stage switched capacitor circuit with automatic voltage-sharing capability is formed. The front-stage switch capacitor circuit can realize voltage division and current sharing, can reduce the voltage stress of a switch tube, reduces the input voltage of a rear-stage LCLCL resonant cavity, and reduces the turn ratio and the volume of a transformer. To clarify the characteristics of the switched capacitor circuit, it is analyzed below.
To simplify the analysis, the following assumptions were made for the switched capacitor circuit:
(1) the switched capacitor circuit works in a static stable state;
(2) input capacitance C1、C2、C3And flying capacitor C4、C5All the volume values are equal;
(3) each switch tube is an ideal switch tube.
(4) Neglecting dead time td。
In a switching period, the switched capacitor circuit can be divided into a switching tube S1、S3、S5Mode 1 and switching tube S during simultaneous conduction2、S4、S6Mode 2 when on at the same time. Fig. 2 shows a simplified circuit of the switched capacitor and corresponding equivalent circuits in two modes, and the charging and discharging conditions of the current are labeled.
Mode 1: when switching tube S1、S3、S5When turned on, the equivalent circuit diagram is shown in fig. 2 (b). At this time, the input capacitance C1And flying capacitor C4Parallel flying capacitor C4To input capacitance C1Charging until the voltage of the two is balanced; input capacitance C2And flying capacitor C5Parallel, input capacitance C2To flying capacitor C5Charging until the two voltages are balanced. Because of the input capacitance C1、C2、C3The voltage at both ends is inputted with a voltage VinClamping, so that the input capacitance C3The balance of the total amount of charge is maintained by discharging the electricity to the outside. And has a flying capacitor C4Discharge capacity and flying capacitor C5The charging amount of the capacitor is equal to maintain the stability of the voltage at the output end of the switched capacitor. At this time Vout1＝Vin、Vout2＝2/3Vin、Vout3＝1/3VinCorresponding switching tube S2、S4、S6The voltage stress at both ends is 1/3Vin。
Mode 2: when switching tube S2、S4、S6When turned on, the equivalent circuit diagram is shown in fig. 2 (c). At this time, the input capacitance C2And flying capacitor C4Parallel, input capacitance C2To flying capacitor C4Charging until the voltage of the two is balanced; input capacitance C3And flying capacitor C5Parallel flying capacitor C5To input capacitance C3Charging until the two voltages are balanced. Because of the input capacitance C1、C2、C3The voltage at both ends is inputted with a voltage VinClamping, so that the input capacitance C1The balance of the total amount of charge is maintained by discharging the electricity to the outside. And has a flying capacitor C4Charge amount and flying capacitor C5The discharge amount of the capacitor is equal to maintain the stability of the voltage at the output end of the switched capacitor. At this time Vout1＝2/3Vin、Vout2＝1/3Vin、Vout30, corresponding switching tube S1、S3、S5The voltage stress at both ends is 1/3Vin。
Analyzing the mode of the switch capacitor circuit, the following results can be obtained: at each oneIn one switching period, through the input capacitor C1、C2、C3And flying capacitor C4、C5The automatic voltage sharing among the input capacitors is realized by charging and discharging. And the voltage stress of each switching tube is equal and is one third of the voltage of the high-voltage side, which is beneficial to the converter to work in a high-voltage occasion. Fig. 3 shows output voltage waveforms of the respective output terminals of the switched capacitor circuit, and it can be seen that three output terminals output voltage square waves with different amplitudes. Fourier decomposition is performed on the three output voltages to obtain:
Figure BDA0003084899550000041
according to fourier decomposition, the three output voltages have different dc components, but their fundamental components are identical.
The LCLCLCL resonant circuit is connected to the rear stage of the switch capacitor and is composed of a resonant capacitor Cr1、Cr2、Cr3Resonant inductor L consisting of primary side leakage inductance and external leakage inductance of transformerrAnd transformer exciting inductance LmFormed due to resonant capacitance Cr1、Cr2、Cr3The function of blocking direct current is achieved, so that three output voltages at the output end of the switched capacitor circuit can be considered to be equal, and can be used as input voltages of a resonant tank of the rear-stage LCLCLCL. Wherein the switch tube S1、S3、S5Are simultaneously conducted, S2、S4、S6And meanwhile, the two groups of switching tubes are conducted in a complementary mode, and the duty ratio of all primary side switching tubes is D-0.5.
In the rear-stage LCLCLCL resonant circuit, the resonant capacitor CrSplit into three equal resonance capacitors Cr1、Cr2、Cr3The parallel structure can be known from the formula (2) of the current flowing through the capacitor, and the current values flowing through the three resonant capacitor branches are equal and are the resonant current i Lr1/3 of (1). Neglecting the charge and discharge between the flying capacitors, it can be seen that the current flowing through the switch tube in the positive and negative half periods is symmetrical and is the resonance current i Lr1/3 of (1). Thus openingThe output end of the off-capacitor circuit adopts a parallel structure, so that the current stress of the switch tubes can be reduced, and the current sharing among the switch tubes is realized.
Figure BDA0003084899550000051
The output circuit is a full-wave rectification circuit consisting of a middle tap transformer and a rectifying diode D1、D2Output filter capacitor CoAnd a load RoAnd (4) forming. By adopting a digital control method, after the output voltage of the output end is subjected to A/D sampling, sampling data enter a digital controller for carrying out related control calculation, and the switching frequency of a switching tube is adjusted according to an operation result so as to ensure the stability of the output voltage of the output end of the converter.
In order to verify the feasibility of the topological structure and parameter design, a prototype with the following indexes is built:
rated input voltage: 400V;
rated power: 400W;
series resonance frequency: 1MHz (fundamental), 3MHz (third harmonic);
parallel resonance frequency: 2 MHz;
efficiency: higher than 95%;
output voltage: 24V;
output voltage ripple: less than 200 mV;
the model number and parameters of the chip selected by the prototype are shown in Table 1.
TABLE 1
Component and device Parameter value/model number Component and device Parameter value/model number
Main switch tube S1,S2 C2M0280120D Trap capacitor Cp 2.44nF
Trapped wave inductance Lp 2.6uH Primary side driving chip 1EDI20N12AF
Resonant capacitor Cr 4nF Transformer turn ratio n 8:1
Resonant inductor Lr 2.8uH Magnetic core EQ30 EQ20
Excitation inductance Lm 13uH Digital controller TMS320F28335
The following waveforms were obtained: FIG. 4 is a driving waveform diagram, 250 kHz; fig. 5 is a waveform diagram of output waveforms of three output ends of the switched capacitor circuit, and theoretically, the three waveforms are square waves with different upper and lower amplitudes and consistent duty ratios. Fig. 6 shows the output voltage waveform (input voltage 60V) at the output terminal.
The oscillogram shows that the topological structure provided by the invention has feasibility, has the characteristics of high efficiency and high power density, and is suitable for high-frequency occasions with high voltage reduction.

Claims (9)

1. A novel LCLCL resonant converter is characterized in that: the circuit comprises a half-bridge switch capacitor converter used as a front-stage circuit and used for carrying out n-time voltage reduction and a half-bridge LCLCL resonant converter used as a rear-stage circuit, wherein the half-bridge switch capacitor converter is connected with the half-bridge LCLCL resonant converter in series; n is an integer.
2. The LCLCLCL resonant converter according to claim 1, wherein: the half-bridge switched capacitor converter comprises a plurality of input capacitors CnA plurality of flying capacitors CiAnd a plurality of switching tubes Sj(ii) a Wherein n is the number of input capacitors, i is the number of flying capacitors, and j is the number of switching tubes;
the switching tubes are connected in series two by two to form a switching tube pair, each pair of switching tube pairs is connected with an input capacitor in parallel, the connection position of the switching tubes in the switching tube pair is defined as a flying capacitor access point, the flying capacitor access points of two adjacent pairs of switching tube pairs are connected with a flying capacitor, and the voltage of each flying capacitor access point is used as the output voltage of the half-bridge switched capacitor converter;
and the duty ratio of all primary side switching tubes is D-0.5.
3. The LCLCLCL resonant converter according to claim 2, wherein: the capacitance values of the input capacitor and the flying capacitor are the same.
4. A novel lclclclcl resonant converter as claimed in any of claims 1, 2 or 3 wherein: the half-bridge LCLCLCLCL resonant converter comprises a resonant capacitor CrResonant inductor LrAnd transformer excitation inductance LmSaid resonant capacitor CrIs formed by connecting n identical resonance capacitors in parallel.
5. A novel LCLCL resonant converter as claimed in any one of claims 4 wherein: the circuit further comprises an output circuit which is a full-wave rectifying circuit.
6. A novel LCLCL resonant converter as claimed in claim 1 or 5 wherein: the digital controller comprises an A/D sampling circuit, a compensation circuit and a PWM control circuit; the output voltage of the output circuit enters the compensation circuit after being sampled by the A/D sampling circuit to obtain a control result, and the PWM control circuit adjusts the switching frequency of the primary side switching tube based on the control result.
7. A high efficiency resonant driving method, characterized by: the method comprises the following steps:
the converter is constructed by taking a half-bridge switch capacitor converter as a preceding-stage circuit, taking a half-bridge LCLCLCL resonant converter as a subsequent-stage circuit and taking a full-wave rectification circuit as an output circuit, and connecting the half-bridge switch capacitor converter and the half-bridge LCLCL resonant converter in series:
in the front-stage circuit, according to the switching frequency, the corresponding switching tube is conducted, and n times of voltage reduction and current equalization are carried out on the input high-voltage direct-current voltage; when the voltage with completely same fundamental wave components is input to the rear-stage circuit, third harmonic waves are injected into the rear-stage circuit;
in a post-stage circuit, filtering higher harmonics to obtain a required working voltage;
in an output circuit, full-wave rectification is carried out on the output voltage of the half-bridge LCLCLCL resonant converter to obtain the final output voltage;
adjusting the switching frequency of a primary side switching tube in the half-bridge switched capacitor converter according to the final output voltage by a digital control method; and applying the adjusted switching frequency to the front-stage circuit.
8. A high efficiency resonant driving method as set forth in claim 7, wherein: the half-bridge switched capacitor converter comprises a plurality of input capacitors CnA plurality of flying capacitors CiAnd a plurality of switching tubes Sj(ii) a Wherein n is the number of input capacitors, i is the number of flying capacitors, and j is the number of switching tubes;
the switching tubes are connected in series two by two to form a switching tube pair, each pair of switching tube pairs is connected with an input capacitor in parallel, the connection position of the switching tubes in the switching tube pair is defined as a flying capacitor access point, the flying capacitor access points of two adjacent pairs of switching tube pairs are connected with a flying capacitor, and the voltage of each flying capacitor access point is used as the output voltage of the half-bridge switched capacitor converter; the capacitance values of the input capacitor and the flying capacitor are the same; and the duty ratio of all primary side switching tubes is D-0.5.
9. A high efficiency resonant driving method according to claim 7 or 8, characterized by: the half-bridge LCLCLCLCL resonant converter comprises a resonant capacitor CrResonant inductor LrAnd transformer excitation inductance Lm(ii) a Wherein the resonant capacitor CrIs formed by connecting n identical resonance capacitors in parallel.
CN202110577586.8A 2021-05-26 2021-05-26 Novel LCLCL resonant converter and high-efficiency resonant driving method thereof Pending CN113315381A (en)

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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN116191879A (en) * 2023-01-04 2023-05-30 重庆平创半导体研究院有限责任公司 Step-down power converter and control method thereof

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20090303753A1 (en) * 2008-06-10 2009-12-10 Dianbo Fu Multi-Element Resonant Converters
CN103296882A (en) * 2013-05-29 2013-09-11 浙江大学 DC-DC (direct-current to direct-current) resonant converter with automatic voltage equalizing function
US20170353116A1 (en) * 2016-06-07 2017-12-07 Linear Technology Corporation Transformer-based hybrid power converters
CN111682768A (en) * 2020-06-04 2020-09-18 哈尔滨工业大学 LCLCL high-order direct current converter based on stacked bridge and control method
CN112838766A (en) * 2021-01-06 2021-05-25 西南交通大学 High-voltage-reduction-ratio three-level LLC resonant converter and control method thereof
CN113162422A (en) * 2021-04-07 2021-07-23 哈尔滨修齐治平科技开发有限公司 High-voltage-reduction-ratio switch capacitor LCLCLCL resonant converter based on third harmonic and parameter design method

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20090303753A1 (en) * 2008-06-10 2009-12-10 Dianbo Fu Multi-Element Resonant Converters
CN103296882A (en) * 2013-05-29 2013-09-11 浙江大学 DC-DC (direct-current to direct-current) resonant converter with automatic voltage equalizing function
US20170353116A1 (en) * 2016-06-07 2017-12-07 Linear Technology Corporation Transformer-based hybrid power converters
CN111682768A (en) * 2020-06-04 2020-09-18 哈尔滨工业大学 LCLCL high-order direct current converter based on stacked bridge and control method
CN112838766A (en) * 2021-01-06 2021-05-25 西南交通大学 High-voltage-reduction-ratio three-level LLC resonant converter and control method thereof
CN113162422A (en) * 2021-04-07 2021-07-23 哈尔滨修齐治平科技开发有限公司 High-voltage-reduction-ratio switch capacitor LCLCLCL resonant converter based on third harmonic and parameter design method

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
罗清璟 等: "具有自主均压能力的混合型 LLC 谐振变流器研究", 《中国电机工程学报》 *
郝瑞祥等: "一种具有自动均压均流特性的组合式LLC谐振变换器", 《电工技术学报》 *

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN116191879A (en) * 2023-01-04 2023-05-30 重庆平创半导体研究院有限责任公司 Step-down power converter and control method thereof

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Application publication date: 20210827