CN112600446B - Voltage source rectifier current control method of frequency conversion system - Google Patents

Voltage source rectifier current control method of frequency conversion system Download PDF

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CN112600446B
CN112600446B CN202011623320.4A CN202011623320A CN112600446B CN 112600446 B CN112600446 B CN 112600446B CN 202011623320 A CN202011623320 A CN 202011623320A CN 112600446 B CN112600446 B CN 112600446B
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current
phase
voltage
voltage source
quasi
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CN112600446A (en
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杨卫朋
闫新军
王智慧
赵建新
张艳芳
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Shaanxi Aero Electric Co Ltd
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Shaanxi Aero Electric Co Ltd
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B64—AIRCRAFT; AVIATION; COSMONAUTICS
    • B64D—EQUIPMENT FOR FITTING IN OR TO AIRCRAFT; FLIGHT SUITS; PARACHUTES; ARRANGEMENT OR MOUNTING OF POWER PLANTS OR PROPULSION TRANSMISSIONS IN AIRCRAFT
    • B64D47/00—Equipment not otherwise provided for
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Aviation & Aerospace Engineering (AREA)
  • Rectifiers (AREA)

Abstract

The application belongs to the field of control of aircraft power supply systems, and particularly relates to a voltage source rectifier current control method of a frequency conversion system. Mainly comprises the following steps: s1, converting a current dynamic equation in a three-phase static coordinate system into a current dynamic equation in a two-phase static coordinate system to obtain two-phase currents, and similarly obtaining two-phase voltages; s2, obtaining reference currents for regulating and controlling the two-phase currents, wherein the reference currents are designed to be respectively in proportional relation with the two-phase voltages in the corresponding axial directions; s3, acquiring a digital self-adaptive quasi-resonance control law with the center frequency continuously changing along with the system frequency, and determining a proportion quasi-resonance controller based on the control law; s4, determining fundamental wave reference voltage according to a dynamic equation; and S5, generating PWM signals based on the fundamental wave reference voltage and driving switching devices of the corresponding voltage source rectifiers to act. The method can provide good performance for the system when the frequency is changed rapidly in a large range.

Description

Voltage source rectifier current control method of frequency conversion system
Technical Field
The application belongs to the field of control of aircraft power supply systems, and particularly relates to a voltage source rectifier current control method of a frequency conversion system.
Background
The voltage source rectifier has the characteristics of high power density, high electric energy quality and the like, and has very wide application prospect in an aircraft power supply system. The current tracking control in the two-phase static coordinate system has the advantages of simple structure, easiness in implementation, high dynamic response speed and the like, and is one of the most common control strategies of the voltage source converter.
Current control in a two-phase stationary coordinate system often employs a proportional-quasi-resonant controller. However, existing proportional-quasi-resonant controllers are designed for fixed frequencies by setting a bandwidth parameter that is suitable for small range variations in frequency. The aircraft variable frequency alternating current power supply system has the characteristics of large frequency change range (the frequency range of the active wide variable frequency alternating current power supply system is 360Hz-800Hz, the variable frequency range of the narrow variable frequency alternating current power supply system is about 360Hz-540 Hz), high change speed and the like. If a conventional proportional-quasi-resonant controller is used, the tracking performance of the quasi-resonant control law is rapidly reduced when the actual frequency of the power supply system deviates from the design frequency greatly, so that the system performance is seriously reduced, and the system is extremely liable to lose stability. On the other hand, the output of the dc voltage outer loop is usually used as the reference current in the conventional control strategy. This method is simple in principle, but causes current distortion when the three-phase alternating voltage is unbalanced. In order to improve the system performance under the unbalanced voltage condition, the existing method controls the positive sequence current component and the negative sequence current component respectively, so that the quality of the current is improved, but the complexity and the implementation difficulty of a control system are greatly increased.
Disclosure of Invention
In order to solve the technical problems, the application provides a voltage source rectifier current control method of a frequency conversion system, which is a control strategy of self-adaptive proportion-quasi-resonance current and is used for improving the performance of the control system and simplifying the realization of the control system.
The voltage source rectifier current control method of the frequency conversion system mainly comprises the following steps:
step S1, converting a current dynamic equation in a three-phase static coordinate system into a current dynamic equation in a two-phase static coordinate system to obtain a two-phase current i α I β Similarly, two-phase voltage e is obtained α E β ；
Step S2, obtaining a current i for two phases α I β Reference current i for regulation αr I βr Wherein the reference current i αr I βr Two-phase voltages e designed to correspond to the respective axial directions α E β Proportional relationship;
s3, acquiring a digital self-adaptive quasi-resonance control law with center frequency continuously changing along with system frequency, and based on the controlLaw-determining proportional quasi-resonant controller H APQR ；
Step S4, determining fundamental wave reference voltage according to a dynamic equation:
wherein R is the equivalent resistance of the three-phase voltage source rectifier;
and S5, generating PWM signals based on the fundamental wave reference voltage and driving switching devices of the corresponding voltage source rectifiers to act.
Preferably, in step S1, the CLARKE transformation is applied to convert the current dynamics equation in the three-phase stationary coordinate system into the current dynamics equation in the two-phase stationary coordinate system.
Preferably, in step S2, the reference current i αr I βr Two-phase voltages e designed to correspond to the respective axial directions α E β The proportionality coefficient k in the proportionality relationship is designed to: voltage u for said direct current d With the expected output voltage u of the direct current dr The regulated PI controller output, expressed as:
k＝k dp +k di ∫(u dr -u d )
wherein k is dp And k di Respectively representing the proportional and integral gains of the dc voltage control loop.
Preferably, in step S3, the proportional quasi-resonant controller is:
H APQR ＝k id +k qr H d (z)
wherein k is id And k qr Respectively representing the proportion and quasi-resonant gain of the controller, H d (z) is an adaptive quasi-resonant control law H a (s) discretized values.
Preferably, in step S4, a sine wave adjustment method is used to generate a PWM signal, and the corresponding voltage modulation signal is:
wherein u is d Is the voltage of direct current.
Preferably, in step S5, a space vector modulation method is used to generate the PWM signal.
The invention provides a self-adaptive proportion-quasi-resonant current control method of a voltage source rectifier suitable for a frequency conversion system, which can provide good performance for the system when the frequency is changed in a large range and fast, and has good quality of alternating current and reasonable three-phase output distribution when the three-phase alternating voltage is unbalanced. In addition, the invention ensures that the system operates at a high power factor, and has simple principle and easy realization.
Drawings
Fig. 1 is a schematic and schematic diagram of a three-phase voltage source rectifier.
Fig. 2 is a schematic block diagram of a voltage source rectifier adaptive proportional-quasi-resonant current control method applicable to a variable frequency system.
FIG. 3 is a schematic diagram of a simulation waveform of the present application at a constant system frequency of 560 Hz.
FIG. 4 is a schematic diagram of simulated waveforms during a system frequency change from 360Hz to 400Hz at 400Hz/s in the present application.
FIG. 5 is a schematic diagram of simulated waveforms during a system frequency change from 800Hz to 776Hz at-400 Hz/s.
FIG. 6 is a schematic diagram of simulated waveforms during a system frequency change from 500Hz to 510Hz at 400Hz/s under three-phase voltage imbalance conditions of the present application.
Detailed Description
For the purposes, technical solutions and advantages of the present application, the following describes the technical solutions in the embodiments of the present application in more detail with reference to the drawings in the embodiments of the present application. In the drawings, the same or similar reference numerals denote the same or similar elements or elements having the same or similar functions throughout. The described embodiments are some, but not all, of the embodiments of the present application. The embodiments described below by referring to the drawings are exemplary and intended for the purpose of explaining the present application and are not to be construed as limiting the present application.
Furthermore, unless specifically stated and limited otherwise, the terms "mounted," "connected," and the like in the description herein are to be construed broadly and refer to either a fixed connection, a removable connection, or an integral connection, for example; can be mechanically or electrically connected; can be directly connected or indirectly connected through an intermediate medium, and can also be communicated with the inside of two elements, and the specific meaning of the two elements can be understood by a person skilled in the art according to specific situations.
Referring first to FIG. 1, FIG. 1 is a schematic and schematic diagram of a three-phase voltage source rectifier, with three-phase current regulated to DC through T1-T6, where e a 、e b 、e c Respectively representing three-phase voltages at the point of common coupling, i a 、i b 、i c Respectively represent three-phase currents, u a 、u b 、u c Respectively representing the fundamental voltage of the alternating current side of the converter, L and R respectively representing the inductance and equivalent resistance of the filter reactor, u d And C is the dc bus voltage and dc bus capacitance, respectively.
The application provides a voltage source rectifier current control method of a frequency conversion system, which is used for adjusting the on-off state of a switch of T1-T6 and mainly comprises the following steps:
step S1, converting a current dynamic equation in a three-phase static coordinate system into a current dynamic equation in a two-phase static coordinate system to obtain a two-phase current i α I β Similarly, two-phase voltage e is obtained α E β ；
Step S2, obtaining a current i for two phases α I β Reference current i for regulation αr I βr Wherein the reference current i αr I βr Two-phase voltages e designed to correspond to the respective axial directions α E β Proportional relationship;
step S3, obtaining a center frequency which continuously changes along with the system frequencyDigital adaptive quasi-resonant control law and determining a proportion of quasi-resonant controllers H based on said control law APQR ；
Step S4, determining fundamental wave reference voltage according to a dynamic equation:
wherein R is the equivalent resistance of the three-phase voltage source rectifier;
and S5, generating PWM signals based on the fundamental wave reference voltage and driving switching devices of the corresponding voltage source rectifiers to act.
FIG. 2 is a schematic block diagram of a method for adaptive proportional-quasi-resonant current control of a voltage source rectifier for a variable frequency system according to the present application, and referring to FIG. 2, the uppermost row is a simplified schematic diagram of the three-phase voltage source rectifier of FIG. 1, from which the voltage e of the three-phase current before rectification is obtained α E β Current i α I β Rectified DC voltage u d . Then, a PWM generator is formed through steps S1-S6 of the application, and the on-off of the switches of T1-T6 is adjusted based on the PWM generator, and the method specifically comprises the following steps.
1) According to the working principle of the three-phase voltage source rectifier, a current dynamic equation in a three-phase static coordinate system of an alternating current side is obtained;
the principle of the voltage source converter is shown in fig. 1, and the dynamic equation of the three-phase alternating current is as follows:
wherein e a 、e b 、e c Respectively representing three-phase voltages at the point of common coupling, i a 、i b 、i c Respectively represent three-phase currents, u a 、u b 、u c The fundamental voltage on the ac side of the converter is represented by L and R, respectively, and the inductance and equivalent resistance of the filter reactor are represented by L and R, respectively.
2) The current dynamic equation in the three-phase stationary coordinate system is converted into the current dynamic equation in the two-phase stationary coordinate system by using the CLARKE conversion:
obtaining a two-phase current i α I β Similarly, two-phase voltage e is obtained α E β 。
3) Designing proportional relations between alpha-axis reference current and beta-axis reference current and phase voltages of corresponding axial directions, wherein the proportional coefficients are controlled by a direct-current voltage outer ring;
the design current reference signal is:
where k is a controlled coefficient.
The coefficient k is obtained as follows:
k＝k dp +k di ∫(u dr -u d ) (4)
wherein k is dp And k di Respectively representing the proportional and integral gains of the dc voltage control loop.
Discretizing the formula (4) to obtain:
wherein k is d Representing the coefficient obtained by discretizing k, T s Representing the sampling time, Z refers to the transform operator of the Z transform.
So far, referring to fig. 2, k and two-phase voltage e outputted from PI controller α E β After multiplication, i is obtained αr I βr The method comprises the steps of carrying out a first treatment on the surface of the Then and current i α I β After calculation, the voltage is input into a circuit represented by a calculation box on the right side of FIG. 2, wherein the calculation box relates to a voltage dynamic square in a converted two-phase static coordinate systemThe equation involves a proportional quasi-resonant controller H APQR Obtained by calculation in the following steps.
4) Taking the actual frequency of the system as an input parameter, designing a digital self-adaptive quasi-resonance control law with the center frequency continuously changing along with the system frequency;
the s-domain transfer function of the quasi-resonant control law is:
wherein k is r Indicating gain, omega 0 Represents the resonant frequency omega c Representing the bandwidth parameter.
Discretizing equation (6) and expressing as a sampling time T s 、ω 0 、ω c And k r Is a function of (1), can be obtained:
wherein:
n 1 ＝0 (9)
and parameter n 0 、n 2 、d 0 、d 1 And (5) online real-time computing and updating.
5) Combining the proportional link with the self-adaptive quasi-resonance control law generated in the step 4 to design a frequency self-adaptive proportional-quasi-resonance controller;
the design frequency-adaptive proportional-quasi-resonant controller is as follows:
H APQR ＝k id +k qr H d (z) (13)
wherein k is id And k qr The ratio and quasi-resonant gain of the adaptive current tracking controller are shown, respectively.
6) The alpha-axis current error and the beta-axis current error are respectively input into a self-adaptive proportion-quasi-resonance controller designed in the step 5, and the reference fundamental wave voltage of the alternating current side of the rectifier is obtained by combining a dynamic equation of the system;
fundamental wave reference voltage u on alternating current side of voltage source converter α 、u β It can be calculated as:
wherein i is αr And i βr The alpha-axis and beta-axis reference currents generated in the step 3 are respectively.
7) And taking the fundamental wave reference voltage of the alternating current side of the rectifier as input, generating PWM signals according to a modulation method and driving corresponding switching devices to act. In this step, u generated in step 6 α And u β As input, a sine wave modulation or space vector modulation method is adopted to generate PWM signals, and corresponding switching devices are driven to act.
In this example, sine wave modulation is adopted, and corresponding voltage modulation signals are as follows:
wherein u is αr And u βr The voltage modulation signals of the alpha axis and the beta axis are respectively, u d Representing the dc capacitor voltage. Finally, in step S5, a PWM signal is generated based on the fundamental reference voltage and the corresponding PWM signal is drivenThe switching device of the voltage source rectifier acts.
FIG. 3 is a simulated waveform at a constant system frequency of 560Hz, with per unit value being used except for frequency. Wherein u is d 、u dr Representing the DC voltage and its reference, e abc 、i abc Representing three-phase input voltage and three-phase alternating current, P, Q, P, respectively r 、Q r The active, reactive and references respectively are shown as the same for fig. 4-6, where fig. 4 is a simulated waveform during a system frequency change from 360Hz to 400Hz at 400Hz/s, fig. 5 is a simulated waveform during a system frequency change from 800Hz to 776Hz at-400 Hz/s, and fig. 6 is a simulated waveform during a system frequency change from 500Hz to 510Hz at 400Hz/s under three-phase voltage imbalance conditions. As can be seen from simulation waveforms, the control method provided by the application can provide good performance for the system when the frequency is changed in a large range and rapidly, and the alternating current still has good quality and reasonable three-phase output distribution when the three-phase alternating voltage is unbalanced.
Having thus described the technical aspects of the present application with reference to the preferred embodiments illustrated in the accompanying drawings, it should be understood by those skilled in the art that the scope of the present application is not limited to the specific embodiments, and those skilled in the art may make equivalent changes or substitutions to the relevant technical features without departing from the principles of the present application, and those changes or substitutions will now fall within the scope of the present application.

Claims (4)

1. A method for controlling the current of a voltage source rectifier of a frequency conversion system, wherein the voltage source rectifier is used for converting three-phase alternating current into direct current, and the method is characterized by comprising the following steps:
step S1, converting a current dynamic equation in a three-phase static coordinate system into a current dynamic equation in a two-phase static coordinate system to obtain a two-phase current i α I β Similarly, two-phase voltage e is obtained α E β ；
Step S2, obtaining a current i for two phases α I β Reference current i for regulation αr I βr Wherein the reference current i αr I βr Two-phase voltages e designed to correspond to the respective axial directions α E β Proportional relationship;
s3, acquiring a digital self-adaptive quasi-resonance control law with center frequency continuously changing along with system frequency, and determining a proportion of quasi-resonance controller H based on the control law APQR ；
Step S4, determining fundamental wave reference voltage according to a dynamic equation:
wherein R is the equivalent resistance of the three-phase voltage source rectifier;
s5, generating PWM signals based on the fundamental wave reference voltage and driving switching devices of the corresponding voltage source rectifiers to act;
in step S2, the reference current i αr I βr Two-phase voltages e designed to correspond to the respective axial directions α E β The proportionality coefficient k in the proportionality relationship is designed to: voltage u for said direct current d With the expected output voltage u of the direct current dr The regulated PI controller output, expressed as:
k＝k dp +k di ∫(u dr -u d )
wherein k is dp And k di Respectively representing the proportional and integral gains of the direct-current voltage control loop;
in step S3, the proportional quasi-resonant controller is:
H APQR ＝k id +k qr H d (z)
wherein k is id And k qr Respectively representing the proportion and quasi-resonant gain of the controller, H d (z) is an adaptive quasi-resonant control law H a (s) discretized values.
2. The method for controlling the current of a voltage source rectifier of a variable frequency system according to claim 1, wherein: in step S1, the CLARKE transformation is applied to convert the current dynamic equation in the three-phase stationary coordinate system into the current dynamic equation in the two-phase stationary coordinate system.
3. The method for controlling the current of a voltage source rectifier of a variable frequency system according to claim 1, wherein: in step S4, a sine wave adjustment method is adopted to generate a PWM signal, and the corresponding voltage modulation signal is:
wherein u is d Is the voltage of direct current.
4. The method for controlling the current of a voltage source rectifier of a variable frequency system according to claim 1, wherein: in step S5, a space vector modulation method is used to generate a PWM signal.
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WO2018140824A1 (en) * 2017-01-27 2018-08-02 Murata Manufacturing Co., Ltd. 120-hz ripple reduction with pir controller for llc converter
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