CN112366950A - Electrodeless control series/parallel bidirectional power circuit and control method thereof - Google Patents

Electrodeless control series/parallel bidirectional power circuit and control method thereof Download PDF

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Publication number
CN112366950A
CN112366950A CN202011205099.0A CN202011205099A CN112366950A CN 112366950 A CN112366950 A CN 112366950A CN 202011205099 A CN202011205099 A CN 202011205099A CN 112366950 A CN112366950 A CN 112366950A
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China
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circuit
direct current
switch
switch circuit
current conversion
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CN202011205099.0A
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Chinese (zh)
Inventor
岳秀梅
李奎
马琳
郑真
李情
汪洪亮
罗安
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Hunan University
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Hunan University
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Priority to CN202011205099.0A priority Critical patent/CN112366950A/en
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33584—Bidirectional converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/285—Single converters with a plurality of output stages connected in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
    • H02M1/0077—Plural converter units whose outputs are connected in series

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)

Abstract

The application discloses a stepless control serial/parallel bidirectional power circuit and a control method thereof. The power supply circuit comprises a first switch circuit, a second switch circuit, a first direct current conversion circuit (phase1) and a second direct current conversion circuit (phase2), and input sides of phase1 and phase2 are connected in parallel and output sides of the phase1 and the phase2 are connected in series or in parallel by controlling the first switch circuit, the second switch circuit and switch tubes in phase1 and phase2 to be connected or disconnected. The series/parallel bidirectional power supply topology can realize ultra-wide voltage gain, can be widely applied to occasions of wide-range voltage input and wide-range voltage output, and effectively solves the problem of gain limitation of topologies such as a traditional LLC resonant converter and the like. In addition, because phase1 and phase2 share the output side filter capacitor, series and parallel seamless switching can be realized, and the impact of the transient process on the load side is reduced.

Description

Electrodeless control series/parallel bidirectional power circuit and control method thereof
Technical Field
The application relates to the technical field of LLC resonant circuits, in particular to a stepless control serial/parallel bidirectional power circuit and a control method thereof.
Background
The DC/DC direct current converter is widely applied to the fields of new energy storage, direct current micro-grids, large-scale data centers, electric vehicle charging, LED lighting and the like. In the application field of energy unidirectional flow, such as a large-scale data center, the unidirectional DC/DC direct-current converter is widely applied due to simple structure and control, but due to high-speed development and application of new energy power generation, a direct-current micro-grid and the like, energy storage becomes an essential link, and the traditional unidirectional power supply cannot meet the requirement of energy bidirectional flow, so that the bidirectional DC/DC converter is becoming a mainstream converter applied and researched in the industry. For an LLC resonant converter in a direct Current converter, a primary side Zero Voltage Switching (ZVS) and a secondary side Zero Current Switching (ZCS) are realized, so that the element loss is greatly reduced, and the efficiency is very high. On the other hand, the realization of ZVS and ZCS is beneficial to further improving the switching frequency and reducing the volume of the magnetic element so as to realize the performance of high power density. Therefore, the LLC resonant converter has high efficiency and high power density performance with significant advantages compared to other DC/DC converters, and thus is becoming the mainstream converter in the field of DC/DC direct current converters.
For wide-range voltage input and output occasions, for the LLC resonant converter, to realize wide voltage gain means that the switching frequency fs variation range is large, and the ratio of the resonant inductance to the excitation inductance is large. The large change range of the switching frequency fs can cause the design difficulty of the magnetic element to be large, and in addition, if the switching frequency fs deviates from the resonant frequency fr to be too large, the performance of the converter can be reduced; the large ratio of the resonant inductance to the excitation inductance leads to an increase in reactive current, thereby increasing the loss of elements and reducing the converter efficiency.
However, in the prior art, the gain range can be widened to a certain extent by an optimization method of adding active switches on the input side and the output side, but the method cannot be applied to the occasions with gain requirements more than 3 times, and the method is not beneficial to multi-module capacity expansion. For the optimization strategy of switching in frequency modulation, phase shift and full-bridge/half-bridge working modes, the phase shift can cause the loss of certain ZVS performance, the efficiency of the converter is reduced, in addition, the smooth transition can not be realized in the transient switching process of the full-bridge half-bridge, and the impact on the load and the resonant cavity is large.
Disclosure of Invention
The embodiment of the application provides a stepless control serial/parallel bidirectional power circuit and a control method thereof, which are used for widening a gain range and reducing transient impact on a load.
In a first aspect, an embodiment of the present application provides an electrodeless control serial/parallel bidirectional power circuit, including:
the first switching circuit, the first direct current conversion circuit, the second direct current conversion circuit and the second switching circuit; the electrodeless control serial/parallel bidirectional power circuit realizes that the input sides of the first direct current conversion circuit and the second direct current conversion circuit are connected in parallel, and the output sides are connected in parallel or connected in series under the control of a control signal;
the first switch circuit comprises a first end, a second end, a third end and a fourth end, the third end of the first switch circuit and the fourth end of the first switch circuit are respectively connected with a positive pole and a negative pole of an external power supply or a load, and at least three working modes are realized under the control of a control signal: among the four terminals, the connection between the first terminal of the first switch circuit and the third terminal of the first switch circuit and the connection between the second terminal of the first switch circuit and the fourth terminal of the first switch circuit are conducted, and the connection between the first terminal of the first switch circuit and the second terminal of the first switch circuit is disconnected at the same time; among the four terminals, only the connection between the first end of the first switch circuit and the second end of the first switch circuit is conducted, and the connection between the other end and the end is disconnected; in the four terminals, all the terminals are disconnected;
the first direct current conversion circuit is used for converting a first direct current into a second direct current through high frequency conversion, and comprises: the first direct current conversion first end is connected with the third end of the first switch circuit, and the first direct current conversion second end is connected with the second end of the first switch circuit;
the second dc conversion circuit is configured to convert the first dc power into the desired second dc power through high frequency conversion, and includes: a second direct current conversion first end, a second direct current conversion second end, a second direct current conversion third end, and a second direct current conversion fourth end, wherein the second direct current conversion first end is connected with the first end of the first switch circuit, and the second direct current conversion second end is connected with the fourth end of the first switch circuit;
the second switch circuit comprises a first end, a second end, a third end and a fourth end, the third end of the second switch circuit and the fourth end of the second switch circuit are respectively connected with a load or a positive electrode and a negative electrode of an external power supply, and at least three working modes are provided under the control of a control signal: among the four terminals, the connection between the first end of the second switch circuit and the third end of the second switch circuit and the connection between the second end of the second switch circuit and the fourth end of the second switch circuit are conducted, and the connection between the first end and the second end of the second switch circuit is disconnected at the same time; among the four terminals, only the connection between the first end of the second switch circuit and the second end of the second switch circuit is conducted, and the connection between the other end and the end is disconnected; in the four terminals, all the terminals are disconnected;
the first direct current conversion third end is connected with the third end of the second switch circuit, and the first direct current conversion fourth end is connected with the second end of the second switch circuit;
the second direct current conversion third end is connected with the first end of the second switch circuit, and the second direct current conversion fourth end is connected with the fourth end of the second switch circuit.
In a second aspect, an embodiment of the present application provides a method for controlling a stepless control serial/parallel bidirectional power circuit, where the stepless control serial/parallel bidirectional power circuit is a circuit according to the first aspect, and the method includes:
under the control of a control signal, controlling to conduct the connection between the first end and the third end of the first switch circuit and the connection between the second end and the fourth end of the first switch circuit, and disconnecting the connection between the first end of the first switch circuit and the second end of the first switch circuit; controlling to conduct the connection between the first end of the second switch circuit and the third end of the second switch circuit and the connection between the second end of the second switch circuit and the fourth end of the second switch circuit, and disconnecting the connection between the first end of the second switch circuit and the second end of the second switch circuit, so that the first direct current conversion circuit and the second direct current conversion circuit are connected in parallel for output; or
Under the control of a control signal, controlling to conduct the connection between the first end of the first switch circuit and the third end of the first switch circuit and the connection between the second end of the first switch circuit and the fourth end of the first switch circuit, and to disconnect the connection between the first end of the first switch circuit and the second end of the first switch circuit; and controlling to only conduct the connection between the first end of the second switch circuit and the second end of the second switch circuit, and to disconnect the other ends and the ends of the second switch circuit, so that the first direct current conversion circuit and the second direct current conversion circuit are connected in series for output.
In the above embodiments of the present application, parallel input by the first dc conversion circuit (abbreviated as phase1) and the second dc conversion circuit (abbreviated as phase2) and parallel or serial output of phase1 and phase2 can be realized by controlling the first switch circuit and the second switch circuit. The series/parallel bidirectional power supply topology can realize ultra-wide voltage gain, can be widely applied to occasions of wide-range voltage input and wide-range voltage output, and effectively solves the problem of gain limitation of topologies such as a traditional LLC resonant converter and the like. In addition, because phase1 and phase2 share the output side filter capacitor, series and parallel seamless switching can be realized, and the impact of the transient process on the load side is reduced.
Drawings
In order to more clearly illustrate the embodiments of the present application or the technical solutions in the prior art, the drawings used in the description of the embodiments or the prior art will be briefly described below, it is obvious that the drawings in the following description are only some embodiments of the present application, and for those skilled in the art, other drawings can be obtained according to the drawings without creative efforts.
Fig. 1 is one of schematic diagrams of an electrodeless control series/parallel bidirectional power circuit provided in an embodiment of the present application;
fig. 2 is a second schematic diagram of a stepless control serial/parallel bidirectional power circuit provided in the embodiment of the present application;
fig. 3 is a schematic structural diagram of a dc conversion circuit according to an embodiment of the present disclosure;
fig. 4 is a schematic structural diagram of a resonant unit according to an embodiment of the present disclosure;
fig. 5 is a second schematic structural diagram of a resonant unit according to an embodiment of the present application;
fig. 6 is a third schematic structural diagram of a resonant unit according to an embodiment of the present application;
fig. 7 to 11 are schematic diagrams of operation modes of the electrodeless control series/parallel bidirectional power circuit shown in fig. 2;
fig. 12 is a second schematic diagram of the electrodeless controlled series/parallel bidirectional power circuit according to the embodiment of the present application.
Detailed Description
In order to make the objects, technical solutions and advantages of the present application more apparent, the technical solutions of the present application will be described in detail below. It is to be understood that the embodiments described are only a few embodiments of the present application and not all embodiments. All other embodiments, which can be derived by a person skilled in the art from the examples given herein without making any creative effort, shall fall within the protection scope of the present application.
In order to improve the gain of the LLC resonant converter, embodiment 1 of the present application provides a stepless control series/parallel bidirectional power circuit.
Referring to fig. 1, a circuit shown in fig. 1 is used to illustrate an embodiment of a stepless control serial/parallel bidirectional power circuit provided in the present application.
As shown, the electrodeless control series/parallel bidirectional power circuit may include: a first switch circuit 101, a first dc conversion circuit 102 (phase1 for short), a second dc conversion circuit 103 (phase2 for short), and a second switch circuit 104.
The stepless control series/parallel bidirectional power supply circuit can realize the parallel connection of the phase1 and the input side of the phase2, and the parallel connection or the series connection of the output side under the control of the control signal to the first switch circuit and the second switch circuit.
Specifically, the first switch circuit 101 includes a first terminal, a second terminal, a third terminal and a fourth terminal, and the third terminal and the fourth terminal of the first switch circuit are respectively connected to a first positive electrode and a first negative electrode (V1, which may be an external power source or a load). Under the control of the control signal, the first switch circuit has at least three working modes: 1) among the four terminals, the connection between the first end of the first switch circuit and the third end of the first switch circuit is conducted, the connection between the second end of the first switch circuit and the fourth end of the first switch circuit is conducted, and the connection between the first end of the first switch circuit and the second end of the first switch circuit is disconnected at the same time; 2) among the four terminals, only the connection between the first terminal of the first switch circuit and the second terminal of the first switch circuit is conducted, and the connection between the other terminal and the terminal is disconnected; 3) of the four terminals, all terminals are disconnected from each other.
The second switch circuit 104 includes a first terminal, a second terminal, a third terminal and a fourth terminal, wherein the third terminal and the fourth terminal of the second switch circuit are respectively connected to a second positive electrode and a negative electrode (V2, which may be a load or an external power source). Under the control of the control signal, the second switch circuit has at least three working modes: 1) among the four terminals, the connection between the first end of the second switch circuit and the third end of the second switch circuit is conducted, the connection between the second end of the second switch circuit and the fourth end of the second switch circuit is conducted, and the connection between the first end and the second end of the second switch circuit is disconnected at the same time; 2) among the four terminals, only the connection between the first end of the second switch circuit and the second end of the second switch circuit is conducted, and the connection between the other end and the end is disconnected; 3) of the four terminals, all terminals are disconnected from each other.
phase1 is used to convert the first dc power through high frequency conversion to the desired second dc power, and phase1 also includes four terminals: the first DC conversion device comprises a first DC conversion first end, a first DC conversion second end, a first DC conversion third end and a first DC conversion fourth end. The first dc conversion first terminal is connected to the third terminal of the first switch circuit 101, the first dc conversion second terminal is connected to the second terminal of the first switch circuit 101, the first dc conversion third terminal is connected to the third terminal of the second switch circuit 104, and the first dc conversion fourth terminal is connected to the second terminal of the second switch circuit 104.
Phase2 is used to convert the first dc power into the desired second dc power through high frequency conversion, and Phase2 also includes four terminals: the first direct current conversion terminal comprises a first direct current conversion first end, a first direct current conversion second end, a first direct current conversion third end and a first direct current conversion fourth end. The first end of the second dc conversion is connected to the first end of the first switch circuit 101, the second end of the second dc conversion is connected to the fourth end of the first switch circuit 101, the third end of the second dc conversion is connected to the first end of the second switch circuit 104, and the fourth end of the second dc conversion is connected to the fourth end of the second switch circuit 104.
In one possible implementation, the first switch circuit 101 may include a first switch transistor T11, a second switch transistor T12, and a third switch transistor T13 connected in series in sequence, as shown in fig. 2. The first switch tube T11 is connected to the first positive electrode, and the third switch tube T13 is connected to the first negative electrode. A common connection end of the first switch tube T11 and the second switch tube T12 is a first end of the first switch circuit 101, a common connection end of the second switch tube T12 and the third switch tube T13 is a second end of the first switch circuit 101, a connection end of the first switch tube T11 and the first positive electrode is a third end of the first switch circuit 101, and a connection end of the third switch tube T13 and the first negative electrode is a fourth end of the first switch circuit 101.
Similarly, the second switch circuit 104 also includes a fourth switch transistor T21, a fifth switch transistor T22, and a sixth switch transistor T23 connected in series. The fourth switching tube T21 is connected to the second positive electrode, and the sixth switching tube T23 is connected to the second negative electrode. The common connection end of the fourth switching tube T21 and the fifth switching tube T22 is the first end of the second switching circuit 104, the common connection end of the fifth switching tube T22 and the sixth switching tube T23 is the second end of the second switching circuit T23, the connection end of the fourth switching tube T21 and the second positive electrode is the third end of the second switching circuit 104, and the connection end of the sixth switching tube T23 and the second negative electrode is the fourth end of the second switching circuit 104.
In fig. 2, T11 to T13 and T21 to T23 are all NMOS transistors, and as shown in the figure, a drain of the first switching tube T11 is connected to the first positive electrode, a source of the first switching tube T11 is connected to a drain of the second switching tube T12, a source of the second switching tube T12 is connected to a drain of the third switching tube T13, and a source of the third switching tube T13 is connected to the first negative electrode; the drain of the fourth switching tube T21 is connected to the second positive electrode, the source of the fourth switching tube T21 is connected to the drain of the fifth switching tube T22, the source of the fifth switching tube T22 is connected to the drain of the sixth switching tube T23, and the source of the sixth switching tube T23 is connected to the second negative electrode. The on/off of the terminals of the first switch circuit 101 and the second switch circuit 104 can be realized by applying control signals to the gates of T11 to T13 and T21 to T23 to realize the on/off of T11 to T13 and T21 to T23. It should be understood that the switching tubes may be implemented by other controllable bidirectional elements besides NMOS tubes with built-in diodes, for example, the first switching tube T11, the third switching tube T13, the fourth switching tube T21 and the sixth switching tube T23 may also be replaced by IGBTs with anti-parallel diodes; this time is not exemplified. In order to realize bidirectional current flowing, the switch tubes in the application are connected with a diode in parallel in an opposite direction.
In some embodiments, the first switching circuit 101 may also be connected in parallel with the first capacitor C1; the second switching circuit 102 is connected in parallel with a second capacitor C2, as shown in fig. 2.
In one possible implementation, phase1 may include a first full-bridge circuit 1021, a first resonance unit 1022, and a second full-bridge circuit 1023, as shown in fig. 2. The first full-bridge circuit 1021 is connected to the second full-bridge circuit 1023 through the first resonance unit 1022. Two input ends of the first full-bridge circuit 1021 are respectively used as a first direct current conversion first end and a first direct current conversion second end to be connected with the first switch circuit 101; two output terminals of the second full bridge 1023 are connected to the second switch circuit 102 as a first dc conversion third terminal and a first dc conversion fourth terminal, respectively.
Similarly, phase2 may include a third full-bridge circuit 1031, a second resonant cell 1032, and a fourth full-bridge circuit 1033. Wherein the third full-bridge circuit 1031 is connected to the fourth full-bridge circuit 1033 via the second resonance unit 1032. Two input ends of the third full-bridge circuit 1031 are respectively used as a first end of a second direct current conversion, and a second end of the second direct current conversion is connected with the first switch circuit 101; two output terminals of the fourth full bridge circuit 1033 are respectively used as a second dc converting third terminal and a second dc converting fourth terminal to be connected to the second switch circuit 102.
It should be understood that the embodiments of the present application provide bidirectional power supplies, and therefore, the input and output terminals of the full bridge circuits can be switched with each other. For example, when the first positive and negative electrodes V1 are power sources and the second positive and negative electrodes (V2) are loads, the first dc converter first terminal and the second terminal are input terminals of the first full-bridge circuit; when the second positive and negative electrodes (V2) are power sources and the first positive and negative electrodes (V1) are loads, the terminals of the first dc converter first end and the second end are not changed, but the two terminals are actually the output ends of the first full bridge circuit.
In the example shown in fig. 2, the first full-bridge circuit 1021, the second full-bridge circuit 1023, the third full-bridge circuit 1031, and the fourth full-bridge circuit 1033 are each composed of 4 switching tubes. As shown in the first full-bridge circuit 1021 in fig. 2, the drain of the switch tube Q11 is connected to the drain of the switch tube Q13, and is connected to the first positive electrode as the first end of phase1, the source of the switch tube Q11 is connected to the drain of the switch tube Q12, the source of the switch tube Q13 is connected to the drain of the switch tube Q14, the source of the switch tube Q12 and the source of the switch tube Q14 are connected to the second end of the phase1 and are connected to the second end of the first switch circuit 101, and the source of the switch tube Q11 and the source of the switch tube Q13 are respectively connected to the first resonant unit as the two output ends of the first full-bridge circuit 1021. The connection relationship of the second full-bridge circuit 1023, the third full-bridge circuit 1031 and the fourth full-bridge circuit 1033 is similar to that of the first full-bridge circuit 1021, and is not repeated.
The first full-bridge circuit 1021, the second full-bridge circuit 1023, the third full-bridge circuit 1031 and the fourth full-bridge circuit 1033 shown in fig. 2 are all composed of 4 NMOS transistors, it should be understood that this is only one specific embodiment of the present application, and when the present application is specifically implemented, other controllable bidirectional devices may be adopted to form the full-bridge circuit, for example, IGBTs may be adopted partially or completely. Further, in order to realize bidirectional current flowing, the switching tubes in the application are connected with a diode in parallel in an opposite direction.
In another possible implementation, phase1 may include a first half-bridge circuit, a first resonant cell, and a first full-bridge circuit, and phase2 may include a second half-bridge circuit, a second resonant cell, and a second full-bridge circuit, as shown in fig. 3. The first half-bridge circuit and the second half-bridge circuit may be respectively formed by two switching tubes.
Similarly, the first full-bridge circuit 1021, the second full-bridge circuit 1023, the third full-bridge circuit 1031, and the fourth full-bridge circuit 1033 shown in fig. 2 may be partially or entirely replaced by a half-bridge circuit composed of two switching tubes. However, whether a full-bridge circuit or a half-bridge circuit is adopted, the energy can flow in two directions because the switch tubes can flow in two directions.
In the specific embodiment shown in fig. 2, the first resonance unit 1022 and the second resonance circuit 1032 may respectively include a resonance capacitor, a resonance inductor, an excitation inductor, and a high-frequency isolation transformer.
Specifically, the first resonance unit 1022 may include a first resonance capacitor Cr1, a first resonance inductor Lr1, a first excitation inductor Lm1, and a first high-frequency isolation transformer T1. A first end of the first resonant capacitor Cr1 and a first end of the first resonant inductor Lr1 are connected to the first full bridge circuit 1021 (or the first half bridge circuit) as an input end of the first resonant unit 1022, a second end of the first resonant capacitor Cr1 is connected to a second end of the first resonant inductor Lr1 through the first exciting inductor Lm1, the first high-frequency isolation transformer T1 is connected in parallel to the first exciting inductor Lm1, and an output end of the first high-frequency isolation transformer T1 is connected to the second full bridge circuit 1023 as an output end of the first resonant unit 1022.
Similarly, the second resonance unit 1032 may include a second resonance capacitor Cr2, a second resonance inductor Lr2, a second excitation inductor Lm2, and a second high-frequency isolation transformer T2. A first end of the second resonant capacitor Cr2 and a first end of the second resonant inductor Lr2 are connected to the third full bridge circuit 1031 (or the second half bridge circuit) as an input terminal of the second resonant unit 1032, a second end of the second resonant capacitor Cr2 is connected to a second end of the second resonant inductor Lr2 through the second magnetizing inductor Lm2, the second high-frequency isolation transformer T2 is connected in parallel to the second magnetizing inductor Lm2, and an output terminal of the second high-frequency isolation transformer T2 is connected to the fourth full bridge circuit 1033 as an output terminal of the second resonant unit 1032.
In order to meet the conversion requirements of forward gain and reverse gain, a resonant capacitor can be added on the secondary side of the high-frequency isolation transformer in the resonant circuit, so that the reverse voltage gain of the bidirectional power supply circuit can be higher than 1, and the application range of the bidirectional power supply circuit is effectively widened.
Specifically, one resonance capacitor may be added to each of the first resonance unit 1022 and the second resonance unit 1032. As shown in fig. 4, a third resonant capacitor Cr3 is added to the first resonant circuit 23, a first terminal of the third resonant capacitor Cr3 is connected to a first output terminal of the first high-frequency isolation transformer T1, and a second terminal of the third resonant capacitor Cr3 and a second output terminal of the first high-frequency isolation transformer T1 serve as output terminals of the first resonant circuit 23. Similarly, a fourth resonant capacitor Cr4 is added to the second resonant circuit 33, and as shown in fig. 4, a first terminal of the fourth resonant capacitor Cr4 is connected to the first output terminal of the second high-frequency isolation transformer T2, and a second terminal of the fourth resonant capacitor Cr4 and the second output terminal of the second high-frequency isolation transformer T2 serve as output terminals of the second resonant circuit 33.
Further, in order to make the forward and reverse characteristics of the bidirectional power supply circuit consistent, both having the operating characteristics of LLC, a resonant inductor may be added to each of the first resonant unit 1022 and the second resonant unit 1032. Specifically, a third resonant inductor Lr3 may be added to the first resonant unit 1022, as shown in fig. 5, a first end of the third resonant inductor Lr3 is connected to the second output terminal of the first high-frequency isolation transformer T1, and a second end of the third resonant capacitor Cr3 and a second end of the third resonant inductor Lr3 serve as output terminals of the first resonant unit 1022. Correspondingly, a fourth resonant inductor Lr4 may be added to the second resonant unit 1032, as shown in fig. 5, a first end of the fourth resonant inductor Lr4 is connected to the second output terminal of the second high-frequency isolation transformer T2, and a second end of the fourth resonant capacitor Cr4 and a second end of the fourth resonant inductor Lr4 serve as output terminals of the second resonant unit 1032.
Alternatively, the first resonance unit 1022 and the second resonance unit 1032 may also be as shown in fig. 6, and the first resonance unit 1022 may include a first resonance capacitor Cr1, a first resonance inductor Lr1, a first high-frequency isolation transformer T1, and a capacitor Cp 1. Two ends of the capacitor Cp1 are respectively connected with the second end of the first resonant capacitor Cr1 and the second end of the first resonant inductor Lr 1. The second resonance unit 1032 may include a second resonance capacitor Cr2, a second resonance inductor Lr2, a second high frequency isolation transformer T2, and a capacitor Cp 2. Two ends of the capacitor Cp2 are respectively connected with the second end of the second resonant capacitor Cr2 and the second end of the second resonant inductor Lr 2.
Although the first dc conversion circuit 102 and the second dc conversion circuit 103 each include a resonant unit and perform dc conversion by a resonant method in the above example, this is not limited in the embodiments of the present application, and dc conversion may be implemented by other circuit methods.
The present embodiment provides a bidirectional power circuit, so that V1 shown in fig. 2 may represent a power supply, V2 represents a load, at this time, the first full-bridge circuit 1021 and the third full-bridge circuit 1031 implement an inverting function, and the second full-bridge circuit 1023 and the fourth full-bridge circuit 1033 implement a rectifying function; alternatively, V1 may represent a load and V2 a power supply, at which time the first full-bridge circuit 1021 and the third full-bridge circuit 1031 perform a rectifying function and the second full-bridge circuit 1023 and the fourth full-bridge circuit 1033 perform an inverting function. The principle of the two cases is similar, and the working module of the electrodeless control serial/parallel bidirectional power circuit is exemplified below by taking V1 as a power supply and V2 as a load.
With the parallel inputs and parallel outputs of phase1 and phase2, the circuit shown in fig. 2 has 4 modes of operation, and periodically operates in each of these 4 modes.
Working mode 1 (as shown in FIG. 7)
The second switch tube T12 in the first switch circuit 101 is turned off, the first switch tube T11 and the third switch tube T13 are turned on, the primary sides of phase1 and phase2 are input in parallel, the switch tube Q11 and the switch tube Q14 in the first full-bridge circuit 1021 are turned on, the switch tube Q31 and the switch tube Q34 in the third full-bridge circuit 1023 are turned on, and the directions of currents in the first resonance unit 1022 and the second resonance unit 1032 are as shown by the arrow directions in fig. 7. At this time, Cr1 resonates with Lr1, and Cr2 resonates with Lr 2. The switch tube 21 and the switch tube 24 in the second full-bridge circuit 1023 are controlled to be conducted, the switch tube Q41 and the switch tube Q44 in the fourth full-bridge circuit 1033 are controlled to be conducted, phase1 and phase2 outputs are connected in parallel, electric energy is transmitted to the load V2, and an output filter capacitor (a second capacitor C2) is shared.
Working mode 2 (as shown in figure 8)
The second switch tube T12 in the first switch circuit 101 is turned off, the first switch tube T11 and the third switch tube T13 are turned on, the primary sides of phase1 and phase2 are input in parallel, the switch tube Q11 and the switch tube Q14 in the first full-bridge circuit 1021 are turned on, the switch tube Q31 and the switch tube Q34 in the third full-bridge circuit 1023 are turned on, and the directions of currents in the first resonance unit 1022 and the second resonance unit 1032 are as shown by the arrow directions in fig. 8. Cr1 resonates with Lr1 and Lm1 in series, Cr2 resonates with Lr2 and Lm2 in series, and the three-device resonant state is achieved. When the exciting current is equal to the resonant current, no energy is transmitted to the secondary side from the first resonant unit 1022 and the second resonant unit 1032, and the load V2 is powered by the output filter capacitor (the second capacitor C2).
Working mode 3 (as shown in FIG. 9)
The second switch tube T12 in the first switch circuit 101 is turned off, the first switch tube T11 and the third switch tube T13 are turned on, the primary sides of phase1 and phase2 are input in parallel, the switch tube Q12 and the switch tube Q13 in the first full-bridge circuit 1021 are turned on, the switch tube Q32 and the switch tube Q33 in the third full-bridge circuit 1023 are turned on, and the directions of currents in the first resonance unit 1022 and the second resonance unit 1032 are as shown by the arrow directions in fig. 9. At this time, Cr1 resonates with Lr1, and Cr2 resonates with Lr 2. The switch tube Q22 and the switch tube Q23 in the second full-bridge circuit 1023 are controlled to be conducted, the switch tube Q42 and the switch tube Q43 in the fourth full-bridge circuit 1033 are controlled to be conducted, phase1 and phase2 outputs are connected in parallel, electric energy is transmitted to a load V2, and an output filter capacitor (a second capacitor C2) is shared.
Working mode 4 (as shown in figure 10)
The second switch tube T12 in the first switch circuit 101 is turned off, the first switch tube T11 and the third switch tube T13 are turned on, the primary sides of phase1 and phase2 are input in parallel, the switch tube Q12 and the switch tube Q13 in the first full-bridge circuit 1021 are turned on, the switch tube Q32 and the switch tube Q33 in the third full-bridge circuit 1023 are turned on, and the directions of currents in the first resonance unit 1022 and the second resonance unit 1032 are as shown by the arrow directions in fig. 10. Cr1 resonates with Lr1 and Lm1 in series, Cr2 resonates with Lr2 and Lm2 in series, and the three-device resonant state is achieved. When the exciting current is equal to the resonant current, no energy is transmitted to the secondary side from the first resonant unit 1022 and the second resonant unit 1032, and the load V2 is powered by the output filter capacitor (the second capacitor C2).
The 4 modes are all phase1 and phase2 parallel output structures. When the output voltage varies within a wide range, the output can be switched from the parallel configuration to the series configuration or from the series output configuration to the parallel output configuration.
The following description will be made in detail with reference to the operation mode 1 as an example, when switching from the parallel output to the series output. As shown in fig. 11, when the parallel output is switched to the series output, the second switching tube T12 in the first switching circuit 101, the fourth switching tube T21 in the second switching circuit 104, and the sixth switching tube T23 are controlled to be turned off, and the first switching tube T11, the third switching tube T13, and the fifth switching tube T22 are controlled to be turned on, at which time phase1 and phase2 are output in series. The second capacitor C2 is the total filter capacitor after the series output. Since the capacitor has the characteristic that the voltage cannot change suddenly, the voltage on the second capacitor C2 does not change suddenly when the outputs of phase1 and phase2 are switched from the parallel structure to the series structure, so that seamless switching can be realized without causing impact on the load.
From the above analysis of the 5 modalities (fig. 7 to 11) it can be concluded that: the on/off of the fourth switching tube T21, the fifth switching tube T22 and the sixth switching tube T23 in the second switching circuit 104 is controlled to realize that the outputs of phase1 and phase2 are connected in parallel or in series, which is not related to what form of dc conversion circuit is specifically adopted by phase1 and phase 2. Therefore, phase1 and phase2 in the embodiment of the present application may also use other dc conversion circuits to implement dc-dc conversion, such as a Buck circuit, a Boost circuit, and the like, and the present application does not limit the specific circuit forms of phase1 and phase 2.
In some embodiments, in order to avoid the phenomenon that the currents may not be matched when switching from the parallel output to the series output, the unbalanced current can be released and absorbed by adding a capacitor. For example, in one embodiment shown in fig. 12, a third capacitor C11 may be added, and both ends of the third capacitor C11 are respectively connected to the input terminals of the first full-bridge circuit 1021; a fourth capacitor C12 is added, and two ends of the fourth capacitor are respectively connected with the output end of the second full bridge 1023; a fifth capacitor C21 is added, and two ends of the fifth capacitor are respectively connected with the input end of the third full-bridge circuit 1031; a sixth capacitor C22 is added, and two ends of the sixth capacitor are respectively connected with the output end of the fourth full bridge circuit 1033, so as to release and absorb the unbalanced current.
In the above embodiments of the present application, when the first positive electrode and the first negative electrode are positive and negative electrodes of the power supply, and the second positive electrode and the second negative electrode are positive and negative electrodes of the load, parallel input of the first dc conversion circuit (phase1 for short) and the second dc conversion circuit (phase2 for short) and parallel or serial output of the phase1 and the phase2 can be realized by controlling the first switch circuit and the second switch circuit. The circuit may further include a second positive electrode and a second negative electrode as positive and negative electrodes of the power supply, and a first positive electrode and a first negative electrode as positive and negative electrodes of the load. The series/parallel bidirectional power supply topology can realize ultra-wide voltage gain, can be widely applied to occasions of wide-range voltage input and wide-range voltage output, and effectively solves the problem of gain limitation of topologies such as a traditional LLC resonant converter and the like. In addition, because phase1 and phase2 share the output side filter capacitor, series and parallel seamless switching can be realized, and the impact of the transient process on the load side is reduced.
Based on the same technical concept, the embodiment of the present application further provides a control method for a stepless control serial/parallel bidirectional power circuit, which can be applied to the stepless control serial/parallel bidirectional power circuit in the foregoing embodiment, and the method can include:
step 11, under the control of the control signal, controlling to conduct the connection between the first end and the third end of the first switch circuit, conduct the connection between the second end and the fourth end of the first switch circuit, and disconnect the connection between the first end and the second end of the first switch circuit; and controlling to conduct the connection between the first end and the third end of the second switch circuit, conduct the connection between the second end and the fourth end of the second switch circuit, and disconnect the connection between the first end and the second end of the second switch circuit, so that the first direct current conversion circuit and the second direct current conversion circuit are connected in parallel for output.
Step 12, under the control of the control signal, controlling to only conduct the connection between the first end and the second end of the first switch circuit, and disconnecting the other ends of the first switch circuit from the ends; and controlling to conduct the connection between the first end and the second end of the second switch circuit and disconnect the connection between the other ends and the ends of the second switch circuit, so that the first direct current conversion circuit and the second direct current conversion circuit are connected in series for output.
As mentioned above, the first switch circuit may include a first switch tube, a second switch tube, and a third switch tube connected in series, and the second switch circuit may include a fourth switch tube, a fifth switch tube, and a sixth switch tube connected in series. Correspondingly, when the step 11 is executed, the second switching tube and the fifth switching tube are controlled to be turned off, and the first, third, fourth and sixth switching tubes are controlled to be turned on, so that the parallel output of phase1 and phase2 is realized.
When the step 12 is executed, the second switching tube, the fourth switching tube and the sixth switching tube may be controlled to be turned off, and the first switching tube, the third switching tube and the fifth switching tube may be controlled to be turned on, so that phase1 and phase2 are output in series.
The execution sequence of the steps 11 and 12 is not limited in the embodiment of the present application.
It is understood that the same or similar parts in the above embodiments may be mutually referred to, and the same or similar parts in other embodiments may be referred to for the content which is not described in detail in some embodiments.
It should be noted that, in the description of the present application, the terms "first", "second", etc. are used for descriptive purposes only and are not to be construed as indicating or implying relative importance. Further, in the description of the present application, the meaning of "a plurality" means at least two unless otherwise specified.
Although embodiments of the present application have been shown and described above, it is understood that the above embodiments are exemplary and should not be construed as limiting the present application, and that variations, modifications, substitutions and alterations may be made to the above embodiments by those of ordinary skill in the art within the scope of the present application.

Claims (14)

1. An electrodeless controlled series/parallel bidirectional power supply circuit, comprising: the first switching circuit, the first direct current conversion circuit, the second direct current conversion circuit and the second switching circuit; the electrodeless control serial/parallel bidirectional power circuit realizes that the input sides of the first direct current conversion circuit and the second direct current conversion circuit are connected in parallel, and the output sides are connected in parallel or connected in series under the control of a control signal;
the first switch circuit comprises a first end, a second end, a third end and a fourth end, the third end of the first switch circuit and the fourth end of the first switch circuit are respectively connected with a positive pole and a negative pole of an external power supply or a load, and at least three working modes are realized under the control of a control signal: among the four terminals, the connection between the first terminal of the first switch circuit and the third terminal of the first switch circuit and the connection between the second terminal of the first switch circuit and the fourth terminal of the first switch circuit are conducted, and the connection between the first terminal of the first switch circuit and the second terminal of the first switch circuit is disconnected at the same time; among the four terminals, only the connection between the first end of the first switch circuit and the second end of the first switch circuit is conducted, and the connection between the other end and the end is disconnected; in the four terminals, all the terminals are disconnected;
the first direct current conversion circuit is used for converting a first direct current into a second direct current through high frequency conversion, and comprises: the first direct current conversion first end is connected with the third end of the first switch circuit, and the first direct current conversion second end is connected with the second end of the first switch circuit;
the second dc conversion circuit is configured to convert the first dc power into the desired second dc power through high frequency conversion, and includes: a second direct current conversion first end, a second direct current conversion second end, a second direct current conversion third end, and a second direct current conversion fourth end, wherein the second direct current conversion first end is connected with the first end of the first switch circuit, and the second direct current conversion second end is connected with the fourth end of the first switch circuit;
the second switch circuit comprises a first end, a second end, a third end and a fourth end, the third end of the second switch circuit and the fourth end of the second switch circuit are respectively connected with a load or a positive electrode and a negative electrode of an external power supply, and at least three working modes are provided under the control of a control signal: among the four terminals, the connection between the first end of the second switch circuit and the third end of the second switch circuit and the connection between the second end of the second switch circuit and the fourth end of the second switch circuit are conducted, and the connection between the first end and the second end of the second switch circuit is disconnected at the same time; among the four terminals, only the connection between the first end of the second switch circuit and the second end of the second switch circuit is conducted, and the connection between the other end and the end is disconnected; in the four terminals, all the terminals are disconnected;
the first direct current conversion third end is connected with the third end of the second switch circuit, and the first direct current conversion fourth end is connected with the second end of the second switch circuit;
the second direct current conversion third end is connected with the first end of the second switch circuit, and the second direct current conversion fourth end is connected with the fourth end of the second switch circuit.
2. The circuit of claim 1, wherein the first switch circuit comprises a first switch tube, a second switch tube and a third switch tube connected in series in sequence, the first switch tube is connected with the positive pole of the external power supply or load, and the third switch tube is connected with the negative pole of the external power supply or load;
a common connection end of the first switching tube and the second switching tube is a first end of the first switching circuit, a common connection end of the second switching tube and the third switching tube is a second end of the first switching circuit, a connection end of the first switching tube and an external power supply or a load anode is a third end of the first switching circuit, and a connection end of the third switching tube and the external power supply or the load cathode is a fourth end of the first switching circuit; and/or
The second switch circuit comprises a fourth switch tube, a fifth switch tube and a sixth switch tube which are sequentially connected in series, the fourth switch tube is connected with the positive pole of the load or the external power supply, and the sixth switch tube is connected with the negative pole of the load or the external power supply;
the common connection end of the fourth switching tube and the fifth switching tube is the first end of the second switching circuit, the common connection end of the fifth switching tube and the sixth switching tube is the second end of the second switching circuit, the fourth switching tube and the connection end of the load or the anode of the external power supply are the third end of the second switching circuit, and the connection end of the sixth switching tube and the cathode of the load or the external power supply is the fourth end of the second switching circuit.
3. The circuit of claim 2, wherein the first switch tube, the second switch tube and the third switch tube are all NMOS tubes; the drain electrode of the first switching tube is connected with the positive electrode of the external power supply or the load, the source electrode of the first switching tube is connected with the drain electrode of the second switching tube, the source electrode of the second switching tube is connected with the drain electrode of the third switching tube, and the source electrode of the third switching tube is connected with the negative electrode of the external power supply or the load; and/or
The fourth switching tube, the fifth switching tube and the sixth switching tube are NMOS tubes; the drain electrode of the fourth switching tube is connected with the positive electrode of the load or the external power supply, the source electrode of the fourth switching tube is connected with the drain electrode of the fifth switching tube, the source electrode of the fifth switching tube is connected with the drain electrode of the sixth switching tube, and the source electrode of the sixth switching tube is connected with the negative electrode of the load or the external power supply.
4. The circuit of claim 1, wherein the first DC conversion circuit comprises a first full bridge circuit, a second full bridge circuit and a first resonance unit, and the first full bridge circuit is connected with the second full bridge circuit through the first resonance unit;
two input ends of the first full-bridge circuit are respectively used as a first direct current conversion first end and a first direct current conversion second end, and two output ends of the second full-bridge circuit are respectively used as a first direct current conversion third end and a first direct current conversion fourth end; and/or
The second direct current conversion circuit comprises a third full-bridge circuit, a fourth full-bridge circuit and a second resonance unit, and the third full-bridge circuit is connected with the fourth full-bridge circuit through the second resonance unit;
two input ends of the third full-bridge circuit are respectively used as the first end of the second direct current conversion and the second end of the second direct current conversion, and two output ends of the fourth full-bridge circuit are respectively used as the third end of the second direct current conversion and the fourth end of the second direct current conversion.
5. The circuit of claim 4, wherein the first full-bridge circuit and the second full-bridge circuit are respectively replaced by a first half-bridge circuit and a second half-bridge circuit; and/or
And the third full-bridge circuit and the fourth full-bridge circuit are respectively replaced by a third half-bridge circuit and a fourth half-bridge circuit.
6. The circuit of claim 4, wherein the first full-bridge circuit and the second full-bridge circuit respectively comprise 4 switching tubes; and/or
The third full-bridge circuit and the fourth full-bridge circuit respectively comprise 4 switching tubes.
7. The circuit of claim 5, wherein the first half-bridge circuit and the second half-bridge circuit respectively comprise 2 switching tubes; and/or
The third half-bridge circuit and the fourth half-bridge circuit respectively comprise 2 switching tubes.
8. The circuit according to claim 4 or 5, wherein the first resonance unit comprises a first resonance capacitor, a first resonance inductor and a first high-frequency isolation transformer;
the first end of the first resonant capacitor and the first end of the first resonant inductor are respectively connected with two output ends/input ends of the first full-bridge circuit, the second end of the first resonant capacitor and the second end of the first resonant inductor are connected with the first side of the first high-frequency isolation transformer, and the second side of the first high-frequency isolation transformer is connected with two input ends/output ends of the second full-bridge circuit;
the second resonance unit comprises a second resonance capacitor, a second resonance inductor and a second high-frequency isolation transformer;
the first end of the second resonance capacitor and the first end of the second resonance inductor are respectively connected with two output/input ends of the third full-bridge circuit, the second end of the second resonance capacitor and the second end of the second resonance inductor are connected with the first side of the second high-frequency isolation transformer, and the second side of the second high-frequency isolation transformer is connected with two input/output ends of the fourth full-bridge circuit.
9. The circuit of claim 8, wherein the first resonant cell further comprises a third resonant capacitor;
the first end of the third resonant capacitor is connected with the first end of the second side of the first high-frequency isolation transformer, and the second end of the third resonant capacitor is connected with the first input end/output end of the second full-bridge circuit;
the second resonance unit further comprises a fourth resonance capacitor;
and the first end of the fourth resonant capacitor is connected with the first end of the second side of the second high-frequency isolation transformer, and the second end of the fourth resonant capacitor is connected with the first input end/output end of the fourth full-bridge circuit.
10. The circuit of claim 9, further comprising: a third resonant inductor and a fourth resonant inductor;
the first end of the third resonant inductor is connected with the second end of the second side of the first high-frequency isolation transformer, and the second end of the third resonant inductor is connected with the second input end/output end of the second full-bridge circuit;
and the first end of the fourth resonant inductor is connected with the second end of the second side of the second high-frequency isolation transformer, and the second end of the fourth resonant inductor is connected with the second input/output end of the fourth full-bridge circuit.
11. The circuit of claim 8, wherein the first resonant cell further comprises a third resonant capacitor;
the first end of the third resonant capacitor is connected with the second end of the first resonant capacitor, and the second end of the third resonant capacitor is connected with the second end of the first resonant inductor;
the second resonance unit further comprises a fourth resonance capacitor;
and the first end of the fourth resonant capacitor is connected with the second end of the second resonant capacitor, and the second end of the fourth resonant capacitor is connected with the second end of the second resonant inductor.
12. The circuit of claim 1, wherein the first switching circuit is connected in parallel with a first capacitor;
the second switch circuit is connected in parallel with the second capacitor.
13. The circuit of any one of claims 1-12, further comprising: a third capacitor, a fourth capacitor, a fifth capacitor and a sixth capacitor;
two ends of the third capacitor are respectively connected with the first direct current conversion first end and the first direct current conversion second end;
two ends of the fourth capacitor are respectively connected with the first direct current conversion third end and the first direct current conversion fourth end;
two ends of the fifth capacitor are respectively connected with the second direct current conversion first end and the second direct current conversion second end;
and two ends of the sixth capacitor are respectively connected with the second direct current conversion third end and the second direct current conversion fourth end.
14. A control method for a stepless control series/parallel bidirectional power circuit, wherein the stepless control series/parallel bidirectional power circuit is the circuit as claimed in any one of claims 1 to 13, the method comprises:
under the control of a control signal, controlling to conduct the connection between the first end and the third end of the first switch circuit and the connection between the second end and the fourth end of the first switch circuit, and disconnecting the connection between the first end of the first switch circuit and the second end of the first switch circuit; controlling to conduct the connection between the first end of the second switch circuit and the third end of the second switch circuit and the connection between the second end of the second switch circuit and the fourth end of the second switch circuit, and disconnecting the connection between the first end of the second switch circuit and the second end of the second switch circuit, so that the first direct current conversion circuit and the second direct current conversion circuit are connected in parallel for output; or
Under the control of a control signal, controlling to conduct the connection between the first end of the first switch circuit and the third end of the first switch circuit and the connection between the second end of the first switch circuit and the fourth end of the first switch circuit, and to disconnect the connection between the first end of the first switch circuit and the second end of the first switch circuit; and controlling to only conduct the connection between the first end of the second switch circuit and the second end of the second switch circuit, and to disconnect the other ends and the ends of the second switch circuit, so that the first direct current conversion circuit and the second direct current conversion circuit are connected in series for output.
CN202011205099.0A 2020-11-02 2020-11-02 Electrodeless control series/parallel bidirectional power circuit and control method thereof Pending CN112366950A (en)

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Application publication date: 20210212