CN112134820A - Modulation method, modulator, demodulation method, demodulator, communication method and system - Google Patents

Modulation method, modulator, demodulation method, demodulator, communication method and system Download PDF

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CN112134820A
CN112134820A CN202010859652.6A CN202010859652A CN112134820A CN 112134820 A CN112134820 A CN 112134820A CN 202010859652 A CN202010859652 A CN 202010859652A CN 112134820 A CN112134820 A CN 112134820A
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signal
chirp
data
modulation
frequency
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CN112134820B (en
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唐晓柯
王于波
丘四海
胡毅
李德建
李铮
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State Grid Information and Telecommunication Co Ltd
Beijing Smartchip Microelectronics Technology Co Ltd
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State Grid Information and Telecommunication Co Ltd
Beijing Smartchip Microelectronics Technology Co Ltd
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2657—Carrier synchronisation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2662—Symbol synchronisation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2668—Details of algorithms
    • H04L27/2669—Details of algorithms characterised by the domain of operation
    • H04L27/2671—Time domain
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/38—Demodulator circuits; Receiver circuits
    • H04L27/3845—Demodulator circuits; Receiver circuits using non - coherent demodulation, i.e. not using a phase synchronous carrier
    • H04L27/3854—Demodulator circuits; Receiver circuits using non - coherent demodulation, i.e. not using a phase synchronous carrier using a non - coherent carrier, including systems with baseband correction for phase or frequency offset

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Abstract

The invention relates to the technical field of communication, and discloses a modulation method and a modulator based on a linear frequency modulation signal, a demodulation method and a demodulator based on the linear frequency modulation signal, a communication method and a communication system. The modulation method comprises the following steps: selecting M different phase data or M different frequency data, wherein M is 2LL is a positive integer, and the phase data or the frequency data are discretized phase data or frequency data of a chirp signal implanted with Doppler shift; mapping M-ary data modulation to the M different phase data or the M different frequency data; and generating and outputting M modulation signals corresponding to the M-ary data according to the M different phase data or the M different frequency data. The invention can realize modulation and demodulation of multi-system data in one pulse width, thereby greatly improving the transmission efficiency of communication data.

Description

Modulation method, modulator, demodulation method, demodulator, communication method and system
Technical Field
The invention relates to the technical field of communication, in particular to a modulation method and a modulator based on a linear frequency modulation signal, a demodulation method and a demodulator based on the linear frequency modulation signal, a communication method and a communication system.
Background
From the beginning of the mobile communication in the 90 s of the 19 th century to the present, the wireless communication technology has been rapidly developed, and the life of people has been greatly changed. Due to the dependence of wireless communication on frequency spectrum and the non-renewable characteristic of frequency spectrum resources, with the wide application of various wireless communications, each frequency band is more and more crowded, and the interference of communication is more and more serious. In order to achieve wireless communication with high capacity, high speed, high security, and high reliability, the ultra-wideband spread spectrum communication technology is an efficient solution to this problem. Spread spectrum communication technology performs communication using correlation of signals, transmits a spread spectrum code modulated signal at a transmitting end, and performs correlation processing on a received signal using a known spread spectrum code at a receiving end. Due to the autocorrelation characteristic of the spread spectrum code, the spread spectrum communication has strong anti-interference capability.
Wireless communication using Chirp signals (Chirp signals, which have natural spread spectrum characteristics) is an ultra wide band spread spectrum communication technique. The Chirp Spread Spectrum (CSS) technique is similar to the conventional Spread Spectrum techniques such as direct sequence Spread Spectrum and frequency hopping Spread Spectrum, and has the advantages of deep fading resistance, low transmission power and low interception probability, and has high processing gain at the receiving end. In addition, the CSS technology has the excellent performances of strong frequency deviation resistance, long transmission distance and easy spread spectrum. Two modulation modes based on the CSS technology include: binary Orthogonal Keying (BOK) and Direct Modulation (DM). The BOK represents different data by using different Chirp pulses (or a combination of a plurality of different pulses), such as 1 represented by a low-to-high linear frequency change (up-Chirp) and 0 represented by a high-to-low linear frequency change (down-Chirp). DM multiplies a Chirp signal by a signal modulated by other methods (such as Differential Phase Shift Keying (DPSK), Quadrature Phase Shift Keying (DQPSK), etc.), so as to achieve the purpose of spreading.
The existing BOK and DM technologies adopt Chirp symbols formed by ascending frequency pulses, descending frequency pulses or a combination of the ascending frequency pulses and the descending frequency pulses to map with single data, so that the time corresponding to each Chirp symbol is required to be greater than or equal to the pulse width, and the mapping of multi-system data cannot be realized in one pulse width (or pulse period). In addition, the existing BOK and DM technologies all use a direct demodulation method to demodulate the encoded data: firstly, converting a radio frequency signal into a baseband signal, and then performing matched filtering by using an original Chirp signal; then, searching a peak value in the output pulse compression signal, and outputting a corresponding mapping signal by a decision device according to the peak value; finally, the encoded data is obtained by demapping. However, in the direct demodulation method, only a single bit of data can be obtained for each compressed pulse. Therefore, the existing modulation and demodulation techniques make the transmission efficiency of the communication data low.
Disclosure of Invention
The invention aims to provide a modulation method and a modulator based on a linear frequency modulation signal, a demodulation method and a demodulator based on the linear frequency modulation signal, a communication method and a communication system, which can realize modulation and demodulation of multi-system data in one pulse width, thereby greatly improving the transmission efficiency of communication data.
In order to achieve the above object, a first aspect of the present invention provides a modulation method based on a chirp signal, the modulation method including: selectingSelecting M different phase data or M different frequency data, wherein M is 2LL is a positive integer, and the phase data or the frequency data are discretized phase data or frequency data of a chirp signal implanted with Doppler shift; mapping M-ary data modulation to the M different phase data or the M different frequency data; and generating and outputting M modulation signals corresponding to the M-ary data according to the M different phase data or the M different frequency data.
Preferably, any one of the M different phase data
Figure BDA0002647635050000031
Generated by the following method:
Figure BDA0002647635050000032
or
Figure BDA0002647635050000033
Wherein N is the number of time segments in which the pulse period of the chirp signal without implanted Doppler shift is divided, and delta phimIs a random value, a value satisfying a predetermined rule or a constant value,
Figure BDA0002647635050000034
the phase of the mth chirp signal without implanted Doppler shift in the nth time segment; or any one of the M different frequency data
Figure BDA0002647635050000035
Generated by the following method:
Figure BDA0002647635050000036
or
Figure BDA0002647635050000037
Wherein N is the number of time segments into which the pulse period of the chirp signal without implanted Doppler shift is divided, and Δ fmIs a random value, a value satisfying a predetermined rule or a constant value,
Figure BDA0002647635050000038
the frequency of the mth chirp signal without implanted doppler shift in the nth time segment.
Preferably, before performing the step of mapping the M-ary data modulation to M different phase data or M different frequency data, the modulation method further comprises: generating a synchronous timing signal; selecting phase data or frequency data of a reference chirp signal in response to generation of the synchronization timing signal; and generating and outputting the reference chirp signal as a synchronous timing signal according to the phase data or the frequency data of the reference chirp signal.
Preferably, the reference chirp signal is a chirp signal with no doppler shift implanted or a chirp signal with doppler shift implanted.
Preferably, the phase of the doppler-shifted chirp signal is a function of a quadratic polynomial or a non-linear function with respect to time.
Through the technical scheme, the invention creatively selects M different discretization phase data (or frequency data) of the Doppler frequency shift implanted chirp signals, then modulates and maps M-system data to the selected M phase data (or frequency data), and finally generates M different chirp waveforms (namely M different modulation signals) according to the M phase data (or frequency data), thereby realizing modulation and mapping of multilevel data in one pulse width and greatly improving the transmission efficiency of communication data.
A second aspect of the present invention provides a demodulation method based on a chirp signal, the demodulation method including: performing matched filtering on a specific modulation signal in M modulation signals output according to the modulation method based on the linear frequency modulation signal to obtain a first pulse compression signal corresponding to the specific modulation signal; acquiring a peak value of the first pulse compression signal and a first time offset of a peak position corresponding to the peak value, wherein the first time offset is an offset of the peak position corresponding to the peak value of the first pulse compression signal relative to a central time of a linear frequency modulation signal without implanted Doppler frequency shift; under the condition that the peak value of the first pulse compression signal is larger than a first preset intensity, receiving the specific modulation signal, and calculating the difference value of the first time offset and a reference time offset; and outputting demodulation data corresponding to the specific modulation signal according to the difference.
Preferably, the reference time offset is obtained by: performing matched filtering on a reference linear frequency modulation signal serving as a synchronous timing signal to obtain a second pulse compression signal corresponding to the reference linear frequency modulation signal; acquiring a peak value of the second pulse compression signal and a second time offset of a peak position corresponding to the peak value, wherein the offset of the peak position corresponding to the peak value of the second pulse compression signal relative to the central time of the chirp signal without implanted Doppler shift; and receiving the reference chirp signal and recording the second time offset as a reference time offset when the peak value of the second pulse compression signal is greater than a second preset intensity.
Preferably, the reference chirp signal is a chirp signal with no doppler shift implanted or a chirp signal with doppler shift implanted.
Preferably, after the step of outputting the demodulation data corresponding to the specific modulation signal is performed, the demodulation method further includes: counting the output mediation data; and determining that the M modulation signals are received completely and feeding back a specific signal to trigger generation of a next synchronization signal in the case that the number of output demodulation data is equal to M.
Through the technical scheme, the invention creatively carries out matched filtering on a specific modulation signal in M different Doppler frequency shift implanted linear frequency modulation signals, and obtains the peak value of a first pulse compression signal corresponding to the specific modulation signal and the time offset of the peak position corresponding to the peak value; then, performing amplitude decision to determine whether to receive the specific modulation signal, for example, if the peak value of the first pulse compression signal is greater than a preset intensity, receiving the specific modulation signal, and calculating a difference between the time offset and a reference time offset; and finally, outputting demodulation data mapped with the specific modulation signal according to the calculated difference, thereby accurately and effectively demodulating the multilevel data in a single pulse period modulated by the Doppler frequency shift implanted chirp signal, and greatly improving the transmission efficiency of the data.
A third aspect of the invention provides a modulator based on a chirp signal, the modulator comprising: selection means for selecting M different phase data or M different frequency data, where M is 2LL is a positive integer, and the phase data or the frequency data are discretized phase data or frequency data of a chirp signal implanted with Doppler shift; modulation mapping means for modulation mapping M-ary data to the M different phase data or the M different frequency data; and a modulation signal generating device for generating and outputting M modulation signals corresponding to the M-ary data according to the M different phase data or the M different frequency data.
Preferably, the modulator further comprises: synchronization signal generation means for generating a synchronization timing signal, and correspondingly, the selection means is further configured to select phase data or frequency data of a reference chirp signal in response to the generation of the synchronization timing signal; and the modulation signal generating means is further configured to generate and output the reference chirp signal as a synchronous timing signal based on phase data or frequency data of the reference chirp signal.
For details and advantages of the chirp-based modulator provided by the present invention, reference may be made to the above description of the chirp-based modulation method, and details are not repeated herein.
A fourth aspect of the present invention provides a demodulator based on a chirp signal, the demodulator comprising: the matched filter is used for performing matched filtering on a specific modulation signal in M modulation signals output by the modulator based on the linear frequency modulation signal so as to obtain a first pulse compression signal corresponding to the specific modulation signal; a peak-to-peak position obtaining device, configured to obtain a peak value of the first pulse compressed signal and a first time offset of the peak position corresponding to the peak value, where the first time offset is an offset of the peak position corresponding to the peak value of the first pulse compressed signal with respect to a center time of a chirp signal in which a doppler shift is not implanted; a difference calculating means for receiving the specific modulation signal and calculating a difference between the first time offset and a reference time offset in a case where a peak value of the first pulse compression signal is greater than a first preset intensity; and a demodulating means for outputting demodulated data corresponding to the specific modulated signal based on the difference.
Preferably, the matched filter is further configured to match-filter a reference chirp signal as a synchronous timing signal to obtain a second pulse compression signal corresponding to the reference chirp signal, and the peak-to-peak obtaining device is further configured to obtain a peak of the second pulse compression signal and a second time offset of a peak corresponding to the peak, where the peak corresponding to the peak of the second pulse compression signal is offset from a center time of the chirp signal without doppler shift implantation, and accordingly, the demodulator further includes: and the recording device is used for receiving the reference chirp signal and recording the second time offset as a reference time offset under the condition that the peak value of the second pulse compression signal is greater than a second preset intensity.
For details and advantages of the demodulator based on chirp signals provided by the present invention, reference may be made to the above description of the demodulation method based on chirp signals, and details are not described herein again.
A fifth aspect of the present invention provides a communication method, including: outputting M modulation signals corresponding to the M-ary data according to the modulation method based on the linear frequency modulation signals; and outputting demodulation data corresponding to a specific modulation signal of the M modulation signals according to the demodulation method based on the linear frequency modulation signal.
A sixth aspect of the present invention provides a communication system comprising: the modulator based on the linear frequency modulation signal is used for outputting M modulation signals corresponding to the M-system data; and the demodulator based on the linear frequency modulation signals is used for outputting demodulation data corresponding to a specific modulation signal in the M modulation signals.
The seventh aspect of the present invention also provides a machine-readable storage medium having stored thereon instructions for causing a machine to execute the chirp-based modulation method, demodulation method, and/or communication method.
Additional features and advantages of embodiments of the invention will be set forth in the detailed description which follows.
Drawings
The accompanying drawings, which are included to provide a further understanding of the embodiments of the invention and are incorporated in and constitute a part of this specification, illustrate embodiments of the invention and together with the description serve to explain the embodiments of the invention without limiting the embodiments of the invention. In the drawings:
fig. 1 is a flowchart of a modulation method based on a chirp signal according to an embodiment of the present invention;
FIG. 2A is an example of frequency data (or vectors) provided by an embodiment of the present invention;
fig. 2B is an example of phase data (or vectors) provided by an embodiment of the present invention.
Fig. 3A shows 2 frequency vectors (corresponding to 4-ary data) according to an embodiment of the present invention
Figure BDA0002647635050000072
Figure BDA0002647635050000071
) Examples of (a);
FIG. 3B is an embodiment of the present invention2 frequency vectors corresponding to 4-ary data are provided (
Figure BDA0002647635050000073
Figure BDA0002647635050000074
) Examples of (a);
fig. 4 is a block diagram of a communication system based on chirp signals provided by an embodiment of the present invention;
fig. 5 is a flowchart of a demodulation method based on a chirp signal according to an embodiment of the present invention;
fig. 6 is a flowchart for obtaining the reference time offset according to an embodiment of the present invention;
fig. 7 is a diagram illustrating relative offsets between a transmitting end and a receiving end according to an embodiment of the present invention;
FIG. 8 is a diagram of a pulse compression signal according to an embodiment of the present invention;
FIG. 9 is a timing diagram of matched filtering according to an embodiment of the present invention;
fig. 10 is a diagram illustrating the output results of the peak value and the peak position of the reference Chirp signal (Nor-Chirp signal) and the doppler shift-embedded Chirp signal (ID-Chirp signal) according to an embodiment of the present invention;
FIG. 11 is a flow chart of a communication process for 4-ary data according to an embodiment of the present invention;
fig. 12 is a block diagram of a chirp based modulator according to an embodiment of the present invention; and
fig. 13 is a block diagram of a demodulator based on a chirp signal according to an embodiment of the present invention.
Description of the reference numerals
1 data generating device 10 selecting device
Modulation mapping device for 1-out-of-152 switch 20
30 modulated signal generating means 35 first signal conversion means
40 synchronization signal generating means 45 second signal conversion means
Device for acquiring peak position of 60 peak of 50-matched filter
62 peak value peak position acquisition module 64 offset calculation module
66 amplitude judgment module 70 difference value calculation device
80 demodulator 90 channel
100 decision device
Detailed Description
The following detailed description of embodiments of the invention refers to the accompanying drawings. It should be understood that the detailed description and specific examples, while indicating the present invention, are given by way of illustration and explanation only, not limitation.
The formula of the Chirp signal (Chirp signal) is as follows:
Figure BDA0002647635050000081
wherein j is a complex unit symbol; phi (t) is the phase of the Chirp signal;
Figure BDA0002647635050000082
the pulse width (or period) of the rectangular pulse signal with the amplitude of 1 and the pulse width of T is represented by the following specific formula:
Figure BDA0002647635050000091
for a chirp signal without an implanted doppler shift, its phase may be:
Figure BDA0002647635050000092
so for a chirp signal without an implanted doppler shift, its phase is symmetric about t-0 and the frequency (i.e., the derivative of phase with respect to time) varies linearly with time. The doppler-shifted Chirp signal (ID-Chirp signal) in various embodiments of the present invention is based on a doppler-shift-unimplanted Chirp signal (i.e., a raw Chirp signal) with doppler shift implanted to form discretized frequency data (or vector, also referred to as ID-Chirp symbols) as shown in fig. 2A. The chirp signals based on multiple implanted Doppler frequency shifts can realize modulation mapping of multi-system data in one pulse period.
Fig. 1 is a flowchart of a modulation method based on a chirp signal according to an embodiment of the present invention. As shown in fig. 1, the modulation method may include steps S101-S103.
In an embodiment, before performing step S101, the modulation method may further include: generating any one of the M different phase data by equation (1) or (2)
Figure BDA0002647635050000093
Wherein M is 2LL is a positive integer,
Figure BDA0002647635050000094
Figure BDA0002647635050000095
wherein N is the number of time segments in which the pulse period of the chirp signal without implanted Doppler shift is divided, and delta phimIs a random value, a value satisfying a predetermined rule or a constant value,
Figure BDA0002647635050000096
the phase of the mth chirp signal without implanted doppler shift in the nth (i.e., the sequence number of the frequency vector) time period. Due to delta phimCan be random value or value satisfying preset rule, so that the relation between the phase of the linear frequency modulation signal implanted with Doppler frequency shift and time is the functional relation or nonlinear function of quadratic polynomialA numerical relationship (the non-linear functional relationship may extend the type of frequency data, so that more types of frequency data may be used to characterize a more binary data signal, e.g., it is hyperbolic). For example, FIG. 2B shows
Figure BDA0002647635050000101
No longer symmetrical with respect to t-0.
In another embodiment, before performing step S101, the modulation method may further include: generating any one of the M different frequency data by equation (3) or (4)
Figure BDA0002647635050000102
Figure BDA0002647635050000103
Figure BDA0002647635050000104
Wherein N is the number of time segments into which the pulse period of the chirp signal without implanted Doppler shift is divided, and Δ fmIs a random value, a value satisfying a predetermined rule or a constant value,
Figure BDA0002647635050000105
the frequency of the mth chirp signal without implanted doppler shift in the nth time segment. For example, FIG. 2A shows
Figure BDA0002647635050000106
In a specific form of (1), wherein Δ fmIs a constant value, therefore
Figure BDA0002647635050000107
Is a regular frequency vector. The M different frequency data
Figure BDA0002647635050000108
Different Δ f can be selectedmAs shown in fig. 3A and 3B.
To limit the spectral width of the output Chirp waveform, f can be takenmn∈[-B/2,+B/2]。
The above-mentioned M different phase data (or frequency) data are referred to as M different Chirp symbols, so the above-mentioned process can be referred to as a process of generating M different Chirp symbols, and the following processes of modulating and mapping M-ary data to M Chirp symbols and outputting M Chirp waveforms according to the M Chirp symbols are performed through steps S101 to S103.
In order to assume that the relative speeds of the transmitting and receiving ends (i.e., the modulator end and the demodulator end) are not substantially changed within M Chirp symbols (i.e., the time period of the Chirp pulse), the transmitting end can transmit a reference Chirp pulse every M Chirp symbols at intervals, and the receiving end can correct the time offset of the ID-Chirp signal after the reference Chirp pulse according to the received reference Chirp pulse, as shown in fig. 7. Therefore, the invention can solve the problem that the direct demodulation mode can not judge the multi-system pulse compression result, and can also avoid the problem that the external Doppler frequency shift in mobile communication causes wrong system judgment. GP in fig. 7 indicates a guard interval, and may be used as a function of transmitting/receiving conversion of an upper layer protocol. The GP is configurable as a parameter of the system, and may even be 0 in duration.
Before performing step S101, the modulation method may further include: generating a synchronous timing signal; selecting phase data or frequency data of a reference chirp signal in response to generation of the synchronization timing signal; and generating and outputting the reference chirp signal as a synchronous timing signal according to the phase data or the frequency data of the reference chirp signal.
The reference chirp signal is a chirp signal without Doppler frequency shift implanted or a chirp signal with Doppler frequency shift implanted.
Specifically, a synchronization timing signal is generated by the synchronization signal generation means 40 as a control signal for controlling the transmission timing of the phase data (or the frequency data); the phase data (or frequency data) of the reference Chirp signal can be selected by the 2-to-1 switch 15 while the synchronous timing signal is generated; then, the reference Chirp signal (i.e., Chirp waveform) can be generated based on the phase data (or frequency data) of the reference Chirp signal and the above equation (1), and the reference Chirp signal can be used as the synchronous timing signal to correct the time offset of the ID-Chirp signal after the reference Chirp pulse.
Step S101, M different phase data or M different frequency data are selected.
Wherein M is 2LL is a positive integer (L ═ 1, 2, 3, or the like), and the phase data or the frequency data are discretized phase data or frequency data of a chirp signal in which doppler shift is implanted.
For example, discretized frequency data (or frequency vectors) of M different doppler shifted chirped signals may be selected from the data generation device 1 according to the synchronized timing signal and by means of the 1-out-of-2 switch 15 in fig. 4.
Step S102, mapping M-ary data modulation to the M different phase data or M different frequency data.
Wherein the phase data or the frequency data are discretized phase data or frequency data of a chirp signal with an implanted doppler shift.
For example, for a 4-ary modulation system, the relevant parameters are: the signal bandwidth B is 100 KHz; the pulse period T is 1.5 ms; sampling time Ts 1/(2B) 1e-5s; m is 4; and N is 100.
Table 14 mapping relationship between the binary symbols and 4 Chirp symbols
Figure BDA0002647635050000121
Specifically, the modulation mapping process in step S101 may be performed according to the mapping relationship of table 1. Of course, in another embodiment of the present invention, the terms "00011011" and "00011011" may also be used
Figure BDA0002647635050000122
Or other mapping means.
Step S103, generating and outputting M modulation signals corresponding to the M-ary data according to the M different phase data or the M different frequency data.
M different modulation signals (i.e., Chirp waveforms) can be generated based on the M different phase data (or frequency data) and the formula (1), and the generated M modulation signals correspond to M-ary data one to one.
After performing the step of outputting the M modulation signals corresponding to the M-ary data, the modulation method may further include: converting the M modulation signals from baseband signals to radio frequency signals to transmit the radio frequency signals through a channel.
In an embodiment of the present invention, data may also be channel coded to improve the reliability of data transmission by adding redundancy. In addition, since the energy is concentrated on a certain frequency when the data is repeatedly transmitted, thereby generating EMI noise, the scrambling code is added to the data in this embodiment of the present invention, so that the concentrated energy can be dispersed, and the EMI noise that may be generated can be made white. Specifically, before performing step S101, the modulation method may further include: performing channel coding on the M-system data; and scrambling the M-ary data subjected to channel coding.
In various embodiments of the present invention, different Chirp symbols may be used to distinguish between the phase data (or frequency data) of the reference Chirp signal and the phase data (or frequency data) of the ID-Chirp signal.
In summary, the present invention creatively selects discretized phase data (or frequency data) of M different doppler-shift-implanted chirps, then modulates and maps M-ary data to the selected M phase data (or frequency data), and finally generates M different chirp waveforms (i.e., M different modulation signals) according to the M phase data (or frequency data), thereby implementing modulation and mapping on multilevel data within one pulse width, and greatly improving transmission efficiency of communication data.
Fig. 5 is a flowchart of a demodulation method based on a chirp signal according to an embodiment of the present invention. The demodulation method may include steps S501-S504.
Before performing step S501, as shown in fig. 6, the demodulation method may further include: the reference time offset is acquired by the following steps S601 to S603.
Step S601, performing matched filtering on a reference chirp signal serving as a synchronous timing signal to obtain a second pulse compression signal corresponding to the reference chirp signal.
That is, in the case where the reference Chirp signal is received by the matched filter 50, the reference Chirp signal (for example, from the Chirp-0 signal in fig. 7) is matched-filtered (i.e., pulse-compressed) by the matched filter 50 in fig. 4 to obtain a pulse-compressed signal corresponding to the reference Chirp signal.
Step S602, a peak of the second pulse compressed signal and a second time offset of a peak position corresponding to the peak are obtained, where the peak position corresponding to the peak of the second pulse compressed signal is offset from a center time of the chirp signal without doppler shift implantation.
According to the compressed pulse algorithm (matched filter theory), when the received signal is aligned with the matched filtered Chirp signal (original Chirp signal) without implanted doppler shift, the amplitude of its output pulse is maximum. As shown in fig. 9, the peak value of the signal of the pulse compression output is maximum at time t3 in fig. 9. Therefore, in the present embodiment, the time offset of the peak position of the Chirp signal implanted with the doppler shift after matched filtering can be identified by using this feature of the pulse compression technique.
Calculating the peak value and the peak position of the pulse compression signal corresponding to the reference Chirp signal in step S601 through the peak position obtaining module 62 in the peak position obtaining apparatus in fig. 4; and the offset calculating module 64 in the peak position obtaining device 60 in fig. 4 calculates the offset of the peak position time relative to the center time based on the time of the peak position and the center time of the Chirp signal (original Chirp signal) without doppler shift implantation. As shown in fig. 10, ID-Chirp refers to a Chirp signal with doppler shift implanted, and the corresponding result is the output of the peak position acquisition module 62. The Nor-Chirp is a Chirp signal without implanted doppler shift, in which a right triangle represents a time offset of the ID-Chirp signal (or the Nor-Chirp signal) output by the offset calculation module 64, and an isosceles triangle (or an isosceles trapezoid) represents a peak value of the ID-Chirp signal (or the Nor-Chirp signal) output by the amplitude determination module 66, and in which an abscissa-time sequence number corresponds to a measurement time of the matched filter. As can be seen from fig. 10, the peak value of the ID-chirp signal is 505.5 (time number 1160), and the time of the peak position corresponding to the peak value is 549 (i.e., the ordinate of the right triangle of the ID-chirp signal at time number 1160); the peak value of the Nor-chirp signal is 597 (time number 1200), and the time of the peak position corresponding to the peak value is 598 (i.e. the ordinate of the right triangle of the Nor-chirp signal at time number 1200), so the time offset between the ID-chirp signal and the Nor-chirp signal is (598-.
Step S603, receiving the reference chirp signal when the peak value of the second pulse compression signal is greater than a second preset intensity, and recording the second time offset as a reference time offset.
If the peak value of the pulse compression signal corresponding to the reference Chirp signal is greater than a certain preset intensity, it indicates that the reference Chirp signal is not an interference signal, and the reference Chirp signal may be received by the decision device 100 in fig. 4, and the time offset corresponding to the reference Chirp signal is recorded as a parametric time offset.
The reference time offset obtained in steps S601-S603 may be used as a reference value of the time offsets of the M modulation signals, and a difference between the time offsets of the M modulation signals and the reference value is used as a basis for a demodulation process.
Step S501, performing matched filtering on a specific modulation signal of M modulation signals output according to the modulation method based on the chirp signal, so as to obtain a first pulse compression signal corresponding to the specific modulation signal.
Similarly to step S601, in the case that the matched filter 50 receives a specific modulation signal (for example, the Chirp-2 signal in fig. 7) in the M modulation signals, the specific modulation signal (for example, the Chirp-2 signal in fig. 7) is matched-filtered (i.e., pulse-compressed) by the matched filter 50 in fig. 4 to obtain a pulse-compressed signal corresponding to the specific modulation signal, as shown in fig. 8.
Step S502, a peak value of the first pulse compressed signal and a first time offset of a peak position corresponding to the peak value are obtained.
The first time offset is an offset of a peak position corresponding to a peak value of the first pulse compression signal relative to a center time of the chirp signal without implanted doppler shift.
Calculating the peak value and the peak position of the pulse compression signal corresponding to the specific modulation signal (for example, Chirp-2 signal in fig. 7) in step S501 by the peak-to-peak position obtaining device in fig. 4; and the offset calculating means in fig. 4 calculates the offset of the time of the peak position with respect to the center time based on the time of the peak position and the center time of the Chirp signal (original Chirp signal) not implanted with the doppler shift.
Step S503, receiving the specific modulation signal when the peak value of the first pulse compression signal is greater than a first preset intensity, and calculating a difference between the first time offset and a reference time offset.
If the peak value of the pulse compression signal corresponding to the specific modulation signal (e.g., the Chirp-2 signal in fig. 7) is greater than another preset intensity, it indicates that the specific modulation signal is not an interference signal, and the specific modulation signal may be received by the decision device 100 in fig. 4, and the difference between the time offset corresponding to the specific modulation signal and the parametric time offset is calculated.
Step S504, outputting the demodulated data corresponding to the specific modulation signal according to the difference.
Combining the difference output with the time offset of the compressed pulse based on a mapping relationship between the symbol and the time offsetAnd demodulation data corresponding to the specific modulation signal (for example, a Chirp-2 signal in fig. 7). For example, if the difference is τ1Then the demodulated data corresponding to the particular modulated signal is 00.
After performing the step of outputting the demodulation data corresponding to the specific modulation signal, the demodulation method may further include: counting the output mediation data; and determining that the M modulation signals are received completely and feeding back a specific signal to trigger generation of a next synchronization signal in the case that the number of output demodulation data is equal to M.
After performing the step of outputting the demodulation data corresponding to the specific modulation signal, the demodulation method may further include: channel-decoding the outputted demodulated data corresponding to the specific modulated signal; and performing descrambling processing on the demodulated data subjected to channel decoding.
Specifically, the communication process of the 4-ary data will now be explained and explained by taking the communication system shown in fig. 4 as an example, which mainly includes steps S1101-S1114, as shown in fig. 11.
In step S1101, a synchronous timing signal is generated, and a frequency vector of the original Chirp signal is selected.
The frequency vector of the original Chirp signal can be selected as input for Chirp generation by the 2-out-of-1 switch 15.
Step S1102 is to generate an original Chirp signal based on the frequency vector of the original Chirp signal, and to transmit the original Chirp signal through a channel.
Specifically, the modulation signal generating device 30 may generate an original Chirp signal according to a frequency vector of the original Chirp signal; then, the original Chirp signal can be converted from a baseband signal to a radio frequency signal suitable for transmission in the channel 90 by the first signal conversion device 35; then transmitting the original Chirp signal through a channel 90; finally, the original Chirp signal can be converted from a radio frequency signal to a baseband signal by the second signal conversion device 45.
Step S1103, performing pulse compression on the original Chirp signal to obtain a pulse compressed signal corresponding to the original Chirp signal.
Step S1104, a peak value and a peak position of the pulse compression signal are obtained.
The peak value and the peak position of the pulse compression signal can be obtained by a peak position obtaining module 62 in the peak position obtaining device 60.
Step S1105, calculating a second time offset of a peak position of the pulse compression signal, determining whether the peak value is greater than a1, if so, executing step S1106, otherwise, executing step S1101.
The second time offset may be calculated by the offset calculating module 64 in the peak-to-peak obtaining device 60, and whether the peak is greater than a1 may be determined by the amplitude determining module 66 in the peak-to-peak obtaining device 60, if so, it indicates that the original Chirp signal is not an interference signal, and step S1106 is executed; otherwise, it indicates that the original Chirp signal is an interference signal, and the transmission of the original Chirp signal is re-performed through step S1101.
In step S1106, the second time offset is recorded as a reference time offset.
The second time offset can be recorded by the decision device 100 as a reference time offset, so that the decision influence of doppler shift in the environment on the demodulation of the communication system can be solved by using the reference Chirp signal, and accurate and effective demodulation data can be obtained.
Step S1107, selects a frequency vector of the i-th ID-Chirp signal according to the synchronization timing signal.
And selecting the frequency vector of the ith ID-Chirp signal through a 2-to-1 switch 15 according to the synchronous timing signal.
Step S1108, generating the ith ID-Chirp signal based on the frequency vector of the ith ID-Chirp signal, and transmitting the ith ID-Chirp signal through a channel.
Similar to the process of step S1102, see the detailed description about step S1102.
Step S1109, performing matched pulse compression on the ith ID-Chirp signal to obtain an ith pulse compressed signal corresponding to the ith ID-Chirp signal.
The pulse compression process in steps S1103 and S1109 described above may be performed by the matched filter 50.
Step S1110, a peak value and a peak position of the ith pulse compression signal are obtained.
The peak value and the peak position of the pulse compression signal can be obtained by the peak-to-peak position obtaining module 62.
Step S1111, calculating a first time offset of a peak position of the ith pulse compression signal, determining whether the peak value is greater than a2, if so, executing step S1112; otherwise, step S1107 is executed.
The first time offset may be calculated by the offset calculating module 64, and the amplitude determining module 66 determines whether the peak value is greater than a2, if so, it indicates that the ith ID-Chirp signal is not an interference signal, and step S1112 is executed; otherwise, it indicates that the ith ID-Chirp signal is an interference signal, and re-performs transmission of the ith ID-Chirp signal through step S1107.
In step S1112, a difference between the first time offset and the reference time offset is obtained.
The difference between the first time offset and the reference time offset may be calculated by a difference calculation means 70 (which may be integrated in the decision means 100).
Step S1113, outputting the demodulated data corresponding to the i-th ID-Chirp signal based on the difference.
The demodulated data corresponding to the specific modulated signal (for example, Chirp-2 signal in fig. 7) can be output by the demodulating means 80 based on the mapping relationship between the symbols and the time offsets of the compressed pulses in combination with the difference. For example, if the difference is τ1Then the demodulated data bit 00 corresponding to the particular modulated signal.
Step S1114, determining whether i is equal to 4, if yes, executing step S1101; otherwise, i +1 and step S1107 are executed.
If i is equal to 4, all the 4-ary data corresponding to the frame is received, and step S1101 is executed to re-execute the reception of the 4-ary data of the next frame. If i is less than 4, it indicates that the 4-ary data of the frame has not been received, and it is necessary to perform i ═ i +1 and perform the demodulation and reception process of the next data through step S1107 until i ═ 4.
In summary, the present invention creatively performs matched filtering on a specific modulation signal among M different doppler-shift-implanted chirp signals, and obtains a peak value of a first pulse compression signal corresponding to the specific modulation signal and a time offset of a peak position corresponding to the peak value; then, performing amplitude decision to determine whether to receive the specific modulation signal, for example, if the peak value of the first pulse compression signal is greater than a preset intensity, receiving the specific modulation signal, and calculating a difference between the time offset and a reference time offset; and finally, outputting demodulation data mapped with the specific modulation signal according to the calculated difference, thereby accurately and effectively demodulating the multilevel data in a single pulse period modulated by the Doppler frequency shift implanted chirp signal, and greatly improving the transmission efficiency of the data.
Fig. 12 is a block diagram of a modulator based on a chirp signal according to an embodiment of the present invention. As shown in fig. 12, the modulator may include: selection means 10 for selecting M different phase data or M different frequency data, where M is 2LL is a positive integer, and the phase data or the frequency data are discretized phase data or frequency data of a chirp signal implanted with Doppler shift; a modulation mapping device 20 for modulating and mapping the M-ary data to the M different phase data or the M different frequency data; and a modulation signal generating means 30 for generating and outputting M modulation signals corresponding to the M-ary data based on the M different phase data or the M different frequency data. Wherein, the selection device 10 can be a 1-out-of-2 switch 15.
Preferably, the modulator further comprises: a data generation device 1 for any one of the M different phase data
Figure BDA0002647635050000191
Generated by the following method:
Figure BDA0002647635050000192
or
Figure BDA0002647635050000193
Wherein N is the number of time segments in which the pulse period of the chirp signal without implanted Doppler shift is divided, and delta phimIs a random value, a value satisfying a predetermined rule or a constant value,
Figure BDA0002647635050000194
the phase of the mth chirp signal without implanted Doppler shift in the nth time segment; or any one of the M different frequency data
Figure BDA0002647635050000201
Generated by the following method:
Figure BDA0002647635050000202
or
Figure BDA0002647635050000203
Wherein N is the number of time segments into which the pulse period of the chirp signal without implanted Doppler shift is divided, and Δ fmIs a random value, a value satisfying a predetermined rule or a constant value,
Figure BDA0002647635050000204
the frequency of the mth chirp signal without implanted doppler shift in the nth time segment.
Preferably, the modulator further comprises: the synchronization signal generating means 40 is used for generating a synchronization timing signal, as shown in fig. 4. Accordingly, the selection means 10 is further configured to select, in response to the generation of the synchronization timing signal, phase data or frequency data of a reference chirp signal; and the modulation signal generating means 30 is further configured to generate and output the reference chirp signal as a synchronous timing signal according to the phase data or the frequency data of the reference chirp signal.
For details and advantages of the chirp-based modulator provided by the present invention, reference may be made to the above description of the chirp-based modulation method, and details are not repeated herein.
Fig. 13 is a block diagram of a demodulator based on a chirp signal according to an embodiment of the present invention. As shown in fig. 13, the demodulator may include: a matched filter 50, configured to perform matched filtering on a specific modulation signal of the M modulation signals output by the chirp-based modulator, so as to obtain a first pulse compression signal corresponding to the specific modulation signal; a peak position obtaining device 60, configured to obtain a peak value of the first pulse compressed signal and a first time offset of the peak position corresponding to the peak value, where the first time offset is an offset of the peak position corresponding to the peak value of the first pulse compressed signal with respect to a center frequency of the chirp signal without doppler shift implantation; a difference calculating means 70 for receiving the specific modulation signal and calculating a difference between the first time offset and a reference time offset in a case where a peak value of the first pulse compression signal is greater than a first preset intensity; and a demodulating means 80 for outputting demodulated data corresponding to the specific modulated signal based on the difference.
Preferably, the matched filter 50 is further configured to match-filter the reference chirp signal as the synchronous timing signal to obtain a second pulse compression signal corresponding to the reference chirp signal, and the peak-to-peak position obtaining device 60 is further configured to obtain a peak value of the second pulse compression signal and a second time offset of a peak position corresponding to the peak value, where the peak position corresponding to the peak value of the second pulse compression signal is offset from a center time of the chirp signal without doppler shift implantation, and accordingly, the demodulator further includes: and a recording device (not shown) for receiving the reference chirp signal and recording the second time offset as a reference time offset in a case where a peak value of the second pulse compression signal is greater than a second preset intensity. Wherein the recording means (not shown) may be integrated in the decision means 100.
Preferably, the demodulator further comprises: counting means (not shown) for counting the outputted mediation data; and feedback means (not shown) for determining that the M modulation signals are received completely and feeding back a specific signal to trigger generation of a next synchronization signal, in a case where the number of outputted mediation data is equal to M.
For details and advantages of the demodulator based on chirp signals provided by the present invention, reference may be made to the above description of the demodulation method based on chirp signals, and details are not described herein again.
An embodiment of the present invention further provides a communication method, where the communication method may include: outputting M modulation signals corresponding to the M-ary data according to the modulation method based on the linear frequency modulation signals; and outputting demodulation data corresponding to a specific modulation signal of the M modulation signals according to the demodulation method based on the linear frequency modulation signal.
An embodiment of the present invention further provides a communication system, where the communication system may include: the modulator based on the linear frequency modulation signal is used for outputting M modulation signals corresponding to the M-system data; and the demodulator based on the linear frequency modulation signals is used for outputting demodulation data corresponding to a specific modulation signal in the M modulation signals.
An embodiment of the present invention further provides a machine-readable storage medium having stored thereon instructions for causing a machine to execute the chirp-based modulation method, demodulation method, and/or communication method.
The machine-readable storage medium includes, but is not limited to, Phase Change Random Access Memory (PRAM, also known as RCM/PCRAM), Static Random Access Memory (SRAM), Dynamic Random Access Memory (DRAM), other types of Random Access Memory (RAM), Read Only Memory (ROM), Electrically Erasable Programmable Read Only Memory (EEPROM), Flash Memory (Flash Memory) or other Memory technology, compact disc read only Memory (CD-ROM), Digital Versatile Disc (DVD) or other optical storage, magnetic cassettes, magnetic tape, magnetic disk storage or other magnetic storage devices, and various media capable of storing program code.
The preferred embodiments of the present invention have been described in detail with reference to the accompanying drawings, however, the present invention is not limited to the specific details of the above embodiments, and various simple modifications can be made to the technical solution of the present invention within the technical idea of the present invention, and these simple modifications are within the protective scope of the present invention.
It should be noted that the various features described in the above embodiments may be combined in any suitable manner without departing from the scope of the invention. The invention is not described in detail in order to avoid unnecessary repetition.
In addition, any combination of the various embodiments of the present invention is also possible, and the same should be considered as the disclosure of the present invention as long as it does not depart from the spirit of the present invention.

Claims (15)

1. A modulation method based on chirp signals, the modulation method comprising:
selecting M different phase data or M different frequency data, wherein M is 2LL is a positive integer, and the phase data or the frequency data are discretized phase data or frequency data of a chirp signal implanted with Doppler shift;
mapping M-ary data modulation to the M different phase data or the M different frequency data; and
and generating and outputting M modulation signals corresponding to the M-ary data according to the M different phase data or the M different frequency data.
2. The chirp-based modulation method according to claim 1,
any one of the M different phase data
Figure FDA0002647635040000011
Generated by the following method:
Figure FDA0002647635040000012
or
Figure FDA0002647635040000014
Wherein N is the number of time segments in which the pulse period of the chirp signal without implanted Doppler shift is divided, and delta phimIs a random value, a value satisfying a predetermined rule or a constant value,
Figure FDA0002647635040000015
the phase of the mth chirp signal without implanted Doppler shift in the nth time segment; or
Any one of the M different frequency data
Figure FDA0002647635040000016
Generated by the following method:
Figure FDA0002647635040000017
or
Figure FDA0002647635040000018
Wherein N is the number of time segments into which the pulse period of the chirp signal without implanted Doppler shift is divided, and Δ fmIs a random value, a value satisfying a predetermined rule or a constant value,
Figure FDA0002647635040000019
for the mth linear frequency modulation signal without implanted Doppler frequency shift in the nth time segmentOf (c) is detected.
3. The chirp-based modulation method of claim 1, wherein prior to performing the step of mapping M-ary data modulation to M different phase data or M different frequency data, the modulation method further comprises:
generating a synchronous timing signal;
selecting phase data or frequency data of a reference chirp signal in response to generation of the synchronization timing signal; and
and generating and outputting the reference linear frequency modulation signal as a synchronous timing signal according to the phase data or the frequency data of the reference linear frequency modulation signal.
4. The chirp-based modulation method according to claim 1, wherein the reference chirp is a chirp signal without doppler shift implantation or a chirp signal with doppler shift implantation.
5. The chirp-based modulation method of claim 1, wherein the phase of the doppler shift-embedded chirp signal is a function of a quadratic polynomial or a non-linear function with respect to time.
6. A method for demodulation based on a chirp signal, the method comprising:
performing matched filtering on a specific modulation signal in M modulation signals output by the chirp-based modulation method according to any one of claims 1-5 to obtain a first pulse compression signal corresponding to the specific modulation signal;
acquiring a peak value of the first pulse compression signal and a first time offset of a peak position corresponding to the peak value, wherein the first time offset is an offset of the peak position corresponding to the peak value of the first pulse compression signal relative to a central time of a linear frequency modulation signal without implanted Doppler frequency shift;
under the condition that the peak value of the first pulse compression signal is larger than a first preset intensity, receiving the specific modulation signal, and calculating the difference value of the first time offset and a reference time offset; and
and outputting the demodulation data corresponding to the specific modulation signal according to the difference value.
7. The chirp-based demodulation method according to claim 6, wherein the reference time offset is obtained by:
performing matched filtering on a reference linear frequency modulation signal serving as a synchronous timing signal to obtain a second pulse compression signal corresponding to the reference linear frequency modulation signal;
acquiring a peak value of the second pulse compression signal and a second time offset of a peak position corresponding to the peak value, wherein the offset of the peak position corresponding to the peak value of the second pulse compression signal relative to the central time of the chirp signal without implanted Doppler shift; and
and receiving the reference linear frequency modulation signal under the condition that the peak value of the second pulse compression signal is greater than a second preset intensity, and recording the second time offset as a reference time offset.
8. The chirp-based demodulation method according to claim 6, wherein the reference chirp is a chirp signal without doppler shift implantation or a chirp signal with doppler shift implantation.
9. The chirp-based demodulation method according to claim 6, wherein after the step of outputting the demodulated data corresponding to the specific modulation signal is performed, the demodulation method further comprises:
counting the output mediation data; and
in the case where the number of outputted mediation data is equal to M, it is determined that the M modulation signals are received completely, and a specific signal is fed back to trigger generation of a next synchronization signal.
10. A chirp-based modulator, comprising:
selection means for selecting M different phase data or M different frequency data, where M is 2LL is a positive integer, and the phase data or the frequency data are discretized phase data or frequency data of a chirp signal implanted with Doppler shift;
modulation mapping means for modulation mapping M-ary data to the M different phase data or the M different frequency data; and
and the modulation signal generating device is used for generating and outputting M modulation signals corresponding to the M-ary data according to the M different phase data or the M different frequency data.
11. The chirp-based modulator of claim 10, further comprising:
a synchronization signal generating means for generating a synchronization timing signal,
accordingly, the selecting means is further configured to select phase data or frequency data of a reference chirp signal in response to the generation of the synchronization timing signal; and
the modulation signal generation means is further configured to generate and output the reference chirp signal as a synchronous timing signal according to the phase data or the frequency data of the reference chirp signal.
12. A demodulator based on a chirp signal, the demodulator comprising:
a matched filter for matched filtering a specific modulation signal of the M modulation signals output from the chirp-based modulator according to claim 10 or 11 to obtain a first pulse compression signal corresponding to the specific modulation signal;
a peak-to-peak position obtaining device, configured to obtain a peak value of the first pulse compressed signal and a first time offset of the peak position corresponding to the peak value, where the first time offset is an offset of the peak position corresponding to the peak value of the first pulse compressed signal with respect to a center time of a chirp signal in which a doppler shift is not implanted;
a difference calculating means for receiving the specific modulation signal and calculating a difference between the first time offset and a reference time offset in a case where a peak value of the first pulse compression signal is greater than a first preset intensity; and
and a demodulation means for outputting demodulation data corresponding to the specific modulation signal based on the difference.
13. The chirp-based demodulator of claim 12,
the matched filter is further configured to match filter a reference chirp signal as a synchronous timing signal to obtain a second pulse compression signal corresponding to the reference chirp signal, an
The peak position obtaining device is further configured to obtain a peak value of the second pulse compression signal and a second time offset of the peak position corresponding to the peak value, where the offset of the peak position corresponding to the peak value of the second pulse compression signal with respect to a center time of the chirp signal without doppler shift implantation is obtained,
accordingly, the demodulator further comprises: and the recording device is used for receiving the reference chirp signal and recording the second time offset as a reference time offset under the condition that the peak value of the second pulse compression signal is greater than a second preset intensity.
14. A communication method, characterized in that the communication method comprises:
the chirp-based modulation method according to any one of claims 1 to 5, outputting M modulated signals corresponding to the M-ary data; and
the chirp-based demodulation method according to any one of claims 6 to 9, which outputs demodulated data corresponding to a specific modulation signal among the M modulation signals.
15. A communication system, the communication system comprising:
the chirp-based modulator according to claim 10 or 11, configured to output M modulated signals corresponding to the M-ary data; and
a chirp-based demodulator according to claim 12 or 13, for outputting demodulated data corresponding to a particular one of the M modulated signals.
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