CN112019082A - Single-phase bidirectional inversion control circuit and inversion control method thereof - Google Patents
Single-phase bidirectional inversion control circuit and inversion control method thereof Download PDFInfo
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- CN112019082A CN112019082A CN202011138283.8A CN202011138283A CN112019082A CN 112019082 A CN112019082 A CN 112019082A CN 202011138283 A CN202011138283 A CN 202011138283A CN 112019082 A CN112019082 A CN 112019082A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/66—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal
- H02M7/68—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters
- H02M7/72—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/79—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/797—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
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Abstract
The invention discloses a single-phase bidirectional inversion control circuit and an inversion control method thereof, which are characterized in that sampled inductive current and AC source voltage at an AC end are subjected to Park conversion with 90-degree orthogonal quantity generated by the controller to obtain current components Icd and Icq and voltage components Vcd and Vcq under a D-Q coordinate system, the current components Icd and Icq are respectively used as feedback values of a current loop of a controller, the voltage components Vcd and Vcq are respectively used as feedforward values of the controller, values obtained by multiplying the current components Icd and Icq by omega L are respectively used as DQ vector decoupling values, and the controller is used for obtaining driving voltage V alpha for generating PWM driving signals after carrying out iPark conversion on two groups of voltage values output by the voltage loop; the inverter control circuit is controlled by taking an input current reference value icq to a current loop of the control controller as an instruction.
Description
Technical Field
The invention relates to an inverter circuit, in particular to a single-phase bidirectional inverter control circuit and an inverter control method thereof.
Background
An inverter is a power conditioning apparatus composed of semiconductor devices, mainly used for converting dc power into ac power, and generally includes a boost circuit and an inverter bridge circuit. The boosting circuit boosts the direct-current voltage of the solar battery to the direct-current voltage required by the output control of the inverter; the inverter bridge circuit equivalently converts the boosted direct-current voltage into alternating-current voltage with common frequency. With the continuous development of photovoltaic technology, the energy storage type grid-connected power generation solar power supply mode is developed, and in the mode, a bidirectional converter is required to switch two working modes of an energy storage device: when the energy storage device supplies power to a load, the bidirectional inverter plays an inversion role and converts direct current into alternating current; when the energy storage device is charged, the bidirectional inverter plays a role in rectification and conversion, and converts alternating current into direct current.
Most of the existing bidirectional inverters generally comprise a PWM (pulse-width modulation) rectifying circuit and a DC/DC direct current chopper circuit, the PWM rectifying circuit and the DC/DC direct current chopper circuit adopt different control methods, and when the working modes are switched, both the PWM rectifying circuit and the DC/DC direct current chopper circuit need to be switched. The circuit structure of the inverter is relatively complex, the control method is complex, and gaps are easy to occur during switching.
Disclosure of Invention
The invention aims to provide a single-phase bidirectional inversion control circuit and an inversion control method thereof. The single-phase bidirectional inverter control circuit is simple in structure, the inverter control method is simple, and seamless switching can be achieved.
The technical scheme of the invention is as follows: a single-phase bidirectional inversion control circuit is characterized in that: the direct current power supply comprises a capacitor connected to a direct current end interface, wherein a first branch formed by connecting a first diode and a second diode in series is connected to the capacitor in parallel, and a second branch formed by connecting a third diode and a fourth diode in series is also connected to the first branch in parallel; the diode connection node of the first branch circuit and the diode connection node of the second branch circuit are respectively connected to the alternating current terminal interface through a first inductor and a second inductor; a fifth diode and a sixth diode which are connected in parallel and have opposite directions, a sixth diode and a sixth switching tube are also connected between the diode connection node of the first branch and the diode connection node of the second branch; the positive electrodes of the first diode, the second diode, the third diode and the fourth diode point to the same end of the direct current end interface, and a first switch tube, a second switch tube, a third switch tube and a fourth switch tube are respectively connected in parallel on each diode; the first switching tube, the second switching tube, the third switching tube, the fourth switching tube, the fifth switching tube and the sixth switching tube are connected to the controller to be driven, wherein the first switching tube and the fourth switching tube use the same driving signal, and the sixth switching tube and the first switching tube use a group of complementary driving signals; the second switch tube and the third switch tube use the same driving signal, and the fifth switch tube and the second switch tube use a group of complementary driving signals.
The inversion control method using the single-phase bidirectional inversion control circuit is characterized by comprising the following steps of: firstly, conducting Park transformation on sampled inductive current and AC source voltage at an AC end and 90-degree orthogonal quantity generated by the controller, obtaining current components Icd and Icq and voltage components Vcd and Vcq under a D-Q coordinate system, respectively taking the current components Icd and Icq as feedback values of a current loop of the controller, respectively taking the voltage components Vcd and Vcq as feedforward values of the controller, simultaneously respectively taking the values of the current components Icd and Icq after omega L (angular frequency multiplied by inductance) operation as DQ vector decoupling values, and obtaining a driving voltage V alpha for generating a PWM driving signal after carrying out iPark inverse transformation on two groups of voltage values output by the voltage loop by the controller; controlling an inverter control circuit by taking an input current reference value icd to a current loop of a control controller as an instruction, and inverting from direct current to alternating current when the current reference value icd is larger than 0 in the input instruction; when icd is less than 0, alternating current is converted into direct current, so that bidirectional seamless switching between alternating current and direct current can be realized; and the reactive current output of the control system can be carried out through the input current reference value icq. Where icd and icq are the two components of the control current in DQ coordinates.
In the inversion control method of the single-phase bidirectional inversion control circuit, during control, when the positive half cycle of the alternating current side is reached, the controller controls the first switching tube and the fourth switching tube to be alternately switched on and off with the sixth switching tube; the second switching tube and the third switching tube are normally closed, and the fifth switching tube is normally open; when the alternating current side is in a negative half cycle, the controller controls the second switching tube and the third switching tube to be alternately switched on and off with the fifth switching tube; the first switch tube and the fourth switch tube are normally closed, and the sixth switch tube is normally open.
Compared with the prior art, the invention adds the switch tube for switching the follow current loop on the basis of the full-bridge inverter circuit, and reasonably distributes the driving mode of each switch tube, so that the bidirectional inversion can be realized under a more simplified structure, and the structure has smaller leakage current and higher conversion efficiency; meanwhile, the invention carries out vector control by matching with the mode of transforming and inversely transforming the acquired inductive current and the AC source voltage in a D-Q coordinate system, realizes the seamless switching of the bidirectional current and can carry out decoupling control on active power and reactive power.
Drawings
FIG. 1 is a schematic diagram of the circuit configuration of the present invention;
FIG. 2 is a schematic diagram of the control principle of the present invention;
FIG. 3 is a schematic diagram of the positive half cycle equivalent circuit from DC to AC;
FIG. 4 is a schematic diagram of a negative half cycle equivalent circuit for DC to AC;
FIG. 5 is a schematic diagram of the effective circuit principle of the positive half cycle of AC to DC;
FIG. 6 is a schematic diagram of the effective circuit principle of the negative half cycle of AC to DC;
fig. 7 is a schematic diagram of the driving signal of the switching tube.
Detailed Description
The invention is further illustrated by the following figures and examples, which are not to be construed as limiting the invention.
Examples are given. A single-phase bidirectional inverter control circuit, as shown in fig. 1: the direct current power supply comprises a capacitor C1 connected to a direct current end interface, wherein a first branch formed by connecting a first diode DA and a second diode DB in series is connected to the capacitor C1 in parallel, and a second branch formed by connecting a third diode DC and a fourth diode DD in series is also connected to the first branch in parallel; the diode connection node of the first branch and the diode connection node of the second branch are connected to the alternating current terminal interface through a first inductor L1 and a second inductor L2 respectively; a fifth diode DE and a sixth diode DF which are connected in parallel and have opposite directions are further connected between the diode connecting node of the first branch and the diode connecting node of the second branch, and a fifth switching tube E and a sixth switching tube F are respectively connected in series on the fifth diode DE and the sixth diode DF; the anodes of the first diode DA, the second diode DB, the third diode DC and the fourth diode DD point to the same end of the DC end interface, and a first switch tube A, a second switch tube B, a third switch tube C and a fourth switch tube D are respectively connected in parallel on each diode; the first switching tube A, the second switching tube B, the third switching tube C, the fourth switching tube D, the fifth switching tube E and the sixth switching tube F are connected to a controller to be driven, wherein the first switching tube A and the fourth switching tube D use the same driving signal, and the sixth switching tube F and the first switching tube A use a group of complementary driving signals; the second switch tube B and the third switch tube C use the same driving signal, and the fifth switch tube E and the second switch tube B use a group of complementary driving signals.
The principle of the inversion control method using the single-phase bidirectional inversion control circuit is shown in fig. 2, and the inversion control method comprises the following steps: firstly, conducting Park transformation on sampled inductive current and AC source voltage at an AC end and 90-degree orthogonal quantity generated by the controller, obtaining current components Icd and Icq and voltage components Vcd and Vcq under a D-Q coordinate system, respectively taking the current components Icd and Icq as feedback values of a current loop of the controller, respectively taking the voltage components Vcd and Vcq as feedforward values, simultaneously respectively taking the values of the current components Icd and Icq after omega L operation as DQ vector control decoupling, and obtaining driving voltage V alpha for generating PWM driving signals after carrying out iPark inverse transformation on two groups of voltage values output by the voltage loop by the controller; controlling the inverter control circuit by taking an input current reference value icd to a current loop of the control controller as an instruction, and converting direct current into alternating current when the current reference value icd is greater than 0 in the input instruction; when icd is less than 0, alternating current is converted into direct current, so that bidirectional seamless switching between alternating current and direct current can be realized; and the reactive current output of the control system can be carried out through the input current reference value icq.
The specific principle is as follows (taking the storage battery to discharge the commercial power and the commercial power to charge the storage battery as an example):
and in the inverter part, assuming that Vs is mains voltage, Vc is inverter output voltage, the equivalent inductance and resistance are L and R, and the angular frequency is omega. In the α β coordinate, a variable orthogonal to the mains voltage is virtualized, and the variable and the mains voltage are combined into a mains voltage vector Vs, which rotates in the α β coordinate. And under a DQ coordinate, selecting a DQ coordinate system reference direction, wherein the d axis is superposed with the commercial power voltage vector, the d axis represents an active component, and the q axis represents a reactive component.
Corresponding to the park transform:
corresponding to inverse park transformation:
therefore, it is not only easy to use
Since the mains Vq =0,
then
Because of the existence of reactive power, an included angle theta exists between the inversion output voltage and the power grid, if Vc is decomposed to a DQ coordinate axis, the Vc is divided into a plurality of groups
Similarly, the current can also be written as
According to voltageTabulatable equation
Then it can be obtained from the above equation
The equations for obtaining the decoupled DQ coordinates are respectively
Namely:
is subjected to Las transformation, and
and
as a feed forward, find a transfer function of
With Vcd and Vcq, the inversion output voltage can be obtained through inverse transformation
And the output can be finished by PWM modulation.
The specific working process of the invention is as follows:
when the direct current is required to be output to the alternating current, the direct current is discharged from the C1 to the alternating current side AC, and the circuit works in a buck circuit mode.
In the positive half cycle on the AC side, the current direction is as shown in fig. 3, and the switch tube control signal is as shown by the dashed frame portion of fig. 7: when A and D are switched on, F is switched off, and a current loop is a solid line part; when A and D are closed, F is open, and the current loop is a dotted line part; positive half cycle, B, C are normally closed, E is normally open.
In the negative half cycle of AC, the current direction is shown in fig. 4, and the switch tube control signal is shown in the solid frame portion of fig. 7: when B and C are switched on, E is closed, and a current loop is a solid line part; when B and C are closed, E is open, and the current loop is a dotted line part; in the negative half cycle, A and D are normally closed, and F is normally open;
when the commercial power (alternating current) needs to be converted into direct current, the charging is carried out from the AC to the C1, and the circuit works in a Boost circuit mode.
In the positive AC half cycle, the current direction is shown in fig. 5, and the switch tube control signal is shown in the portion with the dashed frame in fig. 7: when F is switched on, A and D are closed, and a current loop is a solid line part; when F is closed, A and D are open, and the current loop is a dotted line part; positive half cycle, B, C are normally closed, E is normally open.
In the negative half cycle of AC, the current direction is shown in fig. 6, and the switch tube control signal is shown in the solid frame portion of fig. 7: when E is switched on, B and C are switched off, and a current loop is a solid line part; when E is closed, B and C are open, and a current loop is a dotted line part; in the negative half cycle, A and D are normally closed, and F is normally open.
Claims (3)
1. The utility model provides a single-phase two-way contravariant control circuit which characterized in that: the direct current power supply comprises a capacitor (C1) connected to a direct current end interface, wherein a first branch formed by connecting a first Diode (DA) and a second Diode (DB) in series is connected to the capacitor (C1) in parallel, and a second branch formed by connecting a third Diode (DC) and a fourth diode (DD) in series is also connected to the first branch in parallel; the diode connection node of the first branch and the diode connection node of the second branch are connected to the alternating current terminal interface through a first inductor (L1) and a second inductor (L2), respectively; a fifth Diode (DE) and a sixth Diode (DF) which are connected in parallel and have opposite directions are further connected between the diode connection node of the first branch and the diode connection node of the second branch, and a fifth switching tube (E) and a sixth switching tube (F) are respectively connected in series on the fifth Diode (DE) and the sixth Diode (DF); anodes of the first Diode (DA), the second Diode (DB), the third Diode (DC) and the fourth diode (DD) point to the same end of the direct current end interface, and a first switch tube (A), a second switch tube (B), a third switch tube (C) and a fourth switch tube (D) are respectively connected in parallel on each diode; the first switching tube (A), the second switching tube (B), the third switching tube (C), the fourth switching tube (D), the fifth switching tube (E) and the sixth switching tube (F) are connected to the controller to be driven, wherein the first switching tube (A) and the fourth switching tube (D) use the same driving signal, and the sixth switching tube (F) and the first switching tube (A) use a group of complementary driving signals; the second switch tube (B) and the third switch tube (C) use the same driving signal, and the fifth switch tube (E) and the second switch tube (B) use a group of complementary driving signals.
2. The inversion control method using the single-phase bidirectional inversion control circuit of claim 1, characterized by comprising the steps of: firstly, conducting Park transformation on sampled inductive current and AC source voltage at an AC end and 90-degree orthogonal quantity generated by the controller to obtain current components Icd and Icq and voltage components Vcd and Vcq under a D-Q coordinate system, respectively taking the current components Icd and Icq as feedback values of a current loop of the controller, respectively taking the voltage components Vcd and Vcq as feedforward values of the controller, simultaneously respectively taking values obtained by multiplying the current components Icd and Icq by omega L as DQ vector decoupling values, and obtaining driving voltage V alpha for generating PWM driving signals by the controller after carrying out iPark inverse transformation on two groups of output voltage values; controlling the inverter control circuit by taking an input current reference value icd to a current loop of the control controller as an instruction, and converting direct current into alternating current when the current reference value icd is greater than 0 in the input instruction; when icd is less than 0, alternating current is converted into direct current, so that bidirectional seamless switching between alternating current and direct current can be realized; and the reactive current output of the control system can be carried out through the input current reference value icq.
3. The inversion control method of the single-phase bidirectional inversion control circuit according to claim 2, characterized in that: during conversion control, the controller controls the first switching tube (A) and the fourth switching tube (D) to be alternately switched on and off with the sixth switching tube (F) in the positive half cycle of the alternating current side; the second switching tube (B) and the third switching tube (C) are normally closed, and the fifth switching tube (E) is normally open; when the alternating current side is in a negative half cycle, the controller controls the second switching tube (B) and the third switching tube (E) to be alternately switched on and off with the fifth switching tube (E); the first switch tube (A) and the fourth switch tube (D) are normally closed, and the sixth switch tube (F) is normally open.
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| CN104934989A (en) * | 2015-07-09 | 2015-09-23 | 哈尔滨理工大学 | Reactive power compensation device based on novel modular multilevel topology and control method thereof |
| CN205647288U (en) * | 2016-04-29 | 2016-10-12 | 三峡大学 | Non - isolated form photovoltaic grid -connected inverter |
| CN108631639A (en) * | 2017-03-17 | 2018-10-09 | 深圳耐斯特思新能源科技有限公司 | Two-way DC-AC translation circuits for energy storage inverter |
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2020
- 2020-10-22 CN CN202011138283.8A patent/CN112019082A/en active Pending
Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104934989A (en) * | 2015-07-09 | 2015-09-23 | 哈尔滨理工大学 | Reactive power compensation device based on novel modular multilevel topology and control method thereof |
| CN205647288U (en) * | 2016-04-29 | 2016-10-12 | 三峡大学 | Non - isolated form photovoltaic grid -connected inverter |
| CN108631639A (en) * | 2017-03-17 | 2018-10-09 | 深圳耐斯特思新能源科技有限公司 | Two-way DC-AC translation circuits for energy storage inverter |
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Application publication date: 20201201 |