CN111753413B - Electromagnetic transient equivalent modeling method and system for hybrid brake resistor converter - Google Patents
Electromagnetic transient equivalent modeling method and system for hybrid brake resistor converter Download PDFInfo
- Publication number
- CN111753413B CN111753413B CN202010541409.XA CN202010541409A CN111753413B CN 111753413 B CN111753413 B CN 111753413B CN 202010541409 A CN202010541409 A CN 202010541409A CN 111753413 B CN111753413 B CN 111753413B
- Authority
- CN
- China
- Prior art keywords
- equivalent
- sub
- igbt
- module
- converter
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
- 238000000034 method Methods 0.000 title claims abstract description 49
- 230000001052 transient effect Effects 0.000 title claims abstract description 44
- 238000004088 simulation Methods 0.000 claims abstract description 40
- 230000008569 process Effects 0.000 claims abstract description 10
- 239000003990 capacitor Substances 0.000 claims description 22
- 230000014509 gene expression Effects 0.000 claims description 18
- 238000004364 calculation method Methods 0.000 claims description 14
- 238000004458 analytical method Methods 0.000 claims description 12
- 125000004122 cyclic group Chemical group 0.000 claims description 4
- 230000009191 jumping Effects 0.000 claims description 3
- 238000010586 diagram Methods 0.000 description 18
- 238000004590 computer program Methods 0.000 description 7
- 230000006870 function Effects 0.000 description 4
- 238000012545 processing Methods 0.000 description 4
- 230000010354 integration Effects 0.000 description 3
- 238000003860 storage Methods 0.000 description 3
- 101100499229 Mus musculus Dhrsx gene Proteins 0.000 description 2
- 230000004075 alteration Effects 0.000 description 1
- 230000005540 biological transmission Effects 0.000 description 1
- 230000008859 change Effects 0.000 description 1
- 238000010276 construction Methods 0.000 description 1
- 238000005520 cutting process Methods 0.000 description 1
- 238000013461 design Methods 0.000 description 1
- 238000011161 development Methods 0.000 description 1
- 238000005265 energy consumption Methods 0.000 description 1
- 238000012423 maintenance Methods 0.000 description 1
- 238000004519 manufacturing process Methods 0.000 description 1
- 238000012986 modification Methods 0.000 description 1
- 230000004048 modification Effects 0.000 description 1
- 230000003287 optical effect Effects 0.000 description 1
- 238000006467 substitution reaction Methods 0.000 description 1
- 239000002699 waste material Substances 0.000 description 1
Classifications
-
- G—PHYSICS
- G06—COMPUTING; CALCULATING OR COUNTING
- G06F—ELECTRIC DIGITAL DATA PROCESSING
- G06F30/00—Computer-aided design [CAD]
- G06F30/20—Design optimisation, verification or simulation
-
- G—PHYSICS
- G06—COMPUTING; CALCULATING OR COUNTING
- G06F—ELECTRIC DIGITAL DATA PROCESSING
- G06F2113/00—Details relating to the application field
- G06F2113/06—Wind turbines or wind farms
Landscapes
- Engineering & Computer Science (AREA)
- Physics & Mathematics (AREA)
- Theoretical Computer Science (AREA)
- Computer Hardware Design (AREA)
- Evolutionary Computation (AREA)
- Geometry (AREA)
- General Engineering & Computer Science (AREA)
- General Physics & Mathematics (AREA)
- Inverter Devices (AREA)
Abstract
The invention relates to an electromagnetic transient equivalent modeling method and system of a hybrid brake resistor converter, comprising the following steps: 1) Analyzing the sub-module topological structure of the hybrid brake resistor converter, and carrying out equivalent modeling on each main element in the sub-module; 2) Analyzing the running state of the mixed braking resistor converter submodule in the running process, and obtaining the Thevenin equivalent circuits of the submodules in different states based on the equivalent model of each main element in the step 1), so as to obtain the branch Thevenin equivalent circuits of the mixed braking resistor converter; 3) Substituting the branch Thevenin equivalent circuit of the hybrid braking resistor converter into a flexible direct system network to solve, and obtaining a system electromagnetic transient simulation result containing the hybrid braking resistor converter. The invention can be widely applied to the field of electromagnetic transient simulation of hybrid brake resistor converters.
Description
Technical Field
The invention relates to the technical field of electromagnetic transient simulation of offshore wind power sent out by a flexible-straight system, in particular to an electromagnetic transient equivalent modeling method and an electromagnetic transient equivalent modeling system for a hybrid brake resistance converter of offshore wind power sent out by the flexible-straight system.
Background
In the offshore wind power soft direct-delivery system, a delivery end converter station needs to adopt constant alternating voltage and constant frequency control to provide reliable grid-connected voltage for an offshore wind power plant, so that the active power input into the soft direct-delivery system cannot be directly controlled by the soft direct-delivery converter station. When the power transmission capability of the wind power plant is reduced due to the failure of the flexible and straight system, if the wind power plant continuously feeds in power, the power balance of the wind power plant entering and exiting the flexible and straight system is broken, the problem of surplus power is generated, and the time for cutting off the wind power plant by utilizing the safety control device cannot be matched with the development speed of voltage and current under the condition of surplus power. Surplus power is accumulated in the flexible direct current system, so that the direct current voltage of the system is quickly increased, overvoltage and overcurrent stress of system equipment can be broken through, a converter valve is blocked, the flexible direct current system is stopped, and meanwhile, the grid-connected voltage of a wind power plant is fluctuated in a connecting mode, so that the wind power plant is disconnected in a large area, larger impact is generated on a power grid, and serious economic loss is caused. It is therefore necessary to introduce devices such as braking resistor converters, which are flexibly controllable in power.
Because of the shortage of offshore platform area and difficult operation and maintenance, the brake resistor converter is not suitable to be arranged on the alternating current side of the offshore end-transmitting converter station, but is arranged on the direct current side of the land end-receiving converter station, and according to the operation characteristics of the power electronic device and the brake resistor, the brake resistor converter can be divided into three technical routes of centralized type, distributed type and mixed type, and the submodules of each technical route can be further divided into various topological structures. When electromagnetic transient simulation analysis of the offshore wind power through the soft direct delivery system is carried out, the partial braking resistance converter can be directly equivalent by adopting an existing single IGBT device model or an MMC half-bridge submodule integrated model in a power system transient simulation software PSCAD/EMTDC element library. However, the hybrid braking resistor converter adopts a brand-new sub-module topology structure, and although a single sub-module topology can be built by using existing element modules such as an IGBT, a diode, a capacitor, a resistor and the like, the hybrid braking resistor converter in an actual flexible direct system usually comprises hundreds of sub-modules, and trigger instructions of IGBT devices in all the sub-modules are inconsistent, so that the single sub-module topology structure cannot be used for equivalence; if hundreds of sub-module topologies are manually built in the PSCAD/EMTDC, huge time and effort are required, the simulation model interface is not clear and clear at a glance, the signal interface is easy to make mistakes, more importantly, too many element modules occupy too much memory, the operation speed of the PSCAD/EMTDC is seriously influenced, and even the flexible-direct system simulation model cannot operate.
Disclosure of Invention
Aiming at the problems, the invention aims to provide an electromagnetic transient equivalent modeling method and an electromagnetic transient equivalent modeling system for a hybrid brake resistor converter, which are based on the running states of IGBT T1 and IGBT T2 in each sub-module of the hybrid brake resistor converter, convert the sub-module topological structures with different states into corresponding simplified equivalent circuits, further obtain the Thevenin equivalent circuit of the full branch of the hybrid brake resistor converter, and provide a practical, efficient, clear, simple and feasible electromagnetic transient equivalent modeling method for the hybrid brake resistor converter adopting the novel sub-module topological structure.
In order to achieve the above purpose, the present invention adopts the following technical scheme:
In a first aspect of the present invention, an electromagnetic transient equivalent modeling method for a hybrid brake resistor converter is provided, which includes the following steps:
1) Analyzing the sub-module topological structure of the hybrid brake resistor converter, and carrying out equivalent modeling on each main element in the sub-module;
2) Analyzing the operation state of the sub-module of the hybrid brake resistor converter in the operation process, and obtaining the Thevenin equivalent circuit of the sub-module in different operation states based on the equivalent model of each main element in the step 1), so as to obtain the branch Thevenin equivalent circuit of the hybrid brake resistor converter;
3) Substituting the branch Thevenin equivalent circuit of the hybrid braking resistor converter into a flexible direct system network to solve, and obtaining a system electromagnetic transient simulation result containing the hybrid braking resistor converter.
Further, in the step 1), the method for equivalently modeling each main element in the sub-module of the hybrid brake resistor converter includes the following steps:
1.1 Analyzing the topological structure of a sub-module of the hybrid brake resistor converter to obtain main elements contained in the sub-module, wherein the main elements comprise a first IGBT, a second IGBT, a diode, a capacitor, a voltage-sharing resistor and a voltage-limiting resistor element;
1.2 The equivalent resistance of the IGBT and the anti-parallel diode thereof in the on state and the off state is analyzed, and the IGBT and the anti-parallel diode thereof are equivalent to a variable resistor controlled by an IGBT trigger instruction;
1.3 The equivalent resistance of the diode in the conducting state and the clamping state is analyzed, and the diode is equivalent to a variable resistance controlled by the running state;
1.4 Equivalent analysis is performed on the capacitor, and the capacitor is equivalent to a Thevenin equivalent circuit formed by serially connecting an equivalent historical voltage source v CEQ (T-delta T) with an equivalent resistor r CEQ.
Further, in the step 1.2), the equivalent of the IGBT and the anti-parallel diode thereof as the variable resistor controlled by the IGBT trigger instruction means that:
When the trigger instruction is 1, the IGBT is conducted and is equivalent to a resistor with the resistance value of 0.01 omega;
When the trigger instruction is 0, the IGBT is turned off, and the trigger instruction is equivalent to an open circuit state;
in the step 1.3), the equivalent of the diode as a variable resistor controlled by the operation state means that:
When the diode is in a conducting state, the diode is equivalent to a resistor with the resistance value of 0.01 omega;
when the diode is in the clamped state, it is equivalent to an open state.
Further, in the step 1.4), the calculation formulas of the equivalent historical voltage source v CEQ (T- Δt) and the equivalent resistor r CEQ of the capacitor are respectively:
Wherein, delta T is the simulation step length; c is the capacitance of the submodule; i C (T- Δt) is the submodule capacitance history current; v C (T-DeltaT) is the voltage across the capacitance histories of the submodules.
Further, in the step 2), the method for obtaining the branch davin equivalent circuit of the hybrid braking resistor converter includes the following steps:
2.1 Based on the equivalent model of each main element in the sub-module of the hybrid brake resistor converter obtained in the step 1), the sub-module topological structure of the hybrid brake resistor converter is equivalent to a form that the resistor and the voltage source are connected in series and parallel;
2.2 The trigger instructions of the first IGBT and the second IGBT in the sub-module are arranged and combined to obtain the running state of the sub-module of the hybrid brake resistor converter;
2.3 Further simplifying equivalent analysis of each sub-module in the hybrid brake resistor converter under different running states, and calculating to obtain port voltage v SM and capacitance current i C (t) of each sub-module;
2.4 Based on the number of sub-modules turned on by the first IGBT in the hybrid braking resistor converter and the port voltages v SM of the sub-modules in different operation states in step 2.3), the hybrid braking resistor converter is equivalent to a branch davin equivalent circuit composed of a branch history voltage source v armEQ (T- Δt) and a branch equivalent resistor r armEQ connected in series.
Further, in the step 2.2), the arrangement and combination of the trigger command FT1 of the first IGBT and the trigger command FT2 of the second IGBT in the submodule to obtain the running state of the submodule of the hybrid braking resistor converter includes:
① Operating state 1: FT1 = 1 and FT2 = 1, the first IGBT and the second IGBT are both on, the diode is in clamping state;
② Operating state 2: FT1 = 1 and FT2 = 0, the first IGBT is on, the second IGBT is off, the diode is in clamping state;
③ Operating state 3: FT1 = 0 and FT2 = 1, the first IGBT turns off, the second IGBT turns on, the diode is in the on state;
④ Operating state 4: FT1 = 0 and FT2 = 0, and first IGBT and second IGBT all turn off, and the diode is in the on state.
Further, in the step 2.3), the calculation formulas of the port voltage v SM and the capacitance current i C (t) of each sub-module in different operation states in the hybrid braking resistor converter are respectively:
① Operating state 1
The expressions of the port voltage and the capacitance current of the sub-module are respectively:
vSM_1(t)＝0.01Ω·iarm(t)，
Wherein v SM_1 (t) is the port voltage of the submodule in the running state 1 and the running state 2; i C_1 (t) is the capacitive current of the run state 1 and run state 2 sub-modules; r CEQ is the capacitance equivalent resistance, and DeltaT is the simulation step size; t is time; r SEQ is a simplified equivalent resistance, and its expression is:
rSEQ＝(rloss+0.01Ω)//rJ，
wherein r loss is a limiting resistor; r J is a equalizing resistor;
② Operating state 2
The expression of the port voltage and the capacitance current of the sub-module is the same as the operation state 1, and the expression of the simplified equivalent resistor r SEQ at the moment is as follows:
rSEQ＝rJ，
③ Run state 3
The expressions of the port voltage and the capacitance current of the sub-module are respectively:
vSM_2(t)＝rO·iarm(t)+vOC(t-ΔT)，
Wherein v SM_2 (t) is the port voltage of the submodule in the running state 3 and the running state 4; i C_2 (t) is the capacitive current of the run state 1 and run state 2 sub-modules; at this time, the expression of the reduced equivalent resistance r SEQ is:
rSEQ＝(rloss+0.01Ω)//rJ，
④ Operating state 4
The expression of the port voltage and the capacitance current of the sub-module is the same as the running state 3, and at this time, the expression of the simplified equivalent resistor r SEQ is as follows:
rSEQ＝rJ。
Further, in the step 2.4), the calculation formulas of the branch history voltage source v armEQ (T- Δt) and the branch equivalent resistance r armEQ of the branch davin equivalent circuit are respectively:
Wherein n is the number of submodules conducted by the first IGBT in the hybrid brake resistor converter; n is the total number of submodules in the hybrid brake resistor converter; r O,y is the equivalent resistance of the y-th sub-module; r m is a brake resistor; v OC,y (T- Δt) is the equivalent historical voltage source of the y-th sub-module.
Further, in the step 3), the method for solving by substituting the branch davin equivalent circuit of the hybrid braking resistor converter into the flexible-direct system network includes the following steps:
3.1 Initializing data: assuming that a submodule capacitance current i C (0) =0, an initial time submodule capacitance end voltage v C(0)＝UdcN/N, an initial time variable t=Δt, the number n=0 of submodules turned on by the first IGBT at the initial time, and a circulation variable i, j, k=0 in the hybrid braking resistor converter, wherein U dcN is a rated direct current voltage;
3.2 According to the current time sub-module capacitance current and the capacitance equivalent model, calculating an equivalent historical voltage source v CEQ (T-delta T) and a capacitance equivalent resistance r CEQ of the sub-module capacitance of the hybrid brake resistor converter;
3.3 Circularly calculating the sub-modules based on the conduction condition of the second IGBT in the sub-modules to obtain simplified equivalent resistance r SEQ of each sub-module;
3.4 Based on the conduction condition of the first IGBT in the sub-module), performing a cyclic calculation on the sub-module: if the first IGBT is conducted, updating the number of sub-modules conducted by the first IGBT, wherein n=n+1; if the first IGBT is turned off, calculating an equivalent historical voltage source v OC (T-delta T) of the submodule and an equivalent resistance r O of the submodule;
3.5 According to the number of sub-modules conducted by the first IGBT and the equivalent historic voltage sources and the equivalent resistances of the sub-modules, calculating a branch equivalent historic voltage source v armEQ (T-delta T) and a branch equivalent resistance r armEQ;
3.6 A branch Thevenin equivalent circuit formed by serially connecting a branch equivalent historical voltage source v armEQ (T-delta T) and a branch equivalent resistor r armEQ is used for replacing a hybrid braking resistor converter, and is substituted into a flexible direct system network to be solved by using an EMTDC simulation tool, so that a branch current i arm (T) is obtained;
3.7 Circularly calculating the submodule based on the conduction condition of the first IGBT in the submodule to obtain a submodule capacitance current i C (t), and calculating the voltage v C (t) between the submodule capacitance ends based on the submodule capacitance current i C (t);
3.8 Updating the time variable t=t+Δt, jumping to step 3.2) to start the simulation calculation of the next simulation time until the simulation end time is reached.
In a second aspect of the present invention, there is provided an electromagnetic transient equivalent modeling system of a hybrid brake resistor converter, comprising: the element equivalent module is used for analyzing the topological structure of the submodule of the hybrid brake resistor converter and carrying out equivalent modeling on each main element in the submodule; the circuit equivalent module is used for analyzing the operation state of the mixed braking resistor converter submodule in the operation process, obtaining the Thevenin equivalent circuit of the submodule in different operation states based on the equivalent model of each main element, and further obtaining the branch Thevenin equivalent circuit of the mixed braking resistor converter; and the electromagnetic transient simulation module is used for substituting the branch Thevenin equivalent circuit of the hybrid brake resistor converter into the flexible-direct system network to solve so as to obtain a system electromagnetic transient simulation result containing the hybrid brake resistor converter.
Due to the adoption of the technical scheme, the invention has the following advantages: 1. the invention converts the IGBT and the diode in the sub-module of the hybrid brake resistor converter into a variable resistor based on the running states of two IGBTs in each sub-module of the hybrid brake resistor converter, and simultaneously converts the capacitor in the sub-module into a Thevenin equivalent circuit consisting of a capacitor equivalent historical voltage source and a capacitor equivalent resistor by using a trapezoidal integration method, thereby respectively converting the topological structures of the sub-modules in different running states into different simplified equivalent circuits, and facilitating the subsequent modeling of the sub-modules. 2. The invention provides a practical, efficient, clear, simple and feasible electromagnetic transient equivalent modeling method for the hybrid brake resistor converter adopting a brand-new submodule topological structure, can effectively avoid the problems of time and labor waste, complexity and error and serious influence on simulation speed and the like caused by manually constructing hundreds of submodule actual models, and has great practical value and wide application prospect in actual scenes such as offshore wind power output through a flexible and straight system.
Drawings
FIG. 1 is a schematic diagram of a sub-module topology of a hybrid brake resistor converter for which the present invention is directed;
FIG. 2 is a sub-module equivalent circuit diagram of a hybrid brake resistor converter in accordance with the present invention;
fig. 3 is an equivalent circuit diagram of a submodule in the present invention when FT1 = 1 and FT2 = 1;
Fig. 4 is an equivalent circuit diagram of a submodule when FT1 = 1 and FT2 = 0 in the present invention;
fig. 5 is an equivalent circuit diagram of a submodule in the case of FT 1=0 and FT 2=1 in the present invention;
Fig. 6 is an equivalent circuit diagram of a submodule in the present invention when FT1 = 0 and FT2 = 0;
Fig. 7 is a simplified equivalent circuit diagram of a submodule when FT1 = 1 in the present invention;
fig. 8 is a simplified equivalent circuit diagram of a submodule when FT1 = 0 in the present invention;
FIG. 9 is a flow chart of electromagnetic transient simulation calculation of the hybrid brake resistor converter provided by the invention;
FIG. 10 is a graph of DC voltage versus branch current waveforms for a manual construction of a hybrid brake resistor converter actual model in an embodiment of the present invention;
fig. 11 is a graph of dc voltage versus branch current waveforms using a method of electromagnetic transient equivalent modeling of a hybrid brake resistor converter in an embodiment of the present invention.
Detailed Description
The present invention will be described in detail with reference to the accompanying drawings and examples.
The invention provides an electromagnetic transient equivalent modeling method of a hybrid brake resistor converter, which comprises the steps of firstly converting IGBT and diode in a sub-module of the hybrid brake resistor converter into a variable resistor based on the running states of IGBT T1 and IGBT T2 in each sub-module of the hybrid brake resistor converter, and simultaneously converting a capacitor in the sub-module into a Thevenin equivalent circuit consisting of a capacitor equivalent historical voltage source and a capacitor equivalent resistor by using a trapezoidal integration method, so that the topological structure of the sub-module is converted into a simplified equivalent circuit; secondly, solving a simplified equivalent circuit of each sub-module to obtain a sub-module equivalent historical voltage source and a sub-module equivalent resistance; and finally, converting the hybrid braking resistor converter into a Thevenin equivalent circuit consisting of a branch equivalent historical voltage source and a branch equivalent resistor which are connected in series, substituting the Thevenin equivalent circuit into a flexible direct system network to obtain branch current, and further reversely pushing the voltage between the capacitance current of the submodule and the capacitance end of the submodule, thereby obtaining the capacitance historical voltage source of the submodule at the next simulation moment, and the like. Specifically, the method comprises the following steps:
1) Analyzing the topological structure of each sub-module in the hybrid brake resistor converter, and carrying out equivalent modeling on each main element in the sub-module;
2) Analyzing the operation state of the sub-module of the hybrid brake resistor converter in the operation process, and obtaining the Thevenin equivalent circuit of the sub-module in different operation states based on the equivalent model of each main element in the step 1), so as to obtain the branch Thevenin equivalent circuit of the hybrid brake resistor converter;
3) Substituting the branch Thevenin equivalent circuit of the hybrid braking resistor converter into a flexible direct system network to solve, and obtaining a system electromagnetic transient simulation result containing the hybrid braking resistor converter.
In the step 1), the method for analyzing the topology structure of each sub-module in the hybrid braking resistor converter and performing equivalent modeling on each main element in the sub-module comprises the following steps:
1.1 As shown in fig. 1, the sub-module topology structure of the hybrid braking resistor converter is analyzed to obtain main elements included in the sub-module, including elements such as an IGBT T1, an IGBT T2, a diode D, a capacitor C, a equalizing resistor r J, a voltage limiting resistor r loss, and the like.
1.2 The equivalent resistance of the IGBT and the anti-parallel diode thereof in the on state and the off state is analyzed, and the IGBT and the anti-parallel diode thereof are equivalent to a variable resistor controlled by an IGBT trigger instruction according to an analysis result.
The IGBT and the anti-parallel diode thereof can be equivalently used as a variable resistor controlled by an IGBT trigger instruction, when the trigger instruction is 1, the IGBT is conducted, and can be equivalently used as a resistor with smaller resistance value, and the resistance is usually 0.01Ω; when the trigger instruction is 0, the IGBT is turned off, and can be equivalently a resistor with a larger resistance value, and can be equivalently an open circuit state for simplifying analysis.
1.3 The equivalent resistance of the diode in the conducting state and the clamping state is analyzed, and the diode is equivalent to a variable resistance controlled by the running state according to the analysis result.
The diode can be equivalently a variable resistor controlled by an operation state, and can be equivalently a resistor with smaller resistance value when the diode is in a conducting state, and the resistor is usually 0.01Ω; when the diode is in a clamping state, the diode can be equivalent to a resistor with a larger resistance value, and can be equivalent to an open circuit state for simplifying analysis.
1.4 Equivalent analysis of the capacitance and equivalent of the capacitance as a Thevenin equivalent circuit consisting of a historical voltage source v CEQ (T-DeltaT) in series with a resistor r CEQ.
The capacitor can be equivalently used as a Thevenin equivalent circuit formed by serially connecting a historical voltage source v CEQ (T-delta T) with a resistor r CEQ by using a trapezoidal integration method.
The relationship between the voltage between the capacitance ends of the submodule and the capacitance current of the submodule is as follows:
Wherein, C is the capacitance of the submodule; i C (t) is the submodule capacitance current; v C (t) is the voltage between the capacitance ends of the submodules; v C (T-DeltaT) is the voltage between the historic ends of the capacitors of the submodules; delta T is the simulation step length; i C (T- Δt) is the submodule capacitance history current.
The equivalent resistance r CE Q of the submodule capacitor and the equivalent historical voltage source v CEQ (T-delta T) are respectively:
In the above step 2), the method for obtaining the branch davin equivalent circuit of the hybrid braking resistor converter comprises the following steps:
2.1 As shown in fig. 2, based on the equivalent model of each main element in the sub-module of the hybrid braking resistor converter obtained in the step 1), the sub-module topology structure of the hybrid braking resistor converter is equivalent to a form that the resistor and the voltage source are connected in series and parallel.
The resistor r T1、rT2 is the equivalent variable resistor of the IGBT T1, the IGBT T2 and the anti-parallel diode thereof respectively; resistor r D is the equivalent variable resistance of diode D; i arm is the current through the hybrid brake resistor converter branch; v SM is the submodule port voltage.
2.2 The trigger instructions of the IGBT T1 and the IGBT T2 in the sub-modules are arranged and combined to obtain the running state of the sub-modules of the hybrid brake resistor converter.
In the operation process, the trigger instruction FT1 of the IGBT T1 and the trigger instruction FT2 of the IGBT T2 in the sub-module are mutually independent, so that the following 4 operation states can be obtained according to the arrangement and combination of the trigger instructions:
① Operating state 1:
as shown in fig. 3, FT1 = 1 and FT2 = 1, IGBT T1 and IGBT T2 are on, and diode D is in the clamped state;
② Operating state 2:
As shown in fig. 4, FT1 = 1 and FT2 = 0, IGBT T1 is on and IGBT T2 is off, diode D is in the clamped state;
③ Operating state 3:
As shown in fig. 5, FT1 = 0 and FT2 = 1, IGBT T1 is off and IGBT T2 is on, diode D is in the on state;
④ Operating state 4:
as shown in fig. 6, FT1 = 0 and FT2 = 0, IGBT T1 and IGBT T2 are off, and diode D is on.
2.3 Further simplifying equivalent analysis of each sub-module in different running states in the hybrid brake resistor converter, and calculating to obtain port voltage v SM and capacitance current i C (t) of each sub-module.
① Operating state 1
As shown in fig. 7, since the diode D can be equivalently in an open state in the operating state 1, the submodule circuit diagram can be further simplified into two independent equivalent circuits, which are solved respectively below.
At this time, the expression of the port voltage v SM of the submodule is as follows:
vSM_1(t)＝0.01Ω·iarm(t) (4)
Where i arm (t) is the current through the hybrid braking resistor converter branch.
The submodule capacitor is in a discharge state, and based on the historical voltage source v CEQ (T-delta T) of the submodule capacitor, the capacitance current i C (T) can be obtained as follows:
Where r CEQ is the equivalent resistance of the submodule capacitor and r SEQ is the simplified equivalent resistance.
The simplified equivalent resistance r SEQ is:
rSEQ＝(rloss+0.01Ω)//rJ (6)
Wherein, r loss is a limiting resistor; and r J is a voltage equalizing resistor.
② Operating state 2
As shown in fig. 7, since the diode can be equivalently opened in the operating state 2, the circuit diagram of the submodule can be further simplified into two independent equivalent circuits, and the port voltage v SM and the capacitance current i C (t) of the submodule are the same as those in the operating state 1, except that the simplified equivalent resistor r SEQ is provided in the operating state 2:
rSEQ＝rJ (7)
③ Run state 3
As shown in fig. 8, since the IGBT T1 in the running state 3 can be equivalently an open state, the submodule circuit diagram can be further simplified into a submodule davien equivalent circuit formed by connecting the submodule equivalent historical voltage source v OC (T- Δt) and the submodule equivalent resistor r O in series, and the expression is as follows:
rO＝rCEQ//rSEQ+0.01Ω (8)
In the formula, the simplified equivalent resistance r SEQ is:
rSEQ＝(rloss+0.01Ω)//rJ (10)
At this time, the calculation formulas of the port voltage v SM and the capacitance current i C (t) of the submodule are respectively:
vSM_2(t)＝rO·iarm(t)+vOC(t-ΔT) (11)
④ Operating state 4
As shown in fig. 8, since the IGBT T1 in the operating state 4 may be equivalently an open state, the submodule circuit diagram thereof may be further simplified into a submodule davien equivalent circuit composed of a submodule equivalent historical voltage source v OC (T- Δt) and a submodule equivalent resistor r O connected in series, and the port voltage and the capacitance current of the submodule are the same as those in the operating state 3 at this time, except for simplifying the equivalent resistor r SEQ, in the operating state 4, there are:
rSEQ＝rJ (13)
2.4 Based on the number of sub-modules turned on by the IGBT T1 in the hybrid braking resistor converter and the port voltages v SM of the sub-modules in different operation states in step 2.3), the hybrid braking resistor converter is equivalent to a branch davin equivalent circuit composed of a branch history voltage source v armEQ (T- Δt) and a branch equivalent resistor r armEQ connected in series.
Because the hybrid braking resistor converter is formed by connecting hundreds of sub-modules and 1 braking resistor r m in series, if the number of sub-modules in the hybrid braking resistor converter, in which IGBT T1 is conducted, is N and the number of sub-modules in which IGBT T1 is turned off is N-N, wherein N is the total number of sub-modules in the hybrid braking resistor converter, the voltage v arm (T) between the branch ends of the hybrid braking resistor converter is the sum of the port voltages v SM_1 (T) of N sub-modules, the port voltage v SM_2 (T) of N-N sub-modules and the voltage between the braking resistors r m, as shown in the following formula:
Wherein,
Wherein r O,y is the equivalent resistance of the y-th sub-module; r m is a brake resistor; v OC,y (T- Δt) is the equivalent historical voltage source of the y-th sub-module.
It can be seen that the hybrid braking resistor converter can be equivalently a branch davin equivalent circuit formed by serially connecting a branch history voltage source v armEQ (T-deltat) with a branch equivalent resistor r armEQ in the electromagnetic transient simulation process.
In the step 3), the branch davin equivalent circuit of the hybrid braking resistor converter is substituted into the flexible direct system network to be solved, the current i arm (t) passing through the branch of the hybrid braking resistor converter can be solved, then the capacitance current i C (t) of each sub-module can be obtained by using the formula (5) and the formula (12), and then the voltage v C (t) between the capacitance ends of each sub-module can be obtained by using the formula (1), so that the equivalent historical voltage source of the capacitance of each sub-module at the next moment can be calculated by using the formula (3) again. Specifically, the method comprises the following steps:
3.1 Initializing data: in the invention, the sub-module capacitance current i C (0) =0, the voltage v C(0)＝UdcN/N between the sub-module capacitance ends at the initial moment, the initial time variable t=deltaT, the number n=0 of sub-modules conducted by the IGBT T1 at the initial moment and the cyclic variable i, j, k=0 are assumed, wherein U dcN is the rated direct current voltage;
3.2 According to the current time, the voltage between the capacitance ends of the submodules and the capacitance equivalent model (namely formulas (2) and (3)), calculating the equivalent resistance r CEQ and the equivalent historical voltage source v CEQ (T-delta T) of the submodule capacitance of the hybrid braking resistor converter;
3.3 Circularly calculating the submodules based on the conduction condition of the IGBT T2 in the submodules to obtain simplified equivalent resistance r SEQ of each submodule;
if the IGBT T2 is turned on, it is calculated according to the formula (6) or (10), and if the IGBT T2 is turned off, it is calculated according to the formula (7) or (13);
3.4 Based on the conduction condition of the IGBT T1 in the sub-module), performing the cyclic calculation on the sub-module: if the IGBT T1 is conducted, the number of sub-modules conducted by the IGBT T1 is updated, wherein n=n+1; if the IGBT T1 is turned off, calculating an equivalent historical voltage source v OC (T-delta T) of the submodule and an equivalent resistance r O of the submodule;
3.5 According to the number of sub-modules conducted by the IGBT T1 and the equivalent historic voltage sources and the equivalent resistances of the sub-modules, calculating a branch equivalent historic voltage source v armEQ (T-delta T) and a branch equivalent resistance r armEQ;
3.6 A branch Thevenin equivalent circuit formed by serially connecting a branch equivalent historical voltage source v armEQ (T-delta T) and a branch equivalent resistor r armEQ is used for replacing a hybrid braking resistor converter, and is substituted into a flexible direct system network to be solved by using an EMTDC simulation tool, so that a branch current i arm (T) is obtained;
3.7 Circularly calculating the submodule based on the conduction condition of the IGBT T1 in the submodule to obtain a submodule capacitance current i C (T), and calculating the voltage v C (T) between the submodule capacitance ends by using the formula (1) based on the submodule capacitance current i C (T);
if the IGBT T1 is turned on, calculating the capacitance current of the submodule according to the formula (5), and if the IGBT T1 is turned off, calculating the capacitance current of the submodule according to the formula (12);
3.8 Updating the time variable t=t+Δt, jumping to step 3.2) to start the simulation calculation of the next simulation time until the simulation end time is reached.
The invention also provides an electromagnetic transient equivalent modeling system of the hybrid brake resistor converter based on the electromagnetic transient equivalent modeling method of the hybrid brake resistor converter, which comprises the following steps: the element equivalent module is used for analyzing the topological structure of the submodule of the hybrid brake resistor converter and carrying out equivalent modeling on each main element in the submodule; the circuit equivalent module is used for analyzing the operation state of the mixed braking resistor converter submodule in the operation process, obtaining the Thevenin equivalent circuit of the submodule in different operation states based on the equivalent model of each main element, and further obtaining the branch Thevenin equivalent circuit of the mixed braking resistor converter; and the electromagnetic transient simulation module is used for substituting the branch Thevenin equivalent circuit of the hybrid brake resistor converter into the flexible-direct system network to solve so as to obtain a system electromagnetic transient simulation result containing the hybrid brake resistor converter.
Example 1
To further verify the effectiveness and feasibility of the invention, the invention is further illustrated by the following examples:
Building a flexible direct system model with direct current voltage of +/-400 kV in power system transient simulation software PSCAD/EMTDC, and modeling the hybrid brake resistor converter by adopting the following two modes respectively: (1) Manually building an actual model of the N sub-modules connected in series with the brake resistor by using the existing element module; (2) The electromagnetic transient equivalent modeling method of the hybrid brake resistor converter is utilized. The specific simulation parameters are as follows: considering that the manual modeling workload is large and the simulation speed is greatly influenced in the method (1), simplifying the number of sub-modules, and taking n=10; sub-module capacitance c=45 uF; the submodule voltage limiting resistor r loss =92 Ω; submodule balancing resistor r J =150kΩ; assume that the receiving end converter transformer network side has a three-phase ground fault at 1s, and the fault duration is 0.6s.
As shown in fig. 10, if the actual model constructed manually is used to model the hybrid braking resistor converter, the dc voltage and the branch current rise rapidly after the fault occurs, then under the energy consumption of the hybrid braking resistor converter, the dc voltage stabilizes at the set value, the hybrid braking resistor converter exits the operation after the fault is cleared, the dc voltage returns to the rated value, and the branch current drops to 0.
As shown in fig. 11, if the electromagnetic transient equivalent modeling method of the hybrid braking resistor converter provided by the invention is adopted, the variation trend and variation amplitude of the waveforms of the direct current voltage and the branch current are consistent with those of the waveform shown in fig. 10 when the actual model is adopted during the fault period and after the fault is cleared.
The embodiment shows that the electromagnetic transient equivalent modeling method of the hybrid braking resistor converter can highly simulate the external voltage and current change characteristics of the hybrid braking resistor converter, and the effectiveness and feasibility of the hybrid braking resistor converter are verified. In an actual flexible direct-current system with the number of the sub-modules of the hybrid brake resistor converter being hundreds, the method for manually constructing the actual model aiming at the hybrid brake resistor converter is not applicable any more, and the electromagnetic transient equivalent modeling method provided by the invention has great practical value and wide application prospect.
It will be appreciated by those skilled in the art that embodiments of the present application may be provided as a method, system, or computer program product. Accordingly, the present application may take the form of an entirely hardware embodiment, an entirely software embodiment or an embodiment combining software and hardware aspects. Furthermore, the present application may take the form of a computer program product embodied on one or more computer-usable storage media (including, but not limited to, disk storage, CD-ROM, optical storage, and the like) having computer-usable program code embodied therein.
The present application is described with reference to flowchart illustrations and/or block diagrams of methods, apparatus (systems) and computer program products according to embodiments of the application. It will be understood that each flow and/or block of the flowchart illustrations and/or block diagrams, and combinations of flows and/or blocks in the flowchart illustrations and/or block diagrams, can be implemented by computer program instructions. These computer program instructions may be provided to a processor of a general purpose computer, special purpose computer, embedded processor, or other programmable data processing apparatus to produce a machine, such that the instructions, which execute via the processor of the computer or other programmable data processing apparatus, create means for implementing the functions specified in the flowchart flow or flows and/or block diagram block or blocks.
These computer program instructions may also be stored in a computer-readable memory that can direct a computer or other programmable data processing apparatus to function in a particular manner, such that the instructions stored in the computer-readable memory produce an article of manufacture including instruction means which implement the function specified in the flowchart flow or flows and/or block diagram block or blocks.
These computer program instructions may also be loaded onto a computer or other programmable data processing apparatus to cause a series of operational steps to be performed on the computer or other programmable apparatus to produce a computer implemented process such that the instructions which execute on the computer or other programmable apparatus provide steps for implementing the functions specified in the flowchart flow or flows and/or block diagram block or blocks.
A specific embodiment is given above, but the invention is not limited to the described embodiment. The basic idea of the invention is that the above-mentioned scheme, it is not necessary for those skilled in the art to design various modified models, formulas, parameters according to the teaching of the present invention to take creative effort. Variations, modifications, substitutions and alterations are also possible in the embodiments without departing from the principles and spirit of the present invention.
Claims (8)
1. An electromagnetic transient equivalent modeling method of a hybrid brake resistor converter is characterized by comprising the following steps of:
1) Analyzing the sub-module topological structure of the hybrid brake resistor converter, and carrying out equivalent modeling on each main element in the sub-module;
2) Analyzing the operation state of the sub-module of the hybrid brake resistor converter in the operation process, and obtaining the Thevenin equivalent circuit of the sub-module in different operation states based on the equivalent model of each main element in the step 1), so as to obtain the branch Thevenin equivalent circuit of the hybrid brake resistor converter;
The method comprises the following steps:
2.1 Based on the equivalent model of each main element in the sub-module of the hybrid brake resistor converter obtained in the step 1), the sub-module topological structure of the hybrid brake resistor converter is equivalent to a form that the resistor and the voltage source are connected in series and parallel;
2.2 The trigger instructions of the first IGBT and the second IGBT in the sub-module are arranged and combined to obtain the running state of the sub-module of the hybrid brake resistor converter;
Comprising the following steps:
① Operating state 1: FT1 = 1 and FT2 = 1, the first IGBT and the second IGBT are both on, the diode is in clamping state;
② Operating state 2: FT1 = 1 and FT2 = 0, the first IGBT is on, the second IGBT is off, the diode is in clamping state;
③ Operating state 3: FT1 = 0 and FT2 = 1, the first IGBT turns off, the second IGBT turns on, the diode is in the on state;
④ Operating state 4: FT1 = 0 and FT2 = 0, the first IGBT and the second IGBT are both turned off, the diode is in the on state;
2.3 Further simplifying equivalent analysis of each sub-module in the hybrid brake resistor converter under different running states, and calculating to obtain port voltage v SM and capacitance current i C (t) of each sub-module;
2.4 Based on the number of sub-modules turned on by the first IGBT in the hybrid brake resistor converter and the port voltages v SM of the sub-modules in different operation states in the step 2.3), the hybrid brake resistor converter is equivalent to a branch Thevenin equivalent circuit formed by serially connecting a branch history voltage source v armEQ (T-delta T) with a branch equivalent resistor r armEQ; wherein T is time, and DeltaT is simulation step length;
3) Substituting the branch Thevenin equivalent circuit of the hybrid braking resistor converter into a flexible direct system network to solve, and obtaining a system electromagnetic transient simulation result containing the hybrid braking resistor converter.
2. The electromagnetic transient equivalent modeling method of the hybrid braking resistor converter of claim 1, wherein: in the step 1), the method for equivalently modeling each main element in the submodule of the hybrid braking resistor converter comprises the following steps:
1.1 Analyzing the topological structure of a sub-module of the hybrid brake resistor converter to obtain main elements contained in the sub-module, wherein the main elements comprise a first IGBT, a second IGBT, a diode, a capacitor, a voltage-sharing resistor and a voltage-limiting resistor element;
1.2 The equivalent resistance of the IGBT and the anti-parallel diode thereof in the on state and the off state is analyzed, and the IGBT and the anti-parallel diode thereof are equivalent to a variable resistor controlled by an IGBT trigger instruction;
1.3 The equivalent resistance of the diode in the conducting state and the clamping state is analyzed, and the diode is equivalent to a variable resistance controlled by the running state;
1.4 Equivalent analysis is performed on the capacitor, and the capacitor is equivalent to a Thevenin equivalent circuit formed by serially connecting an equivalent historical voltage source v CEQ (T-delta T) with an equivalent resistor r CEQ.
3. The electromagnetic transient equivalent modeling method of the hybrid braking resistor converter of claim 2, wherein: in the step 1.2), the equivalent of the IGBT and the anti-parallel diode thereof as the variable resistor controlled by the IGBT trigger instruction means that:
When the trigger instruction is 1, the IGBT is conducted and is equivalent to a resistor with the resistance value of 0.01 omega;
When the trigger instruction is 0, the IGBT is turned off, and the trigger instruction is equivalent to an open circuit state;
in the step 1.3), the equivalent of the diode as a variable resistor controlled by the operation state means that:
When the diode is in a conducting state, the diode is equivalent to a resistor with the resistance value of 0.01 omega;
when the diode is in the clamped state, it is equivalent to an open state.
4. The electromagnetic transient equivalent modeling method of the hybrid braking resistor converter of claim 2, wherein: in the step 1.4), the calculation formulas of the equivalent historical voltage source v CEQ (T- Δt) and the equivalent resistor r CEQ of the capacitor are respectively:
Wherein, delta T is the simulation step length; c is the capacitance of the submodule; i C (T- Δt) is the submodule capacitance history current; v C (T-DeltaT) is the voltage across the capacitance histories of the submodules.
5. The electromagnetic transient equivalent modeling method of the hybrid braking resistor converter of claim 1, wherein: in the step 2.3), the calculation formulas of the port voltage v SM and the capacitance current i C (t) of each sub-module in different operation states in the hybrid braking resistor converter are respectively as follows:
① Operating state 1
The expressions of the port voltage and the capacitance current of the sub-module are respectively:
vSM_1(t)＝0.01Ω·iarm(t)，
Wherein v SM_1 (t) is the port voltage of the submodule in the running state 1 and the running state 2; i arm (t) is the branch current; i C_1 (t) is the capacitive current of the run state 1 and run state 2 sub-modules; v CEQ (T- Δt) is the equivalent historical voltage source; r CEQ is the capacitance equivalent resistance, and DeltaT is the simulation step size; t is time; r SEQ is a simplified equivalent resistance, and its expression is:
rSEQ＝(rloss+0.01Ω)//rJ，
wherein r loss is a limiting resistor; r J is a equalizing resistor;
② Operating state 2
The expression of the port voltage and the capacitance current of the sub-module is the same as the operation state 1, and the expression of the simplified equivalent resistor r SEQ at the moment is as follows:
rSEQ＝rJ，
③ Run state 3
The expressions of the port voltage and the capacitance current of the sub-module are respectively:
vSM_2(t)＝rO·iarm(t)+vOC(t-ΔT)，
Wherein v SM_2 (t) is the port voltage of the submodule in the running state 3 and the running state 4; r O is the submodule equivalent resistance; v OC (T- Δt) is the operating state 3 and operating state 4 submodule equivalent historical voltage sources; i C_2 (t) is the capacitive current of the run state 3 and run state 4 sub-modules; at this time, the expression of the reduced equivalent resistance r SEQ is:
rSEQ＝(rloss+0.01Ω)//rJ，
④ Operating state 4
The expression of the port voltage and the capacitance current of the sub-module is the same as the running state 3, and at this time, the expression of the simplified equivalent resistor r SEQ is as follows:
rSEQ＝rJ。
6. the electromagnetic transient equivalent modeling method of the hybrid braking resistor converter of claim 1, wherein: in the step 2.4), the calculation formulas of the branch history voltage source v armEQ (T- Δt) and the branch equivalent resistor r armEQ of the branch thevenin equivalent circuit are respectively:
Wherein n is the number of submodules conducted by the first IGBT in the hybrid brake resistor converter; n is the total number of submodules in the hybrid brake resistor converter; r O,y is the equivalent resistance of the y-th sub-module; r m is a brake resistor; v OC,y (T- Δt) is the equivalent historical voltage source of the y-th sub-module.
7. The electromagnetic transient equivalent modeling method of the hybrid braking resistor converter of claim 1, wherein: in the step 3), the method for substituting the branch Thevenin equivalent circuit of the hybrid braking resistor converter into the flexible-direct system network to solve comprises the following steps:
3.1 Initializing data: assuming that a submodule capacitance current i C (0) =0, an initial time submodule capacitance end voltage v C(0)＝UdcN/N, an initial time variable t=Δt, the number n=0 of submodules turned on by the first IGBT at the initial time, and a circulation variable i, j, k=0 in the hybrid braking resistor converter, wherein U dcN is a rated direct current voltage;
3.2 According to the current time sub-module capacitance current and the capacitance equivalent model, calculating an equivalent historical voltage source v CEQ (T-delta T) and a capacitance equivalent resistance r CEQ of the sub-module capacitance of the hybrid brake resistor converter;
3.3 Circularly calculating the sub-modules based on the conduction condition of the second IGBT in the sub-modules to obtain simplified equivalent resistance r SEQ of each sub-module;
3.4 Based on the conduction condition of the first IGBT in the sub-module), performing a cyclic calculation on the sub-module: if the first IGBT is conducted, updating the number of sub-modules conducted by the first IGBT, wherein n=n+1; if the first IGBT is turned off, calculating an equivalent historical voltage source v OC (T-delta T) of the submodule and an equivalent resistance r O of the submodule;
3.5 According to the number of sub-modules conducted by the first IGBT and the equivalent historic voltage sources and the equivalent resistances of the sub-modules, calculating a branch equivalent historic voltage source v armEQ (T-delta T) and a branch equivalent resistance r armEQ;
3.6 A branch Thevenin equivalent circuit formed by serially connecting a branch equivalent historical voltage source v armEQ (T-delta T) and a branch equivalent resistor r armEQ is used for replacing a hybrid braking resistor converter, and is substituted into a flexible direct system network to be solved by using an EMTDC simulation tool, so that a branch current i arm (T) is obtained;
3.7 Circularly calculating the submodule based on the conduction condition of the first IGBT in the submodule to obtain a submodule capacitance current i C (t), and calculating the voltage v C (t) between the submodule capacitance ends based on the submodule capacitance current i C (t);
3.8 Updating the time variable t=t+Δt, jumping to step 3.2) to start the simulation calculation of the next simulation time until the simulation end time is reached.
8. An electromagnetic transient equivalent modeling system for a hybrid brake resistor converter, comprising:
the element equivalent module is used for analyzing the topological structure of the submodule of the hybrid brake resistor converter and carrying out equivalent modeling on each main element in the submodule;
the circuit equivalent module is used for analyzing the operation state of the mixed braking resistor converter submodule in the operation process, obtaining the Thevenin equivalent circuit of the submodule in different operation states based on the equivalent model of each main element, and further obtaining the branch Thevenin equivalent circuit of the mixed braking resistor converter;
Comprising the following steps:
based on the obtained equivalent model of each main element in the sub-module of the hybrid brake resistor converter, the topological structure of the sub-module of the hybrid brake resistor converter is equivalent to a form that the resistor and the voltage source are connected in series and parallel;
The trigger instructions of the first IGBT and the second IGBT in the sub-module are arranged and combined to obtain the running state of the sub-module of the hybrid brake resistor converter;
Comprising the following steps:
① Operating state 1: FT1 = 1 and FT2 = 1, the first IGBT and the second IGBT are both on, the diode is in clamping state;
② Operating state 2: FT1 = 1 and FT2 = 0, the first IGBT is on, the second IGBT is off, the diode is in clamping state;
③ Operating state 3: FT1 = 0 and FT2 = 1, the first IGBT turns off, the second IGBT turns on, the diode is in the on state;
④ Operating state 4: FT1 = 0 and FT2 = 0, the first IGBT and the second IGBT are both turned off, the diode is in the on state;
Further simplifying equivalent analysis of each sub-module in different running states in the hybrid brake resistor converter, and calculating to obtain port voltage v SM and capacitance current i C (t) of each sub-module;
Based on the number of sub-modules conducted by the first IGBT and port voltages v SM of the sub-modules in different running states in the hybrid braking resistor converter, the hybrid braking resistor converter is equivalent to a branch Thevenin equivalent circuit formed by serially connecting a branch history voltage source v armEQ (T-delta T) with a branch equivalent resistor r armEQ; wherein T is time, and DeltaT is simulation step length;
And the electromagnetic transient simulation module is used for substituting the branch Thevenin equivalent circuit of the hybrid brake resistor converter into the flexible-direct system network to solve so as to obtain a system electromagnetic transient simulation result containing the hybrid brake resistor converter.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202010541409.XA CN111753413B (en) | 2020-06-15 | 2020-06-15 | Electromagnetic transient equivalent modeling method and system for hybrid brake resistor converter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202010541409.XA CN111753413B (en) | 2020-06-15 | 2020-06-15 | Electromagnetic transient equivalent modeling method and system for hybrid brake resistor converter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN111753413A CN111753413A (en) | 2020-10-09 |
| CN111753413B true CN111753413B (en) | 2024-05-14 |
Family
ID=72676195
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202010541409.XA Active CN111753413B (en) | 2020-06-15 | 2020-06-15 | Electromagnetic transient equivalent modeling method and system for hybrid brake resistor converter |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN111753413B (en) |
Families Citing this family (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN116729582A (en) * | 2022-03-17 | 2023-09-12 | 中国船舶重工集团公司第七一一研究所 | Method and system for selecting type of ship brake resistor of hybrid power system |
Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102663174A (en) * | 2012-03-23 | 2012-09-12 | 浙江大学 | Simulation method of MMC (modular multilevel converter) and application thereof |
| WO2017041428A1 (en) * | 2015-09-10 | 2017-03-16 | 南方电网科学研究院有限责任公司 | Modelling method and system for diode clamped cascaded multi-level converter |
| CN108920856A (en) * | 2018-07-12 | 2018-11-30 | 东北电力大学 | A kind of improvement type modularization multi-level converter equivalent method |
-
2020
- 2020-06-15 CN CN202010541409.XA patent/CN111753413B/en active Active
Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102663174A (en) * | 2012-03-23 | 2012-09-12 | 浙江大学 | Simulation method of MMC (modular multilevel converter) and application thereof |
| WO2017041428A1 (en) * | 2015-09-10 | 2017-03-16 | 南方电网科学研究院有限责任公司 | Modelling method and system for diode clamped cascaded multi-level converter |
| CN108920856A (en) * | 2018-07-12 | 2018-11-30 | 东北电力大学 | A kind of improvement type modularization multi-level converter equivalent method |
Non-Patent Citations (3)
| Title |
|---|
| 单端口子模块MMC 电磁暂态通用等效建模方法;赵禹辰等;《中国电机工程学报》;第38卷(第16期);4658-4667 * |
| 徐东旭等.钳位双子模块型MMC 的电磁暂态等效模型.《电网技术》.2016,第40卷(第10期),徐东旭等. * |
| 钳位双子模块型MMC 的电磁暂态等效模型;徐东旭等;《电网技术》;第40卷(第10期);徐东旭等 * |
Also Published As
| Publication number | Publication date |
|---|---|
| CN111753413A (en) | 2020-10-09 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN105117543B (en) | A kind of equivalent simulation method based on full-bridge submodule MMC for considering a variety of locking mode | |
| CN108229021B (en) | Blocking modeling method of modular multilevel converter based on real-time digital simulator | |
| CN109256970B (en) | MMC-MTDC transmission system monopolar grounding fault current calculation method | |
| CN105844993A (en) | Energy feedback type aircraft electrical load simulation method and device | |
| Zhang et al. | Development of a converter-based transmission line emulator with three-phase short-circuit fault emulation capability | |
| CN105021943B (en) | Overcurrent detection method and system for MMC-HVDC AC side fault | |
| CN109861240B (en) | Control method of distributed power flow controller based on ADPSS/ETSDAC modeling | |
| Wang et al. | Real-time and faster-than-real-time simulation of Modular Multilevel Converters using standard multi-core CPU and FPGA chips | |
| CN111753413B (en) | Electromagnetic transient equivalent modeling method and system for hybrid brake resistor converter | |
| CN105785976A (en) | Test method and system for control protection device in flexible direct current transmission | |
| CN109241678A (en) | The more topological Universal Simulation Models of modularization multi-level converter | |
| CN108376992B (en) | MMC equivalent simulation method for hybrid sub-module | |
| Tremblay et al. | Real-time simulation of a fully detailed type-IV wind turbine | |
| CN111177932A (en) | Modeling method for improving electromagnetic transient simulation speed of flexible substation | |
| Dufour et al. | Solvers for real-time simulation of bipolar thyristor-based HVDC and 180-cell HVDC modular multilevel converter for system interconnection and distributed energy integration | |
| CN110427660B (en) | Simulation method of high-voltage direct-current circuit breaker | |
| CN107370174A (en) | A kind of HVDC transmission system simplifies modeling method | |
| CN104393594B (en) | Analytical calculation method for medium voltage network flow of urban rail transit | |
| CN111969607B (en) | dSPACE-based distributed power flow controller series side closed loop simulation test method | |
| Li | Real-time simulation of CDSM modular multilevel converter for HIL test applications | |
| Iyoda et al. | History of power system simulators to analyze and test of power electronics equipment | |
| CN111737936B (en) | Quick simulation method and system for modularized direct-current side active power balance device | |
| Meddah et al. | Real-time simulation of a fast charger using a low-cost FPGA platform | |
| CN112765920A (en) | DC short-circuit current calculation method and system based on difference-common mode conversion | |
| CN113852079A (en) | Inversion feedback type regeneration device simulation method suitable for power flow simulation calculation |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |