CN111277131A - Boost power conversion circuit and control method thereof - Google Patents

Boost power conversion circuit and control method thereof Download PDF

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Publication number
CN111277131A
CN111277131A CN202010229548.9A CN202010229548A CN111277131A CN 111277131 A CN111277131 A CN 111277131A CN 202010229548 A CN202010229548 A CN 202010229548A CN 111277131 A CN111277131 A CN 111277131A
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Prior art keywords
voltage
diode
power conversion
switch
conversion circuit
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Pending
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CN202010229548.9A
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Chinese (zh)
Inventor
许颇
程琨
魏万腾
王一鸣
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Ningbo Ginlong New Energy Technology Co ltd
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Ningbo Ginlong New Energy Technology Co ltd
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Priority to CN202010229548.9A priority Critical patent/CN111277131A/en
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/36—Means for starting or stopping converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention discloses a boost power conversion circuit and a control method thereof, and a starting circuit added with a flying capacitor comprises a second capacitor and a first switch, wherein the added flying capacitor voltage starting circuit can carry out voltage clamping on a connecting point of a third diode and a fourth diode, when the voltage of an input end of the boost power conversion circuit is lower than the starting voltage of the boost power conversion circuit, the voltage of the connecting point of the third diode and the fourth diode is smaller than the bus voltage, the voltage stress of the connecting point is further reduced, the selection of a diode is convenient, and the higher the reverse voltage stress borne by the diode is, the higher the cost is, so the cost of the diode can be reduced.

Description

Boost power conversion circuit and control method thereof
Technical Field
The invention relates to the technical field of power electronics, in particular to a photovoltaic grid-connected inverter boost power conversion circuit applied to multi-path MPPT and a control method thereof.
Background
The Boost circuit is a Boost power conversion circuit, and can Boost input voltage and then output the boosted input voltage, so that power conversion is realized. The Boost circuit comprises a two-level Boost circuit and a multi-level Boost circuit, the two-level Boost circuit is generally applied to occasions with lower voltage levels, and the multi-level Boost circuit is applied to occasions with higher voltage levels. Compared with a two-level Boost circuit, the multi-level Boost circuit realizes multi-level by improving a self topological structure, and further realizes high-voltage and high-power output. The multi-level Boost circuit has the outstanding advantages that the voltage stress of the power device can be reduced, the voltage stress borne by the power device is half of that of a two-level Boost circuit, and therefore the power device with a smaller voltage-withstanding grade can be used for realizing the voltage output with a higher grade.
The application of the three-level Boost circuit is described below by taking the photovoltaic power generation field as an example. Compared with a symmetrical three-level Boost circuit, as shown in fig. 1-b, the front-stage common-ground three-level Boost circuit of the photovoltaic grid-connected inverter, as shown in fig. 1-a, has the advantages of no common-mode signal influence, half-reduced energy storage inductance, high operation efficiency and the like, and is a more preferable choice for the photovoltaic grid-connected inverter. However, when the common ground three-level Boost circuit is applied to multiple MPPTs, if a certain or multiple MPPTs normally operate to cause a bus voltage to rise, and the circuit cannot operate because the input voltage is low or the circuit is not connected, the initial voltage of the flying capacitor C1 of the circuit is equal to zero, the igbt T1 is disconnected from the igbt T2, and the voltage between the cathode of the diode D3 and the anode of the diode D2 can be regarded as an equipotential approximately, and it can be known from kirchhoff voltage loop law that the diode D4 bears the entire bus voltage to cause a high reverse voltage stress of the diode D4, as shown in fig. 1-a, which brings a serious challenge to the voltage stress design of the device. When the photovoltaic grid-connected inverter is started, because the photovoltaic grid-connected inverter generally has multiple MPPTs as shown in fig. 13, when one of the MPPTs is not connected to the photovoltaic cell panel or the output voltage of the photovoltaic cell panel is lower at this time, the diode D4 will bear reverse voltage stress as shown in fig. 1-a, and in an extreme case, when the reverse voltage stress is 1500V, the diode D4 will bear the whole bus voltage of 1500V. Therefore, it is necessary to select a diode with a high voltage withstanding value, and the diode with a high voltage withstanding value has a high tube voltage drop and poor reverse recovery characteristics, which may seriously affect the circuit efficiency when in use.
Therefore, it is desirable to obtain a boost power conversion circuit and a control method thereof for protecting a diode that bears a back voltage, so that the type selection is easy, so as to overcome the above-mentioned drawbacks.
Disclosure of Invention
In order to solve the technical problems in the prior art, the starting circuit of the flying capacitor C1 is added, when the MPPT input voltage of a certain path is equal to zero or is not connected with the solar panel, the output bus voltage is equal to 1500V, the reverse voltage born by the diode D4 can be ensured to be less than 1000V, and therefore a diode with a low voltage-resistant grade can be selected, the system cost is reduced, and the working efficiency of a circuit system is improved.
In one aspect, the present invention provides a boost power conversion circuit, including a power source Vin, an inductor L1, a first switch module, a second switch module, a third diode D3, a fourth diode D4, a load unit, and a flying capacitor C1; the inductor L1, the third diode D3, the fourth diode D4 and the power Vin are connected in series to form a main loop; the inductor L1, the first switch module and the second switch module are connected in series to form a first closed loop; the first, second, third and fourth switching modules D3, D4 form a second closed loop; the inductor L1, the first switch module, the flying capacitor C1, the fourth diode D4 and the power source Vin form a third closed loop; the flying capacitor voltage starting circuit is used for enabling the voltage borne by the fourth diode D4 to be smaller than the bus voltage of the boost power conversion circuit, wherein the bus voltage is the voltage difference between the positive bus voltage and the negative bus voltage.
When the flying capacitor voltage starting circuit is connected in series with the third closed loop, the voltage starting circuit comprises a second capacitor C2 and a first switch K1, and the second capacitor C2 and the first switch K1 are connected in series and then connected in parallel to two sides of a fourth diode D4. The first switch K1 includes a mechanical switch and an electronic switch. The first switch module comprises a first switch tube T1 and a first diode D1, the second switch module comprises a second switch tube T2 and a second diode D2, the negative pole end of the diode is connected with the collector electrode of the switch tube, and the positive pole end of the diode is connected with the emitter electrode of the switch tube.
The load unit also comprises a third bus capacitor C3 and a fourth bus capacitor C4 which are connected in series and then are connected in parallel with the load unit; the first switch module, the second switch module, the third diode D3, the fourth diode D4, the third bus capacitor C3, and the fourth bus capacitor C4 form a second closed loop.
When the system starts to be electrified, the first switch K1 is closed, the second capacitor and the fourth diode are connected in parallel, and when the photovoltaic grid-connected inverter system starts to work, the C2 and the C1 bear the bus voltage V togetheroutIf C1 is equal to C2, then VC1＝VC2＝VoutAnd/2, when the system detection circuit detects that the voltage of the flying capacitor C1 is equal to the threshold starting voltage, the first switch K1 is turned off, and the voltage kept on the flying capacitor C1 is the threshold starting voltage, so that the initial voltage of the flying capacitor is quickly established, and the purpose of reducing the withstand voltage of the fourth diode D4 can be realized.
The flying capacitor voltage starting circuit is additionally arranged, voltage clamping can be carried out on the connecting point of the third diode and the fourth diode, when the voltage of the input end of the boost power conversion circuit is lower than the starting voltage of the boost power conversion circuit, the potential of the connecting point of the third diode and the fourth diode is higher than the negative potential of the bus, the voltage stress of the fourth diode is further reduced, the selection of the diodes is facilitated, and the cost is higher as the voltage stress borne by the diodes is larger, so that the cost of the diodes can be reduced.
In another aspect, the present invention provides a method for controlling a boost power converter circuit, wherein when the voltage at the input terminal of the boost power converter circuit is lower than the start voltage, the flying capacitor voltage start circuit makes the voltage received by the fourth diode D4 smaller than the difference between the positive bus potential and the negative bus potential of the boost power converter circuit.
Drawings
FIG. 1-a is a schematic diagram of a three-level BOOST circuit with input and output common ground;
FIG. 1-b is a topological structure diagram of a symmetric three-level BOOST circuit;
FIG. 2 is a waveform diagram of driving signals when D < 0.5;
FIG. 3 is a path diagram of switching mode a when D < 0.5;
FIG. 4 is a path diagram of switching mode b with D < 0.5;
FIG. 5 is a path diagram of switching mode c with D < 0.5;
FIG. 6 is a path diagram of the switching mode D when D < 0.5;
FIG. 7 is a waveform diagram of driving signals when D > 0.5;
FIG. 8 is a path diagram of switch mode a when D > 0.5;
FIG. 9 is a path diagram of switching mode b when D > 0.5;
FIG. 10 is a path diagram of switching mode c for D > 0.5;
FIG. 11 is a path diagram of switching mode D when D > 0.5;
FIG. 12-a is a schematic diagram of a boost power converter circuit with a switch closed according to an embodiment of the present disclosure;
FIG. 12-b is a schematic diagram of a boost power conversion circuit with a switch turned off according to an embodiment of the present disclosure;
fig. 13 is a schematic diagram of an application in which output terminals of a plurality of Boost circuits are connected in parallel to a photovoltaic power generation system;
Detailed Description
In order to make those skilled in the art better understand the technical solutions provided by the embodiments of the present application, the following describes the operation principle of the conventional three-level Boost circuit as an example.
As shown in FIG. 1-a, the resistor R1 is a load cell, which is based on the input voltage VinAnd an output voltage VoutThe Boost circuit respectively works in two working modes of duty ratio D <0.5 and D > 0.5:
1. when V isin＞0.5VoutWhen the duty ratio D is less than 0.5;
in this operation mode, the waveform diagram of the drive signal is shown in fig. 2, and the current flow paths in each switching mode are shown in fig. 3 to 6, in which the current flow paths are shown, and C2 and C3 are bus capacitors. In the figure, T is the switching period, and T1 and T2 drive signals are different in phase angle of 180 degrees.
As in fig. 3, switching mode a: t1 is turned on, T2 is turned off, D4 is turned on, D3 is turned off, and the flying capacitor voltage is controlled as follows: vC1＝0.5VoutWhen the voltage born by the two ends of the inductor L1 is larger than zero, the inductor current linearly rises, and the voltage stress of the D3 is 0.5VoutD4 is on with no reverse voltage stress.
As shown in fig. 4 and 6, the switching modes are b and d: the two switching modes are completely the same and appear twice in the same period. Both T1 and T2 are in the off state. The inductive current freewheels through D3 and D4, D3 and D4 are conducted, and no reverse voltage stress exists.
As shown in fig. 5, switching mode c: t1 is turned off, T2 is turned on, D3 is turned on, D4 is turned off, and the voltage stress is:
Vout-VC1＝0.5Vout；
according to the principle of conservation of voltage at two ends of the inductor in volt-seconds, namely in a working period, the multiplication of the voltage at two ends of the inductor and the time is 0, and the following can be obtained: (V)in-Vout+VC1)·DT+(Vin-Vout)·(1-2D)T+(Vin-VC1) DT ═ 0; after simplification, the method can be obtained: vout＝Vin(1-D), it can be seen from this equation that the output voltage can be controlled by controlling the duty ratio D of T1 and T2.
2. When V isinLess than 0.5VoutWhen the duty ratio D is more than 0.5;
in this operation mode, the waveform diagram of the driving signal is shown in fig. 7, and the current flow paths in each switching mode are shown in fig. 8 to 11, in which the solid line represents the current path, and C2 and C3 are bus capacitors.
As shown in fig. 8 and 10, switching modes a and c: the two switching mode current flow paths are identical and occur at different stages of a cycle. T1 and T2 are turned on, and D3 and D4 are turned off. The voltage across the inductor L1 is VinThe inductor current rises linearly. The voltage stress of D3 and D4 are both 0.5Vout。
As shown in fig. 9, switching mode b: t1 is turned on, T2 is turned off, D4 is turned on, and D3 is turned off. D3 voltage stress of 0.5Vout。
As shown in fig. 11, switching mode d: t2 is ON, T1 is OFF, D3 is ON, and D4 is OFF. D4 voltage stress of 0.5Vout. According to the principle of conservation of voltage at two ends of the inductor in volt-seconds, the following can be obtained: vout＝Vin/(1-D)。
In summary, under various operating conditions in the steady state, the voltage stress of D3 and D4 is half of the output voltage, i.e. 0.5VoutThe diode devices can be selected according to the voltage stress when being selected.
When the output ends of a plurality of three-level Boost circuits are connected in parallel, and the voltage of one or more input ends is lower than the starting voltage of the Boost power conversion circuit, the bus voltage is already established at the output ends of the Boost circuits, because the output ends of all the Boost circuits are connected in parallel, the voltage stress of the bus voltage borne by the diodes in the Boost circuits with the input ends lower than the starting voltage of the Boost power conversion circuit is caused, the diodes are damaged, otherwise, the diodes need to be selected from devices with the voltage stress larger than or equal to the bus voltage, and the cost of the selected diodes is increased. Because a power station in the photovoltaic power generation field generally comprises a plurality of inverters, the output ends of DC-DC in the plurality of inverters are connected in parallel, if the input end of a certain DC-DC is not successfully connected with a photovoltaic module, other DC-DC in the plurality of inverters are successfully connected with the photovoltaic module, and because the output ends are connected in parallel, the bus voltage of the output end of the DC-DC in parallel is already established, so that the diode in the DC-DC of which the input end is not successfully connected with the photovoltaic module can bear the back pressure of the bus voltage.
For example, as shown in fig. 1-a, when there are multiple output ends of the multiple Boost circuits connected in parallel, that is, multiple output buses are shared, if other circuits are powered on, but the Boost circuit is not powered on, then there is bus voltage, since the flying capacitor C1 voltage and the input voltage of the circuit are both 0, the voltage between the cathode of the third diode D3 and the anode of the second diode D2 can be regarded as approximately equal potential, at this time, the fourth diode D4 bears the entire bus voltage Vout, if the fourth diode D4 is driven at 0.5V, the bus voltage Vout is reduced by the voltage of the fourth diode D4outThe stress is selected, and the fourth diode D4 is broken by the overvoltage.
In order that those skilled in the art will better understand the invention and thus more clearly define the scope of the invention as claimed, it is described in detail below with respect to certain specific embodiments thereof. It should be noted that the following is only a few embodiments of the present invention, and the specific direct description of the related structures is only for the convenience of understanding the present invention, and the specific features do not of course directly limit the scope of the present invention.
For the reasons, the DC-DC provided by the embodiment of the application can be used for protecting the diode bearing the back voltage, so that the diode is easy to select and the cost is reduced.
As shown in fig. 12-a and 12-b, a boost power conversion circuit includes a power source Vin, an inductor L1, a first switch module, a second switch module, a third diode D3, a fourth diode D4, a load unit, and a flying capacitor C1; the inductor L1, the third diode D3, the fourth diode D4 and the power Vin are connected in series to form a main loop; the inductor L1, the first switch module and the second switch module are connected in series to form a first closed loop; the first, second, third and fourth switching modules D3, D4 form a second closed loop; the inductor L1, the first switch module, the flying capacitor C1, the fourth diode D4 and the power Vin form a third closed loop; the boost power converter further comprises a flying capacitor voltage starting circuit for enabling the voltage borne by the fourth diode D4 to be smaller than the bus voltage of the boost power conversion circuit, wherein the bus voltage is the difference between the positive bus potential and the negative bus potential. Wherein R1 is considered a load cell.
When the flying capacitor voltage starting circuit is connected in series with the third closed loop, the voltage starting circuit comprises a second capacitor C2 and a first switch K1, and the second capacitor C2 and the first switch K1 are connected in series and then connected in parallel to two sides of a fourth diode D4. The first switch K1 includes a mechanical switch and an electronic switch. The first switch module comprises a first switch tube T1 and a first diode D1, the second switch module comprises a second switch tube T2 and a second diode D2, the negative pole end of the diode is connected with the collector electrode of the switch tube, and the positive pole end of the diode is connected with the emitter electrode of the switch tube.
The load unit also comprises a third bus capacitor C3 and a fourth bus capacitor C4 which are connected in series and then are connected in parallel with the load unit; the first switch module, the second switch module, the third diode D3, the fourth diode D4, the third bus capacitor C3, and the fourth bus capacitor C4 form a second closed loop.
When the system starts to be powered on, the first switch K1 is closed, the second capacitor and the fourth diode are connected in parallel, when the photovoltaic grid-connected inverter system starts to work, the bus voltage Vout is borne by the C2 and the C1 together, if the C1 is equal to C2, the VC1 is equal to VC2 is equal to Vout/2, when the system detection circuit detects that the voltage of the flying capacitor C1 is equal to the threshold starting voltage, the first switch K1 is switched off, and the voltage is kept on the flying capacitor C1 as the threshold starting voltage, so that the initial voltage of the flying capacitor is quickly established, and the purpose of reducing the withstand voltage of the fourth diode D4 can be achieved.
The flying capacitor voltage starting circuit is additionally arranged, voltage clamping can be carried out on the connecting point of the third diode and the fourth diode, when the voltage of the input end of the boost power conversion circuit is lower than the starting voltage of the boost power conversion circuit, the potential of the connecting point of the third diode and the fourth diode is higher than the negative potential of the bus, the voltage stress of the fourth diode is further reduced, the selection of the diodes is facilitated, and the cost is higher as the voltage stress borne by the diodes is larger, so that the cost of the diodes can be reduced.
When the input end voltage of the boost power conversion circuit is lower than the starting voltage, the flying capacitor voltage starting circuit enables the voltage born by the fourth diode D4 to be smaller than the difference between the positive bus potential and the negative bus potential of the boost power conversion circuit.
Such alterations and modifications as are made obvious by those skilled in the art and guided by the teachings herein are intended to be within the scope of the invention as claimed.

Claims (6)

1. A boost power conversion circuit comprises a power source Vin, an inductor L1, a first switch module, a second switch module, a third diode D3, a fourth diode D4, a load unit and a flying capacitor C1;
the inductor L1, the third diode D3, the fourth diode D4 and the power Vin are connected in series to form a main loop;
the inductor L1, the first switch module and the second switch module are connected in series to form a first closed loop;
the first, second, third and fourth switching modules D3, D4 form a second closed loop;
the inductor L1, the first switch module, the flying capacitor C1, the fourth diode D4 and the power source Vin form a third closed loop;
the method is characterized in that: the flying capacitor voltage starting circuit is used for enabling the voltage borne by the fourth diode D4 to be smaller than the bus voltage of the boost power conversion circuit, wherein the bus voltage is the voltage difference between the positive bus voltage and the negative bus voltage.
2. The boost power conversion circuit according to claim 1, wherein: when the flying capacitor voltage starting circuit is connected in series with the third closed loop, the voltage starting circuit comprises a second capacitor C2 and a first switch K1, and the second capacitor C2 and the first switch K1 are connected in series and then connected in parallel to two sides of a fourth diode D4.
3. The boost power conversion circuit according to claim 2, wherein: the first switch K1 includes a mechanical switch and an electronic switch.
4. The boost power conversion circuit according to claim 1, wherein: the first switch module comprises a first switch tube T1 and a first diode D1, the second switch module comprises a second switch tube T2 and a second diode D2, the negative pole end of the diode is connected with the collector electrode of the switch tube, and the positive pole end of the diode is connected with the emitter electrode of the switch tube.
5. The boost power conversion circuit according to claim 1, wherein: the load unit also comprises a third bus capacitor C3 and a fourth bus capacitor C4 which are connected in series and then are connected in parallel with the load unit;
the first switch module, the second switch module, the third diode D3, the fourth diode D4, the third bus capacitor C3, and the fourth bus capacitor C4 form a second closed loop.
6. A control method of a boost power conversion circuit according to any one of claims 1 to 5, characterized in that: when the voltage at the input end of the boost power conversion circuit is lower than the starting voltage, the flying capacitor voltage starting circuit enables the voltage born by the fourth diode D4 to be smaller than the difference between the positive bus potential and the negative bus potential of the boost power conversion circuit.
CN202010229548.9A 2020-03-27 2020-03-27 Boost power conversion circuit and control method thereof Pending CN111277131A (en)

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Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US11329569B2 (en) 2020-01-03 2022-05-10 Delta Electronics, Inc. Power conversion system
US11362589B2 (en) * 2019-08-28 2022-06-14 Delta Electronics, Inc. Flying capacitor converter
US11374490B2 (en) 2020-02-21 2022-06-28 Delta Electronics, Inc. Power conversion system
US11757287B2 (en) 2021-03-03 2023-09-12 Huawei Digital Power Technologies Co., Ltd. Voltage conversion circuit and power supply system

Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US11362589B2 (en) * 2019-08-28 2022-06-14 Delta Electronics, Inc. Flying capacitor converter
US11329569B2 (en) 2020-01-03 2022-05-10 Delta Electronics, Inc. Power conversion system
US11374490B2 (en) 2020-02-21 2022-06-28 Delta Electronics, Inc. Power conversion system
US11831238B2 (en) 2020-02-21 2023-11-28 Delta Electronics, Inc. Power conversion system
US11757287B2 (en) 2021-03-03 2023-09-12 Huawei Digital Power Technologies Co., Ltd. Voltage conversion circuit and power supply system

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