CN110729912B - High-frequency induction heating series resonance soft switch inversion control method - Google Patents

High-frequency induction heating series resonance soft switch inversion control method Download PDF

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CN110729912B
CN110729912B CN201911047349.XA CN201911047349A CN110729912B CN 110729912 B CN110729912 B CN 110729912B CN 201911047349 A CN201911047349 A CN 201911047349A CN 110729912 B CN110729912 B CN 110729912B
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amplitude
switching
inversion
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inverter
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CN110729912A (en
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于占东
付莹
邢星
于震
张鹏
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Bohai University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/083—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the ignition at the zero crossing of the voltage or the current
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B6/00—Heating by electric, magnetic or electromagnetic fields
    • H05B6/02—Induction heating
    • H05B6/04—Sources of current
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B6/00—Heating by electric, magnetic or electromagnetic fields
    • H05B6/02—Induction heating
    • H05B6/06—Control, e.g. of temperature, of power
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Inverter Devices (AREA)
  • General Induction Heating (AREA)

Abstract

A high-frequency induction heating series resonance soft switch inversion control method belongs to the technical field of soft switch inversion control. The invention aims at the problems that in the existing induction heating inversion field, inversion control of a soft switch is realized by adopting phase-shifting resonance square waves, heating caused by hard switching of the soft switch exists in the same switch tube module, and the heat dissipation difficulty is high. The soft switching inversion control method adopts triangular waves with the same frequency as the main loop of the inversion power supply to obtain driving pulses for a switching device; selecting two reference amplitudes by taking the amplitude of the half triangular wave as a reference and combining with a set adjustment amplitude; enabling the comparison result of the triangular wave amplitude and one of the reference amplitudes to serve as the trigger levels of the two switching devices on one bridge arm, and enabling the comparison result of the triangular wave amplitude and the other reference amplitude to serve as the trigger levels of the two switching devices on the other bridge arm; the logic of the two switching devices on each bridge arm is opposite. The invention is used for realizing inversion of the induction heating series resonance soft switch.

Description

High-frequency induction heating series resonance soft switch inversion control method
Technical Field
The invention relates to a high-frequency induction heating series resonance soft switch inversion control method, and belongs to the technical field of soft switch inversion control.
Background
Induction heating, also known as electromagnetic induction heating, uses the principle of electromagnetic induction to generate current inside a material to be heated, and relies on the energy of eddy currents to achieve the purpose of heating, and is an advanced heating technology. The induction heating has the advantages of high heating efficiency, high speed, good controllability, easy realization of mechanization and automation and the like, so that the induction heating is widely applied to the hot processing technologies of smelting, welding, heat treatment, hot forging, epitaxial processing and the like in the industrial fields of metallurgy, machinery, electronics and the like, and has shown more and more extensive application prospects.
At present, in the field of induction heating inversion, phase-shift resonance square waves are mostly adopted to realize inversion control of soft switches, and in the method, under the condition that the power regulation process of a system is detuned, when large current is generated and hard turn-off is carried out, the heating caused by hard switches is generally born by switch tubes of the same module on the same bridge arm, so that the defect of high heat dissipation difficulty exists, and further the reliability of the system can be influenced.
Disclosure of Invention
The invention provides a high-frequency induction heating series resonance soft switch inversion control method, aiming at the problems that in the existing induction heating inversion field, phase-shift resonance square waves are adopted to realize inversion control of a soft switch, heating caused by hard switching of the soft switch exists in the same switch tube module, and the heat dissipation difficulty is high.
The invention relates to a high-frequency induction heating series resonance soft switching inversion control method.A main circuit of an inversion power supply controlled by the inversion control method comprises a single-phase full-bridge inverter circuit, wherein the single-phase full-bridge inverter circuit comprises two bridge arms, and each bridge arm comprises two switching devices; the main loop of the inverter works in an inductive resonance state;
the soft switching inversion control method adopts triangular waves with the same frequency as the main loop of the inversion power supply to obtain driving pulses for a switching device; selecting two reference amplitudes by taking the amplitude of the half triangular wave as a reference and combining with a set adjustment amplitude; the comparison result of the triangular wave amplitude and one of the reference amplitudes is used as the trigger level of two switching devices on one bridge arm, and the comparison result of the triangular wave amplitude and the other reference amplitude is used as the trigger level of two switching devices on the other bridge arm, so that the soft switching control of four switching devices in the main loop of the inverter power supply is realized; the logic of the two switching devices on each bridge arm is opposite.
According to the high-frequency induction heating series resonance soft switching inversion control method, two switching devices on one bridge arm are set to be VT1 and VT2, and two switching devices on the other bridge arm are set to be VT3 and VT 4; the trigger levels comprise level signals triggering VT1, VT2, VT3 and VT 4;
setting one-half triangular wave amplitude value as T0If the amplitude is adjusted to be delta, the amplitude of the triangular wave is greater than T0+ Δ, VT1 is high, VT2 is low; the amplitude of the triangular wave is lower than T0+ Δ, VT1 is low, VT2 is high; setting dead time τ between VT1 and VT20；
The amplitude of the triangular wave is greater than T0At- Δ, VT4 is high and VT3 is low; the amplitude of the triangular wave is lower than T0At- Δ, VT4 is low and VT3 is high; setting dead time τ between VT3 and VT40；
The high level corresponds to the turn-on of the corresponding switching device and the low level corresponds to the turn-off of the corresponding switching device. According to the high-frequency induction heating series resonance soft switch inversion control method, the output power calculation method of the main loop of the inversion power supply in the control method comprises the following steps:
when the main loop of the inverter works in an inductive resonance state, the fundamental frequency component U of the output voltage is invertedAB0Leading load current IABPhase β/2, where β is the phase difference between VT1 and VT 3; then the output voltage U is invertedABThe fourier expression of (a) is:
Figure BDA0002254455110000021
in the formula of UdThe direct current voltage of the main loop of the inverter power supply is used, and omega is the angular frequency of the inverter fundamental wave;
UABfundamental component U of (t)AB0(t) is:
Figure BDA0002254455110000022
UAB0(t) effective value UAB0Comprises the following steps:
Figure BDA0002254455110000023
let the fundamental current phase shift angle phi1Comprises the following steps:
Figure BDA0002254455110000024
in the formula0The phase angle between the load current and the inverted output voltage square wave;
then the load current IABEffective value I of fundamental component of (t)AB0Comprises the following steps:
Figure BDA0002254455110000025
wherein Z is the equivalent impedance of the load;
the output power P of the main loop of the inverter is:
Figure BDA0002254455110000031
according to the high-frequency induction heating series resonance soft switching inversion control method, when the phase difference beta of VT1 and VT3 is 0, the maximum value P of the output power P of the main loop of the inversion power supply ismComprises the following steps:
Figure BDA0002254455110000032
according to the high-frequency induction heating series resonance soft switch inversion control method, the per unit value of the active power of the main loop of the inversion power supply
Figure BDA0002254455110000033
Comprises the following steps:
Figure BDA0002254455110000034
according to the high-frequency induction heating series resonance soft switching inversion control method of the invention, when phi0When the content is equal to 0, the content,
Figure BDA0002254455110000035
the invention has the beneficial effects that: the invention realizes the inversion of the induction heating series resonance soft switch by a pulse generation and control method different from the common phase-shifting resonance square wave inversion. When the inversion main loop works in a series resonance state, the method can obtain the same control effect as the traditional method; when the power adjusting process of the system is detuned and large current is generated to be turned off hard, the heating caused by the hard switch is jointly born by the two modules where the switch tube is located, and the heat dissipation effect is better.
Drawings
FIG. 1 is a schematic diagram of a driving pulse signal generation process of the high-frequency induction heating series resonance soft-switching inversion control method according to the present invention;
fig. 2 is a schematic circuit structure diagram of the main circuit of the inverter power supply;
FIG. 3 is a graph of the relationship between the per unit value of the active power of the main loop of the inverter and the angle beta;
fig. 4 is a timing chart of inverter circuit control in a conventional phase shift control method.
Detailed Description
The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
It should be noted that the embodiments and features of the embodiments may be combined with each other without conflict.
The invention is further described with reference to the following drawings and specific examples, which are not intended to be limiting.
In a first specific embodiment, as shown in fig. 1 and fig. 2, the invention provides a high-frequency induction heating series resonance soft switching inversion control method, where an inverter power supply main loop controlled by the inversion control method includes a single-phase full-bridge inverter circuit, where the single-phase full-bridge inverter circuit includes two bridge arms, and each bridge arm includes two switching devices; the main loop of the inverter works in an inductive resonance state;
the soft switching inversion control method adopts triangular waves with the same frequency as the main loop of the inversion power supply to obtain driving pulses for a switching device; selecting two reference amplitudes by taking the amplitude of the half triangular wave as a reference and combining with a set adjustment amplitude; the comparison result of the triangular wave amplitude and one of the reference amplitudes is used as the trigger level of two switching devices on one bridge arm, and the comparison result of the triangular wave amplitude and the other reference amplitude is used as the trigger level of two switching devices on the other bridge arm, so that the soft switching control of four switching devices in the main loop of the inverter power supply is realized; the logic of the two switching devices on each bridge arm is opposite.
Further, as shown in fig. 1 and fig. 2, two switching devices on one bridge arm are set to be VT1 and VT2, and two switching devices on the other bridge arm are set to be VT3 and VT 4; the trigger levels comprise level signals triggering VT1, VT2, VT3 and VT 4;
setting one-half triangular wave amplitude value as T0If the amplitude is adjusted to be delta, the amplitude of the triangular wave is greater than T0+ Δ, VT1 is high, VT2 is low; the amplitude of the triangular wave is lower than T0+ Δ, VT1 is low, VT2 is high; setting dead time τ between VT1 and VT20；
The amplitude of the triangular wave is greater than T0At- Δ, VT4 is high and VT3 is low; amplitude of triangular waveValue lower than T0At- Δ, VT4 is low and VT3 is high; setting dead time τ between VT3 and VT40；
The high level corresponds to the turn-on of the corresponding switching device and the low level corresponds to the turn-off of the corresponding switching device.
Where Δ is chosen in relation to β, the value of β being related to power regulation and output range.
The main loop of the inverter power supply is shown in fig. 2, wherein a module A and a module B are two bridge arms of full-bridge inversion respectively, in an inverter circuit with medium and low power, the two bridge arms of the inverter bridge are respectively composed of IGBT modules, and each IGBT module integrates 2 IGBT units. The equivalent resonant tank circuit may be equivalent to a series resonant LCR circuit. Wherein R iseqIs the equivalent resistance of the heating system, LeqIs equivalent inductance of the heating system, and C is resonance capacitance. The optimal working state of the main loop of the inverter power supply is a weak inductance resonance state, and the power switch tube works in a soft switch state at the moment. And the system working condition is relatively stable, namely the voltage and the current of the system have unique phase difference under constant frequency.
The specific working process of the main loop of the inverter under the inductive condition is as follows: selecting the frequency of the symmetrical triangular wave T12 as the frequency of an inverter system, and adopting 2 comparison values, namely T, for realizing PWM driving pulse of an inverter bridge power device0+ Δ and T0- Δ. Wherein, T0The value of + delta corresponds to the A-arm switching devices VT1 and VT2, T0The value of- Δ corresponds to B-leg switching devices VT3 and VT 4. I.e. when the amplitude of the triangular wave is greater than T0+ Δ, VT1 is high, when the amplitude of the triangle wave is lower than T0+ Δ, VT1 is low. For the lower arm VT2 of the A arm, the logic is the opposite of VT 1. In order to prevent the upper and lower arms from being conducted simultaneously, it is necessary to set the dead time τ between VT1 and VT20. PWM driving pulse of B bridge arm power device is T0-a value of Δ. When the amplitude of the triangular wave is larger than T0At- Δ, VT4 is high, otherwise it is low; the logic of VT3 is the opposite of VT 4. Like the A bridge arm, the B bridge arm also needs to prevent the upper bridge arm and the lower bridge arm from being conducted simultaneously, and the dead time tau is set0. As can be seen from FIG. 1, the phases of VT1 and VT3The potential difference being beta, the value of which is compared by two bridge arms, i.e. T0+ Δ and T0-a difference of Δ, i.e. by Δ. The larger Δ, the larger β.
τ0The selection principle comprises the following steps: the dead time may be set to 1 mus when the power device is selected as a P-MOSFET, and set to 2-3 mus when the power device is selected as an IGBT.
The generation process of the PWM driving pulse of the inverter bridge power device can be realized by a discrete electronic device or by the internal programming of an MCU processor.
The soft switch working process of the method of the invention is as follows:
the voltage waveform U can be obtained by adopting a frequency tracking technology based on a phase-locked loopABAnd current waveform IABIn phase, at this time, IABCurrent ratio UABFundamental wave U ofAB0The phase lag is beta/2, the system stably works in an inductive load state, and the resonant soft switching technology is facilitated.
The series resonant inverter operates under inductive conditions as follows:
a state: t is t0～t1In phase, VT1 and VT4 are turned on, VT2 and VT3 are turned off, the output voltage is positive, the output current is positive, and increases from 0, so VT1 belongs to zero current turn-on ZCON. At this time, the current flows to: DC + → VT1 → A → RLC slot → B → VT4 → DC-.
b state: t is t1～t2Phase, VT4 continues to conduct, VT1 at t1 +At that moment, the large current is turned off hard. At the moment of turn-off, the current in VT1 moves to C1, the circuit formed by C1 and C2 and the tank circuit works rapidly, C1 charges and C2 discharges. Since the charge-discharge time is very short, the current can be approximately considered to be constant. When C1 charges to near Ud and C2 discharges to near 0, VD2 is biased positive and naturally conducts.
c, state: t is t2～t3Phase, VT2 at t2 +At the moment, VD2 has already finished positive bias natural conduction, the voltage of VT2 is about 0.7V at the moment, VT2 is triggered at the moment, and zero current conduction ZVON belongs to. At this time, the DC power supply stops supplying power to the system, but the DC power supply still exists in the circuitThe current exists and works in a circulating current state, and the current is the energy existing in the tank circuit capacitor and the inductor. At this time, the current flows to: a → RLC slot → B → VT4 → DC- → VD 2.
d state: t is t3～t4Phase, where the current in the circuit is already close to 0, VT4 is at t3 +At time off, ZCOFF with approximately zero current.
e state: t is t4～t5Stage t of4 +At time VT3, which is turned on when the current is close to 0, and zero current conduction ZCON, VT3 and VT2 are both in the on state, the voltage on the tank is negative, the tank current is negative, and the negative direction increases from 0. At this time, the current flows to: DC + → VT3 → B → RLC slot → A → VT2 → DC-.
f state: t is t5～t6Phase, VT2 continues to conduct, VT3 at t5 +At that moment, the large current is turned off hard. At the moment of turn-off, the current in VT3 moves to C3, the circuit formed by C3 and C4 and the tank circuit works rapidly, C3 charges and C4 discharges. Since the charge-discharge time is very short, the current can be approximately considered to be constant. When C3 charges to near Ud and C4 discharges to near 0, VD4 is biased positive and naturally conducts.
g state: t is t6～t7Phase, VT4 at t6 +At the moment, VD4 has already finished positive bias natural conduction, the voltage of VT4 is about 0.7V at the moment, VT4 is triggered at the moment, and zero current conduction ZVON belongs to. At this time, the direct current power supply stops supplying power to the system, but current still exists in the circuit and works in a circulating current state, and the current at this time is energy existing in the tank circuit capacitor and the inductor. At this time, the current flows to: b → RLC slot → A → VT2 → DC- → VD 4.
h state: t is t7～t8Phase, where the current in the circuit is already close to 0, VT2 is at t7 +At time off, ZCOFF with approximately zero current. At t8At time VT1 is on, belonging to zero current conduction ZCON.
It should be noted that: when delta is 0, the current at the switching time of the b state and the f state is close to 0, and at the moment, if the proper dead time is controlled to be slightly larger than the switching time and the capacitor discharging time, the system completely works in a resonant soft switching state, the power factor angle is close to 0, and the power supply is in an optimal working state.
Fig. 4 is a schematic diagram of a control timing sequence of an inverter circuit in a conventional phase shift control manner, in the phase shift control method shown in fig. 4, the switching process of VT3 and VT4 belongs to high current switching, and are in the same bridge arm, and in most existing cases, VT3 and VT4 are in the same module, so that most of the heat generated by hard switching is borne by a single module.
In the method, firstly, the trigger impulse of each bridge arm is not a square wave but a PWM wave with adjustable duty ratio related to beta; second, the phase shift angle β is not achieved by the timing action of the reference arm and the phase shift arm, but rather by T0And setting and realizing the PWM comparison value of +/-delta. When the phase shift angle is close to 0, namely the maximum power output state, the two are basically the same; however, if a phase shift angle exists, the two are different. In the method of the invention, a possible high-current hard turn-off is performed by VT1 and VT3 switches, whereas VT1 and VT3 are usually packaged in different modules, and are therefore very advantageous for heat dissipation.
Still further, the method for calculating the output power of the main loop of the inverter power supply in the control method comprises the following steps:
when the main loop of the inverter works in an inductive resonance state, the fundamental frequency component U of the output voltage is invertedAB0Leading load current IABPhase β/2, and hence the load power factor angle β/2, where β is the phase difference between VT1 and VT 3; then the output voltage U is invertedABThe fourier expression of (a) is:
Figure BDA0002254455110000071
in the formula of UdThe direct current voltage of the main loop of the inverter power supply is used, and omega is the angular frequency of the inverter fundamental wave;
UABfundamental component U of (t)AB0(t) is:
Figure BDA0002254455110000072
UAB0(t) effective value UAB0Comprises the following steps:
Figure BDA0002254455110000073
let the fundamental current phase shift angle phi1Comprises the following steps:
Figure BDA0002254455110000074
in the formula0The phase angle between the load current and the inverted output voltage square wave;
then the load current IABEffective value I of fundamental component of (t)AB0Comprises the following steps:
Figure BDA0002254455110000075
wherein Z is the equivalent impedance of the load;
the output power P of the main loop of the inverter is:
Figure BDA0002254455110000076
still further, when the phase difference β between VT1 and VT3 is 0, the maximum value P of the output power P of the inverter main circuit is set to be 0mComprises the following steps:
Figure BDA0002254455110000077
still further, the per unit value of the active power of the main loop of the inverter power supply
Figure BDA0002254455110000078
Comprises the following steps:
Figure BDA0002254455110000081
still further, when phi0When the content is equal to 0, the content,
Figure BDA0002254455110000082
fig. 3 shows the relationship between the phase shift angle and the power adjustment process. As can be seen from FIG. 3,. phi0The larger the power regulation range of the system, the narrower the power regulation range.
In summary, the present invention uses symmetrical triangular waves as carrier signals, and 2 comparison values, i.e., T0+ Δ and T0- Δ, as PWM comparison values, to generate non-square wave trigger signals to control the inverter bridge arms, thereby implementing the control of the full-bridge inverter series resonance soft switch.
Although the invention herein has been described with reference to particular embodiments, it is to be understood that these embodiments are merely illustrative of the principles and applications of the present invention. It is therefore to be understood that numerous modifications may be made to the illustrative embodiments and that other arrangements may be devised without departing from the spirit and scope of the present invention as defined by the appended claims. It should be understood that features described in different dependent claims and herein may be combined in ways different from those described in the original claims. It is also to be understood that features described in connection with individual embodiments may be used in other described embodiments.

Claims (5)

1. A high-frequency induction heating series resonance soft switching inversion control method is characterized in that an inversion power supply main loop controlled by the inversion control method comprises a single-phase full-bridge type inversion circuit, the single-phase full-bridge type inversion circuit comprises two bridge arms, and each bridge arm comprises two switching devices; the main loop of the inverter works in an inductive resonance state;
the soft switching inversion control method adopts triangular waves with the same frequency as the main loop of the inversion power supply to obtain driving pulses for a switching device; selecting two reference amplitudes by taking the amplitude of the half triangular wave as a reference and combining with a set adjustment amplitude; the comparison result of the triangular wave amplitude and one of the reference amplitudes is used as the trigger level of two switching devices on one bridge arm, and the comparison result of the triangular wave amplitude and the other reference amplitude is used as the trigger level of two switching devices on the other bridge arm, so that the soft switching control of four switching devices in the main loop of the inverter power supply is realized; the logics of the two switching devices on each bridge arm are opposite;
setting two switching devices on one bridge arm as VT1 and VT2, and setting two switching devices on the other bridge arm as VT3 and VT 4; the trigger levels comprise level signals triggering VT1, VT2, VT3 and VT 4;
setting one-half triangular wave amplitude value as T0If the amplitude is adjusted to be delta, the amplitude of the triangular wave is greater than T0+ Δ, VT1 is high, VT2 is low; the amplitude of the triangular wave is lower than T0+ Δ, VT1 is low, VT2 is high; setting dead time τ between VT1 and VT20；
The amplitude of the triangular wave is greater than T0At- Δ, VT4 is high and VT3 is low; the amplitude of the triangular wave is lower than T0At- Δ, VT4 is low and VT3 is high; setting dead time τ between VT3 and VT40；
The high level corresponds to the turn-on of the corresponding switching device and the low level corresponds to the turn-off of the corresponding switching device.
2. The high-frequency induction heating series resonance soft-switching inverter control method according to claim 1,
the method for calculating the output power of the main loop of the inverter power supply in the control method comprises the following steps:
when the main loop of the inverter works in an inductive resonance state, the fundamental frequency component U of the output voltage is invertedAB0Leading load current IABPhase β/2, where β is the phase difference between VT1 and VT 3; then the output voltage U is invertedABThe fourier expression of (a) is:
Figure FDA0002927190910000011
in the formula of UdThe direct current voltage of the main loop of the inverter power supply is used, and omega is the angular frequency of the inverter fundamental wave;
UABfundamental component U of (t)AB0(t) is:
Figure FDA0002927190910000012
UAB0(t) effective value UAB0Comprises the following steps:
Figure FDA0002927190910000021
let the fundamental current phase shift angle phi1Comprises the following steps:
Figure FDA0002927190910000022
in the formula0The phase angle between the load current and the inverted output voltage square wave;
then the load current IABEffective value I of fundamental component of (t)AB0Comprises the following steps:
Figure FDA0002927190910000023
wherein Z is the equivalent impedance of the load;
the output power P of the main loop of the inverter is:
Figure FDA0002927190910000024
3. the method of claim 2The high-frequency induction heating series resonance soft switching inversion control method is characterized in that when the phase difference beta of VT1 and VT3 is 0, the maximum value P of the output power P of the main loop of the inversion power supply ismComprises the following steps:
Figure FDA0002927190910000025
4. the high-frequency induction heating series resonance soft-switching inversion control method according to claim 3, wherein a per unit value of active power of the main loop of the inverter power supply
Figure FDA0002927190910000026
Comprises the following steps:
Figure FDA0002927190910000027
5. the high-frequency induction heating series resonance soft-switching inverter control method according to claim 4, wherein when phi is0When the content is equal to 0, the content,
Figure FDA0002927190910000028
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