CN110571526B - Duplex horn antenna based on E-plane split waveguide - Google Patents
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/20—Frequency-selective devices, e.g. filters
- H01P1/207—Hollow waveguide filters
- H01P1/208—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
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Abstract
The invention discloses a duplex horn antenna based on an E-plane split waveguide, which comprises an E-plane horn, an E-plane split waveguide, an upper metal waveguide cavity and a lower metal waveguide cavity; one end of the E-plane split waveguide is connected with one end of the E-plane horn with small caliber, the other end of the E-plane split waveguide is connected with the upper metal waveguide cavity and the lower metal waveguide cavity, the other end of the upper metal waveguide cavity is connected with the current limiter through the signal input port, and the other end of the lower metal waveguide cavity is connected with the second signal input port through the waveguide elbow. The duplex horn antenna provided by the invention has the advantages of capability of receiving and transmitting signals simultaneously, high port isolation, high selectivity and flat gain; the structure is simple and reliable; the integration is easy; the antenna is suitable for a VSAT satellite communication antenna; can be used as a feed source of the parabolic antenna and can play a self-supporting role of the parabolic antenna.
Description
Technical Field
The invention relates to the technical field of wireless communication, in particular to a duplex horn antenna based on an E-plane split waveguide.
Background
The antenna and the microwave filter are key components indispensable in wireless communication systems, satellite communication systems, modern microwave relay communication systems and the like. The antenna itself is reversible, i.e. the same pair of antennas is used for transmitting and receiving electromagnetic signals. The main function of the microwave filter is to select the desired signal to filter out unwanted signals, and in a certain useful frequency range, to pass the useful signal in that frequency band with low loss, while attenuating the frequency components in other frequency ranges to very low levels. Therefore, the microwave filter of the antenna, as an important part of the wireless communication system, has a performance advantage that largely determines the advantages and disadvantages of the system, and at the same time, its size directly affects the size and portability of the entire system.
With the rapid development of the modern wireless communication demands, the demands of users for high-performance portable terminal devices are becoming more and more widespread, so miniaturization and integration are becoming new trends. The duplex antenna is designed by combining the antenna and the microwave filter, so that the structure of the radio frequency front-end system is more compact, unnecessary loss can be reduced, and the miniaturization and integration of the modern wireless communication system are easier to realize. In the typical communication system in the past, the antenna and the filter are often designed separately as two independent subsystems, however, due to the mutual influence between the devices and the mismatch between ports, the overall performance of the system after cascading is easily deteriorated, and the loss of the system is increased. To eliminate this effect, an additional matching network is required between the two, which tends to complicate the system even more. The size is also larger, which is disadvantageous for the realization of miniaturization. Therefore, the antenna and the filter are directly integrated, and a matching network which is additionally needed to be added can be omitted, so that the size and the weight of the system can be reduced, the loss can be reduced, and the whole performance of the system is improved.
The duplex filter antenna can simultaneously realize the functions of transmitting and receiving, filtering, receiving and transmitting separation and anti-interference of wireless electromagnetic waves by one component, can realize the high efficiency, low cost and light weight of integrated wireless equipment, and can be widely applied to wireless communication systems, satellite communication systems, modern microwave relay communication and other systems. The existing microstrip duplex antenna generally has the defects of low port isolation, larger antenna receiving and transmitting frequency interval, narrower bandwidth and low antenna gain, so that the microstrip duplex antenna still needs to be further researched.
Disclosure of Invention
The invention aims to solve the defects in the prior art that the waveguide horn antenna is difficult to have both the filtering characteristic and the duplex characteristic, and provides the duplex horn antenna based on the E-plane split waveguide, which has the advantages of simple structure, easy tuning, good frequency selectivity, flat gain and the like.
The invention is realized at least by one of the following technical schemes.
A duplex filter feedhorn based on an E-plane splitting waveguide, said duplex filter feedhorn comprising: the device comprises an E-plane horn, an E-plane split waveguide, an upper metal waveguide cavity and a lower metal waveguide cavity; one end of the E-plane split waveguide is connected with one end of the E-plane horn with small caliber, the other end of the E-plane split waveguide is connected with the upper metal waveguide cavity and the lower metal waveguide cavity, the other end of the upper metal waveguide cavity is connected with the current limiter through the signal input port, and the other end of the lower metal waveguide cavity is connected with the second signal input port through the waveguide elbow.
Further, a space exists between the upper metal waveguide cavity and the lower metal waveguide cavity.
Furthermore, the E surface of the E surface loudspeaker (broadside) is opened, and the H surface (narrow side) is unchanged, so that the radiation gain and the directionality of the filter antenna are improved, and the effect of reducing side lobes is achieved.
Further, the upper metal waveguide cavity is divided into an upper channel first resonant cavity, an upper channel second resonant cavity and an upper channel third resonant cavity by a first pair of inductive diaphragms, a second pair of inductive diaphragms, a third pair of inductive diaphragms and a fourth pair of inductive diaphragms in sequence; the capacitive diaphragm, the current limiter and the signal input port form a fourth resonant cavity;
the lower metal waveguide cavity is divided into a lower channel first resonant cavity, a lower channel second resonant cavity and a lower channel third resonant cavity by a fifth pair of inductive diaphragms, a sixth pair of inductive diaphragms, a seventh pair of inductive diaphragms and an eighth pair of inductive diaphragms in sequence.
Further, the upper metal waveguide cavity and the lower metal waveguide cavity are rectangular waveguide cavities.
Further, the first pair of inductive diaphragms, the second pair of inductive diaphragms, the third pair of inductive diaphragms and the fourth pair of inductive diaphragms are respectively used as four impedance inversion converters to form a three-order chebyshev filter.
Further, the fifth pair of inductive diaphragms, the sixth pair of inductive diaphragms, the seventh pair of inductive diaphragms and the eighth pair of inductive diaphragms are respectively used as four impedance inversion converters to form a three-order chebyshev filter.
Further, the first resonant cavity, the second resonant cavity, the third resonant cavity, the capacitive diaphragm, the current limiter and the signal input port of the upper channel form a fourth resonant cavity, and working main modes of the first resonant cavity, the second resonant cavity, the third resonant cavity and the fourth resonant cavity are TE101 modes.
Further, the working main modes of the three resonant cavities of the first resonant cavity of the lower channel, the second resonant cavity of the lower channel and the third resonant cavity of the lower channel are TE101 modes.
Furthermore, the current limiter is of a cavity concave structure and is equivalent to an inductor, and is used for adding a transmission zero point to play a role in improving the isolation of the port; while a capacitive diaphragm is introduced to counteract the effect of the current limiter.
Further, the first signal input port and the second signal input port are rotated 90 degrees for installation and testing, wherein the first signal input port is connected with the current limiter and the second signal input port is connected with the waveguide turn.
The invention passes through an E-plane loudspeaker, an E-plane split waveguide, a transmitting channel inductance diaphragm type 3-order chebyshev filter and a receiving channel inductance diaphragm type 3-order chebyshev filter loaded on the upper side and the lower side of the E-plane split waveguide, a transmitting channel current limiter, a receiving channel waveguide elbow, a transmitting port and a receiving port. The antenna has both a filtering characteristic and a radiating characteristic, wherein the filtering characteristic has a duplex characteristic and is generated by two channel filters, namely an upper channel filter and a lower channel filter, of a split waveguide, and the radiating characteristic is generated by an E-plane loudspeaker. By adjusting the width of the windows of the inductive film sheets and the distance between adjacent inductive film sheets, the coupling strength between adjacent resonant cavities, the external quality factor of the filter and the radiation quality factor of the antenna can be controlled. By introducing a current limiter, the isolation of the two ports is improved; by introducing the E-plane horn, the radiation gain and the directivity of the antenna can be improved, and side lobes can be reduced. The duplex horn antenna provided by the invention has the advantages of capability of receiving and transmitting signals simultaneously, high port isolation, high selectivity and flat gain; the structure is simple and reliable; the integration is easy; the antenna is suitable for a VSAT satellite communication antenna; can be used as a feed source of the parabolic antenna and can play a self-supporting role of the parabolic antenna.
Compared with the prior art, the invention has the following advantages and effects:
1. the duplex horn antenna based on the E-plane split waveguide has the filtering characteristic, the duplex characteristic and the radiation characteristic, wherein the filtering characteristic is generated by two filters formed by an upper channel and a lower channel, the duplex characteristic is generated by the E-plane split waveguide and the filters formed by the two channels, and the radiation characteristic is generated by the E-plane horn.
2. The coupling strength between adjacent resonant cavities, the external quality factor of the filter and the radiation quality factor of the antenna can be controlled by adjusting the width of the inductive film sheet window, the filtering characteristic can be controlled by adjusting the distance between the adjacent inductive film sheet windows, and the fourth order of the filter can be used by adjusting the height and the length of the current limiter, the height of the capacitive film sheet and the distance between the capacitive film sheet and the input port in the upper channel filter, and the isolation degree of the two ports can be improved.
3. When the E-plane horn, the E-plane split waveguide, the upper and lower channel filters and the signal input port are well connected and matched, the E-plane split waveguide duplex horn antenna can be formed, meanwhile, the E-plane split waveguide duplex horn antenna has the filtering characteristic, the duplex characteristic and the radiation characteristic, the radiation gain and the directivity of the antenna can be improved, and the side lobes are reduced.
4. The duplex filtering antenna provided by the invention has the following advantages: the insertion loss is small; the filter has good passband standing wave characteristics and higher out-of-band attenuation; the gain is flat; high selectivity; low side lobes; low cross polarization; the structure is simple and reliable; the integration is easy; the processing is easy; is suitable for various communication systems.
Drawings
Fig. 1 is a perspective structure diagram of an E-plane splitting waveguide duplex horn antenna according to the present embodiment;
fig. 2 is a front view of the E-plane splitting waveguide duplex horn antenna according to the present embodiment;
fig. 3 is a top view of the E-plane splitting waveguide duplex horn antenna according to the present embodiment;
fig. 4 is a perspective view of an upper channel signal input port of the E-plane splitting waveguide duplex horn antenna according to the present embodiment;
fig. 5 is a perspective view of a lower channel signal input port of the E-plane splitting waveguide duplex horn antenna according to the present embodiment;
FIG. 6 is a graph of simulated S-parameters for the E-plane split waveguide duplex horn antenna of the present embodiment;
FIG. 7 is a graph showing the variation of the simulation gain of the antenna according to the present embodiment with frequency;
FIG. 8 is a yoz face simulation pattern for an excitation with a transmit port frequency of 11.5GHz in this embodiment;
FIG. 9 is a xoz face simulation pattern for an excitation with a transmit port frequency of 11.5GHz in this example;
FIG. 10 is a yoz face simulation pattern of the excitation at 14.5GHz emission port frequency of the present embodiment;
FIG. 11 is a xoz face simulation pattern for a 14.5GHz excitation at the transmit port of this embodiment;
wherein: the horn comprises a 1-E surface horn, a 2-E surface split waveguide, a 3-upper layer metal waveguide cavity, a 4-lower layer metal waveguide cavity, a 5-first pair of inductive diaphragms, a 6-second pair of inductive diaphragms, a 7-third pair of inductive diaphragms, a 8-fourth pair of inductive diaphragms, a 9-fifth pair of inductive diaphragms, a 10-sixth pair of inductive diaphragms, a 11-seventh pair of inductive diaphragms, a 12-eighth pair of inductive diaphragms, a 13-capacitive diaphragm, a 14-restrictor, a 15-waveguide corner, a 16-first signal input port, a 17-second signal input port, a 18-upper channel first resonant cavity, a 19-upper channel second resonant cavity, a 20-upper channel third resonant cavity, a 21-fourth resonant cavity, a 22-lower channel first resonant cavity, a 23-lower channel second resonant cavity and a 24-lower channel third resonant cavity.
Detailed Description
For the purpose of making the objects, technical solutions and advantages of the embodiments of the present invention more apparent, the technical solutions of the present invention will be clearly and completely described below with reference to the accompanying drawings in the embodiments of the present invention, and it is apparent that the described embodiments are some embodiments, but not all embodiments of the present invention. All other embodiments, which can be made by those skilled in the art without creative efforts, are within the protection scope of the present invention based on the embodiments in the present novel embodiments.
As shown in fig. 1, a duplex horn antenna based on an E-plane split waveguide of the present embodiment includes: the E-plane horn 1, the E-plane split waveguide 2, the upper metal waveguide cavity 3 and the lower metal waveguide cavity 4; one end of the E-plane split waveguide 2 is connected with one small-caliber end of the E-plane loudspeaker 1, and the other end is connected with the upper metal waveguide cavity 3 and the lower metal waveguide cavity 4 for separating receiving and transmitting signals. The other end of the upper metal waveguide cavity 3 is connected with a current limiter 14 through a signal input port 16, and the other end of the lower metal waveguide cavity 4 is connected with a second signal input port 17 through a waveguide elbow 15.
The upper metal waveguide cavity 3 is divided into an upper channel first resonant cavity 18, an upper channel second resonant cavity 19 and an upper channel third resonant cavity 20 by a first pair of inductive diaphragms 5, a second pair of inductive diaphragms 6, a third pair of inductive diaphragms 7 and a fourth pair of inductive diaphragms 8 in sequence, and meanwhile, the capacitive diaphragm 13, the current limiter 14 and the signal input port 16 form a fourth resonant cavity 21;
the lower metal waveguide cavity 4 is divided into a lower channel first resonant cavity 22, a lower channel second resonant cavity 23 and a lower channel third resonant cavity 24 by a fifth pair of inductive diaphragms 9, a sixth pair of inductive diaphragms 10, a seventh pair of inductive diaphragms 11 and an eighth pair of inductive diaphragms 13 in sequence.
As shown in fig. 2 and 3, the E-plane split waveguide duplex horn antenna structure is symmetrical. Fig. 2 is a front view of fig. 1, wherein: the thickness of all the diaphragms is 1mm, the width A of the large-caliber end of the E-plane loudspeaker 1 is 19.05mm, the loudspeaker height H is 25mm, the distance dH between the upper metal waveguide cavity 3 and the lower metal waveguide cavity 4 and between the upper channel and the lower channel is 1mm, the length of the channels is LL=LH=70.3 mm, and the distances between the diaphragms between the upper channels are L respectively 10 ＝8mm，L 11 ＝14.42mm，L 12 ＝15.5mm，L 13 The distance between the membranes between the lower channels is L 20 ＝9.38mm，L 21 ＝9.3mm，L 22 ＝11.766mm，L 23 =10.76 mm, height of channel W 1 The capacitive diaphragm 13 has a height a=3.65 mm, distance X from the signal input port 16, =4.65 mm 3 10mm, signal input port 16 width W 2 Flow restrictor 14 length b=3.5 mm, height c=1 mm, signal input port 17 width W =9.525 mm 2 =9.525 mm, waveguide turn 15 inclination angle α=45°, X 1 ＝0.5*W 1 ，X 2 ＝0.5*W 2 。
Fig. 3 is a plan view of fig. 1, in which the width of the waveguide is equal to the width of the large diameter end of the horn, a=19.05 mm, and the distances between the first pair of inductive diaphragms 5, the second pair of inductive diaphragms 6, the third pair of inductive diaphragms 7 and the fourth pair of inductive diaphragms 8 in the upper metal waveguide cavity 3 are S 11 ＝13.3mm，S 12 ＝8.7mm，S 13 ＝8.4mm，S 14 =12.9 mm; the fifth pair of inductive diaphragms 9, the sixth pair of inductive diaphragms 10, the seventh pair of inductive diaphragms 11 and the eighth pair of inductive diaphragms 13 in the lower metal waveguide cavity 4 are respectively provided with a distance S 21 ＝10.66mm，S 22 ＝6.1mm，S 23 ＝6.1mm，S 24 ＝9mm。
The E-plane loudspeaker 1 has the advantages that the E-plane loudspeaker 1 is opened, the H-plane is unchanged, the E-plane loudspeaker is used for radiation gain and directionality of a manuscript filtering antenna, and the E-plane loudspeaker has the function of reducing side lobes.
The upper metal waveguide cavity 3 and the lower metal waveguide cavity 4 are rectangular waveguides.
The first pair of inductive diaphragms 5, the second pair of inductive diaphragms 6, the third pair of inductive diaphragms 7 and the fourth pair of inductive diaphragms 8 are respectively used as four impedance inversion converters to form a three-order chebyshev filter.
The fifth pair of inductive diaphragms 9, the sixth pair of inductive diaphragms 10, the seventh pair of inductive diaphragms 11 and the eighth pair of inductive diaphragms 12 respectively serve as four impedance inversion converters to form a three-order chebyshev filter.
The working main modes of the upper channel first resonant cavity 18, the second resonant cavity 19, the third resonant cavity 20 and the fourth resonant cavity 21 are TE101 modes.
The working main modes of the lower channel first resonant cavity 22, the second resonant cavity 23 and the third resonant cavity 24 are TE101 modes.
As shown in fig. 4 and fig. 5, the current limiter 14 is a cavity concave structure, is a current limiter for improving the isolation of the port, and can be equivalently an inductor, and is used for adding a transmission zero point to play a role in improving the isolation of the port; while a capacitive diaphragm 13 is introduced for counteracting the effect of the current limiter 14. In the figure, the channel width is a=19.05 mm, the height W 1 =4.65 mm, capacitanceThe height of the sexual film 13 is a=3.65 mm, and the distance X from the signal input port 16 is the same 3 10mm, signal input port 16 width W 2 Flow restrictor 14 length b=3.5 mm, height c=1 mm =9.525 mm.
The first signal input port 16 and the second signal input port 17 are rotated 90 degrees for installation and testing, wherein the first signal input port is connected to the restrictor 14 and the second signal input port 17 is connected to the waveguide turn 15.
Fig. 5 is a lower port signal input port, with specific numbering and sizing as shown. In the figure, the channel width is a=19.05 mm, the height W 1 Signal input port 17 width w=4.65mm 2 =9.525 mm, waveguide turn 15 inclination angle α=45°, X 1 ＝0.5*W 1 ，X 2 ＝0.5*W 2 。
When the center frequency f is required Hair brush ＝11.5GHz，f Collecting and recovering At=14.5 GHz, the signal input and output ports employ standard rectangular waveguides BJ120, all with a thickness of Δs=1 mm. And simulating and optimizing the structure by adopting three-dimensional simulation software HFSS.
When transmitting, a signal is sent in from a transmitting port, namely a first signal input port 16, and is transmitted to the E-plane loudspeaker 1 through the upper metal waveguide cavity 3, the capacitive diaphragm 13, the fourth pair of inductive diaphragms 8 of the diaphragm of the upper metal waveguide cavity 3, the third pair of inductive diaphragms 7, the second pair of inductive diaphragms 6 and the first pair of inductive diaphragms 5, and radiated by the E-plane loudspeaker 1.
When receiving, the receiving signal is received from the E-plane loudspeaker 1, and the E-plane loudspeaker 1 outputs the received signal from the receiving port, namely the second signal input port 17, through the fifth pair of inductive diaphragms 9, the sixth pair of inductive diaphragms 10, the seventh pair of inductive diaphragms 11 and the eighth pair of inductive diaphragms 12 in the lower metal waveguide cavity 4.
The signal input port 16 of the antenna operates in a frequency band having a center frequency of 11.5 GHz; the receive port 17 operates in the frequency band with a center frequency of 14.5 GHz.
Fig. 6 shows a simulated S-curve of an embodiment duplex filter antenna. The horizontal axis represents the frequency of the input signal, ranging from 10GHz to 16GHz, the vertical axis represents the logarithmic magnitude dB of the S parameter, the 1612.6dB reflection loss of the antenna transmitting port ranges from 10.91GHz to 12.24GHz, the relative bandwidth is 11.5%, and the 1712.4dB reflection loss of the receiving port ranges from 13.98GHz to 15GHz, and the relative bandwidth is 7%. The isolation of both ports is greater than 47dB in both bands.
Fig. 7 shows the gain simulation results of the duplex filter antenna of the embodiment. The horizontal axis represents the frequency of the input signal, ranging from 10GHz to 16GHz, the vertical axis represents the gain (dB), the gain of the low-frequency channel is about 8.4dB, and the gain of the high-frequency channel is about 9.4dB in the working frequency range of the antenna. The antenna has the advantages of flat gain, high selectivity, high out-of-band rejection and the like.
Fig. 8 and 9 are simulation results of an E-plane pattern (yoz plane) and an H-plane pattern (xoz plane) at a center frequency of 11.5GHz of the filter antenna of the embodiment, respectively, and it is seen from the figures that the E-plane cross polarization is less than-35 dB, and the H-plane cross polarization is less than-40 dB.
Fig. 10 and 11 are simulation results of an E-plane pattern (yoz plane) and an H-plane pattern (xoz plane) at a center frequency of 14.5GHz of the filter antenna of the embodiment, respectively, and it is seen that the E-plane cross polarization is less than-30 dB, and the H-plane cross polarization is less than-40 dB.
The above examples are preferred embodiments of the present invention, but the embodiments of the present invention are not limited to the above examples, and any other changes, modifications, substitutions, combinations, and simplifications that do not depart from the spirit and principle of the present invention should be made in the scope of the present invention.
Claims (7)
1. A duplex horn antenna based on E-plane splitting waveguide, wherein said duplex filtering horn antenna comprises: the device comprises an E-plane loudspeaker (1), an E-plane split waveguide (2), an upper metal waveguide cavity (3) and a lower metal waveguide cavity (4); one end of the E-plane split waveguide (2) is connected with one small-caliber end of the E-plane loudspeaker (1), the other end of the E-plane split waveguide is connected with the upper metal waveguide cavity (3) and the lower metal waveguide cavity (4), the other end of the upper metal waveguide cavity (3) is connected with the current limiter (14) through the first signal input port (16), and the other end of the lower metal waveguide cavity (4) is connected with the second signal input port (17) through the waveguide elbow (15);
the upper metal waveguide cavity (3) comprises a fourth resonant cavity (21) formed by sequentially dividing a first pair of inductive diaphragms (5), a second pair of inductive diaphragms (6), a third pair of inductive diaphragms (7) and a fourth pair of inductive diaphragms (8) into an upper channel first resonant cavity (18), an upper channel second resonant cavity (19) and an upper channel third resonant cavity (20), and a capacitive diaphragm (13), a current limiter (14) and a first signal input port (16); the capacitive diaphragm (13) is used for counteracting the action of the current limiter (14);
the lower metal waveguide cavity (4) is divided into a lower channel first resonant cavity (22), a lower channel second resonant cavity (23) and a lower channel third resonant cavity (24) by a fifth pair of inductive diaphragms (9), a sixth pair of inductive diaphragms (10), a seventh pair of inductive diaphragms (11) and an eighth pair of inductive diaphragms (12) in sequence;
the first pair of inductive diaphragms (5), the second pair of inductive diaphragms (6), the third pair of inductive diaphragms (7) and the fourth pair of inductive diaphragms (8) are respectively used as four impedance inversion converters to form a three-order chebyshev filter; the fifth pair of inductive diaphragms (9), the sixth pair of inductive diaphragms (10), the seventh pair of inductive diaphragms (11) and the eighth pair of inductive diaphragms (12) are respectively used as four impedance inversion converters to form a three-order chebyshev filter.
2. A duplex horn antenna based on E-plane splitting waveguides according to claim 1, characterized in that there is a spacing between the upper (3) and lower (4) metal waveguide cavities.
3. A duplex horn antenna based on E-plane splitting waveguides according to claim 1, wherein the upper (3) and lower (4) metal waveguide cavities are rectangular waveguide cavities.
4. A duplex horn antenna based on E-plane splitting waveguide according to claim 3, wherein the main modes of operation of the upper channel first resonant cavity (18), the upper channel second resonant cavity (19), the upper channel third resonant cavity (20) and the fourth resonant cavity (21) are TE101 modes.
5. The duplex horn antenna based on the E-plane splitting waveguide according to claim 1, wherein the three main modes of operation of the lower channel first resonant cavity (22), the lower channel second resonant cavity (23) and the lower channel third resonant cavity (24) are TE101 modes.
6. The duplex horn antenna based on the E-plane splitting waveguide according to claim 1, wherein the current limiter (14) is a cavity concave structure, equivalent to an inductor, and is used for adding a transmission zero point to improve the isolation of the port.
7. A duplex horn antenna based on E-plane splitting waveguides according to claim 1, characterized in that the first signal input port (16) and the second signal input port (17) are rotated 90 degrees for installation and testing, wherein the first signal input port is connected to a current limiter (14) and the second signal input port (17) is connected to a waveguide turn (15).
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|---|---|---|---|---|
| CN106450749A (en) * | 2016-11-14 | 2017-02-22 | 华南理工大学 | Pyramid horn filtering antenna based on waveguide structure |
| CN211789546U (en) * | 2019-09-27 | 2020-10-27 | 华南理工大学 | Duplex horn antenna based on E-plane split waveguide |
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| Publication number | Publication date |
|---|---|
| CN110571526A (en) | 2019-12-13 |
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