CN110417131B - Fundamental wave-harmonic wave parallel energy transmission multichannel non-contact power supply system - Google Patents
Fundamental wave-harmonic wave parallel energy transmission multichannel non-contact power supply system Download PDFInfo
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Abstract
The invention discloses a multi-channel non-contact power supply system for fundamental wave-harmonic wave parallel energy transmission, which comprises a primary side circuit, a non-contact transformer and a secondary side circuit. The primary side circuit comprises a cascade inverter circuit and a primary side compensation network, and the primary side compensation network is a multi-frequency resonance circuit. The secondary side of the non-contact transformer is wound with a main winding and one or more auxiliary windings, and the main winding and the auxiliary windings share a magnetic core. The secondary side circuit comprises a plurality of channel units, each channel unit comprises a cascade secondary side compensation network and a rectifying and filtering circuit, the secondary side compensation network is formed by connecting a resonance network and a frequency selection network, and the primary winding and the auxiliary winding are respectively connected with one channel unit. The frequency selection network is used for blocking other frequency currents except the resonant frequency of the channel from passing through, and the frequency selection network in each channel unit realizes decoupling of fundamental waves and odd harmonics. The invention utilizes abundant harmonic energy in the non-contact system under the existing strong coupling condition, and realizes decoupling control of fundamental waves and harmonic waves.
Description
Technical Field
The invention relates to a non-contact power supply technology, in particular to a non-contact power supply system for fundamental wave-harmonic wave parallel energy transmission, which is particularly suitable for a wireless power supply system with small air gap and rotating occasions.
Background
The non-contact power supply adopts a non-contact transformer with completely separated primary and secondary sides to realize wireless power transmission (Wireless Power Transmission, WPT) through magnetic field coupling. Compared with the traditional contact type power supply, the non-contact type power supply has the advantages of safety, convenience, no spark, no abrasion, no maintenance and the like. Has wide application in the fields of aerospace, transportation, medical equipment, mobile communication and the like. Particularly, in some occasions needing to be powered by rotating equipment, such as mechanical conductive slip rings for realizing energy transmission and information interaction through dynamic contact of electric brushes and conductive rings, the electric brushes and the conductive rings are easy to wear, strike fire, accumulate dust and the like due to friction in the rotating process.
To avoid wear, the mechanical contact slip ring may be replaced by a non-contact slip ring (CS, contactless Sliprings), the core of which is a non-contact rotary transformer based on WPT technology. However, up to the present, the non-contact power supply system still has the problems of low efficiency, large electromagnetic radiation and the like. The low coupling coefficient of the non-contact transformer is a key factor for limiting the efficiency improvement of the system. At present, a planarized non-contact transformer structure is adopted, and the dead area of the transformer is increased, so that the magnetic resistance of a primary side coupling magnetic circuit and a secondary side coupling magnetic circuit of the non-contact transformer is not overlarge when an air gap is large, and the coupling coefficient of the non-contact transformer is improved as much as possible. The non-contact rotary transformer used in the non-contact slip ring system has the air gap of the primary side and the secondary side within 10mm, the coupling coefficient is generally larger than 0.5 through the magnetic field optimization design, the non-contact slip ring coupling coefficient in the category .A.Abdolkhani,A.P.Hu and N.C.Nair,"A Double Stator Through-hole Type Contactless Slipring for Rotary Wireless Power Transfer Applications,"in IEEE Transactions on Energy Conversion,vol.29,no.2,pp.426-434,June 2014 of strong coupling in WPT is 0.81, and the system efficiency can reach 98.8 percent at most. However ,G.He,Q.Chen,P.Xin and X.Chen,"Analysis,and correction of soft switching missing phenomenon in high coupling coefficient WPT system,"2017 IEEE PELS Workshop on Emerging Technologies:Wireless Power Transfer(WoW),Chongqing,2017,pp.1-6 proposes that under the condition of strong coupling, as the coupling coefficient increases, the harmonic content, especially the third harmonic content, in the resonance network of the non-contact power supply system increases and decreases, and has an extremely high peak value, and the coupling coefficient is greatly increased when the coupling coefficient is higher. The fundamental wave and the harmonic wave currents are mutually coupled, so that the characteristics of the non-contact power supply system, such as input phase angle, output gain and the like, are changed, the design and control difficulty is increased, and the further improvement of the system efficiency is limited.
In order to reduce harmonic content in the non-contact power supply system, LC connected in series in a compensation network can be used for reducing input current harmonic, or regulating the duty ratio of output voltage of a primary inverter bridge, switching time of a switching tube is controlled to eliminate specific times of harmonic .Cai H,Shi L,Li Y.Harmonic-Based Phase-Shifted Control of Inductively Coupled Power Transfer[J].IEEE Transactions on Power Electronics,2013,29(2):594-602, phase shift control is used for reducing switching frequency to one third or one fifth of fundamental frequency, and power is transferred in the non-contact power supply system by using third or fifth harmonic. This, while beneficial for reducing system volume and weight, tends to increase current amplitude by delivering the same power due to the smaller harmonic voltage amplitude, resulting in increased conduction losses and copper losses in the inverter circuit.
Whether harmonic wave is restrained or harmonic wave energy is utilized through measures such as reducing system frequency, fundamental wave and harmonic energy in a non-contact power supply system cannot be fully utilized, and a fundamental wave-third harmonic dual-channel system is preferably provided in a transmission .Xia,C.-Y.Xia,W.-T.Zhu,N.Ma,R.-H.Jia,and Q.Yu,"A Load Identification Method for ICPT System Utilizing Harmonics,"Journal of Electrical Engineering and Technology,vol.13,no.6,pp.2178–2186,Nov.2018 of fundamental wave and harmonic wave simultaneously, an independent compensation network is adopted by primary two channels, symmetrical two groups of fundamental wave channel coils and harmonic channel coils are adopted by a transformer for eliminating cross coupling, currents with different frequencies are separated by two auxiliary transformers in a dual-channel system in a complicated .Z.Ding,F.Liu,Y.Yang,X.Chen and R.M.Kennel,"High-Efficiency Design and Close-loop Power Distribution Control for Double-Frequency Double-Load Magnetically Coupled Resonant Wireless Power Transfer System,"2019 IEEE Applied Power Electronics Conference and Exposition(APEC),Anaheim,CA,USA,2019,pp.3111-3116 structure, the structure is not simple, and the two frequencies cannot be far apart for guaranteeing high efficiency.
Disclosure of Invention
The invention aims to: aiming at the prior art, a multi-channel non-contact power supply system for fundamental wave-harmonic wave parallel energy transfer is provided, and the abundant harmonic wave energy in the non-contact system under the existing strong coupling condition is utilized to realize decoupling control of the fundamental wave and the harmonic wave.
The technical scheme is as follows: a multi-channel non-contact power supply system for fundamental wave-harmonic wave parallel energy transmission comprises a primary side circuit, a non-contact transformer and a secondary side circuit; the primary side circuit comprises a cascade inverter circuit and a primary side compensation network, and the primary side compensation network is a multi-frequency resonant circuit; the secondary side of the non-contact transformer is wound with a main winding and one or more auxiliary windings, and the main winding and the auxiliary windings share a magnetic core; the secondary side circuit comprises a plurality of channel units, each channel unit comprises a cascade secondary side compensation network and a rectifying and filtering circuit, the secondary side compensation network is formed by connecting a resonance network and a frequency selection network, and the main winding and the auxiliary winding are respectively connected with one channel unit; the frequency selection network is used for blocking other frequency currents except the resonant frequency of the channel from passing through, and the frequency selection network in each channel unit realizes decoupling of fundamental waves and odd harmonics.
Further, the multi-frequency resonance circuit is an LC ladder network which takes series inductance and parallel capacitance as basic units or a high-order network which takes series-parallel LC as basic units; in the LC ladder network, when the number of LC units is n, the resonance of n frequency points in fundamental wave and each odd harmonic frequency is realized, and the primary side output current gain is irrelevant to the equivalent load of a primary side circuit through the design of LC network parameters.
Further, the inductance elements in the multi-frequency resonance circuit adopt coupling inductances which are mutually coupled.
Further, if the multi-frequency resonant circuit is a fourth-order LC ladder resonant network, and the fundamental wave and the third harmonic are simultaneously resonant, the network parameters satisfy the following conditions:
Wherein, L A、CA、LB、CB is two inductances and two capacitances in the four-order LC ladder type resonant network respectively, omega _1 is fundamental wave frequency, and G _1、G_3 is fundamental wave and third harmonic constant current gain value respectively.
Further, the primary side circuit also comprises an input phase angle adjusting unit.
Further, the resonance network of the secondary circuit is a capacitor or an LC hybrid network connected in series or in parallel with the main winding and the auxiliary winding respectively, and the frequency-selecting network is an LC hybrid network.
Furthermore, when the resonance networks of the secondary side circuits are all connected in series in each channel unit network to realize constant-voltage output of each channel unit, the multi-channel units are output in series combination; when the resonance network of the secondary side circuit is connected in parallel in each channel unit network, and constant current output of each channel unit is realized, the multichannel units are output in parallel.
Furthermore, the switching tube of the inverter circuit of the primary side circuit is subjected to closed-loop control or the rectifying and filtering circuit of the secondary side circuit is subjected to closed-loop control by adopting a controllable rectifying circuit, so that the output voltage or power of the system is regulated and controlled.
The beneficial effects are that: 1. the primary side adopts a multi-frequency resonance network, namely, the primary side only needs one channel, and the corresponding non-contact transformer also only needs one primary side winding, thereby being beneficial to reducing the whole volume and weight of the system and improving the power density;
2. The invention adopts multichannel parallel transmission of fundamental wave and harmonic wave energy, effectively utilizes abundant harmonic wave energy in the non-contact transformer under the strong coupling condition, realizes decoupling control of the fundamental wave and the harmonic wave, is beneficial to further improving the efficiency of the non-contact transformer, and simultaneously brings convenience for the combination output of multichannel series-parallel connection.
Drawings
FIG. 1 is a schematic diagram of a fundamental wave-harmonic wave multichannel parallel energy transmission system;
FIG. 2 is a schematic diagram of a primary multi-frequency resonant network topology according to the present invention;
FIG. 3 is a schematic diagram of a primary-side multi-frequency resonant network according to the present invention;
FIG. 4 is a block diagram of a constant pressure type output dual channel system of the present invention;
FIG. 5 is a block diagram of a constant current type output dual channel system of the present invention;
FIG. 6 is a diagram of a decoupling equivalent circuit of a primary side dual-frequency network using a coupling inductor in the present invention;
FIG. 7 is a schematic diagram of a cross-sectional structure of a rotary disk type non-contact transformer according to the present invention;
FIG. 8 is a schematic diagram of a cross-sectional structure of a rotary disk type non-contact transformer according to the present invention;
FIG. 9 is a schematic diagram of a cross-sectional structure of a rotary column type non-contact transformer according to the present invention;
FIG. 10 is a schematic diagram showing a cross-sectional structure of a rotary column type non-contact transformer according to the present invention;
FIG. 11 is a schematic diagram of a constant voltage type dual-channel output series structure of the present invention;
FIG. 12 is a schematic diagram of a constant current type dual channel output parallel structure of the present invention;
FIG. 13 is a diagram of an equivalent circuit of the primary constant current source of the dual channel system of the present invention;
FIG. 14 is a schematic diagram of the closed loop control of the primary inverter circuit of the multi-channel system of the present invention;
FIG. 15 is a schematic view of the secondary side multichannel switching control of the invention by a relay;
FIG. 16 is a schematic diagram of a closed-loop control of each harmonic channel controlled rectification of the secondary side of the present invention;
FIG. 17 is a graph of current gain for a primary side dual frequency resonant network in accordance with the present invention;
FIG. 18 is a graph of a constant voltage output DC voltage gain sweep of a dual channel system of the present invention;
FIG. 19 is a graph showing a second constant voltage type output DC voltage gain sweep frequency curve of the dual-channel system of the present invention;
FIG. 20 is a graph of a constant current output DC gain sweep of a dual channel system of the present invention;
FIG. 21 is a graph of a constant current output DC gain sweep of a dual channel system of the present invention;
In the figure: 1-primary side magnetism, 2-secondary side magnetism, 3-primary side coil, 4-secondary side main winding coil, 5-secondary side auxiliary winding coil, 6-air gap, 7-rotating shaft and 8-acrylic connector.
Detailed Description
The invention is further explained below with reference to the drawings.
A multi-channel non-contact power supply system for parallel energy transfer of fundamental wave and harmonic wave comprises a primary side circuit, a non-contact transformer and a secondary side circuit. The primary side circuit comprises a cascade inverter circuit and a primary side compensation network, and the primary side compensation network is a multi-frequency resonance circuit. The secondary side of the non-contact transformer is wound with a main winding and one or more auxiliary windings, and the main winding and the auxiliary windings share a magnetic core. The secondary side circuit comprises a plurality of channel units, each channel unit comprises a cascade secondary side compensation network and a rectifying and filtering circuit, the secondary side compensation network is formed by connecting a resonance network and a frequency selection network, and the primary winding and the auxiliary winding are respectively connected with one channel unit. The frequency selection network is used for blocking other frequency currents except the resonant frequency of the channel from passing through, and the frequency selection network in each channel unit realizes decoupling of fundamental waves and odd harmonics.
Embodiment one:
Fig. 1 is a schematic diagram of a multichannel system of the invention, wherein the input is direct-current voltage V in, a high-frequency square wave is obtained through an inverter circuit, n resonant frequencies are selected under the action of a2 n-order LC ladder network, the resonant frequencies are coupled to a secondary side through a non-contact transformer, and after decoupling through a secondary side compensation network corresponding to n channel units, the resonant frequencies are rectified and filtered to output. The primary side multi-frequency resonance network can also adopt the figure 2 or the figure 3 or other high-order networks with similar characteristics by taking the serial-parallel LC as a basic unit; x e is an input phase angle adjustment unit. The non-contact transformer adopts a rotary disk type, as shown in fig. 7 and 8, the primary coil and the secondary coil are opposite to each other vertically. For ease of analysis, the constant pressure type two channel system shown in fig. 3 will be described as an example.
In fig. 4, L A,LB,CA,CB forms a primary side dual-frequency resonant network, s ω is defined as complex frequency, s ω_m＝jω_m is satisfied, ω _m is m harmonic frequency, and the output current gain G iP of the dual-frequency resonant network can be obtained as follows:
Wherein, I P is the primary side double-frequency resonant network output current, V AB is the inverter circuit bridge arm midpoint output voltage, and Z o is the equivalent load of the primary side circuit.
As can be seen from the above, whenWhen G iP is independent of the load Z o. If the fundamental wave and the third harmonic resonance are realized, G iP is irrelevant to the load Z o, the following needs to be satisfied:
Wherein ω _1 is the fundamental frequency.
And defining the fundamental wave and third harmonic constant current gain values as G _1、G_3 respectively, and then:
And (3) obtaining the parameters of the dual-frequency resonance network by combining the steps (2) and (3):
therefore, through the design of the resonant element parameters, the current gain of the primary side double-frequency network at the fundamental wave and third harmonic frequency can be realized without being influenced by load change. The n-frequency resonant network parameter design can be analogized so as to realize that the current gain of resonance under n frequency points of fundamental wave and any odd harmonic is not influenced by load change.
For the input phase angle adjusting unit X e, the primary circuit equivalent load Z o is the total impedance of the primary coil self-inductance L P, the primary coil ac internal resistance R P, the secondary refraction impedance Z R, and the like, and the combination of the resistance and the reactance is written as Z o＝Ro+jXo. The input phase angles of the fundamental wave and the third harmonic wave of the double-frequency resonance network are respectively:
In the formula, m 1＝4096,m2＝192,m3＝1664.Xo_1,Ro_1 is the equivalent resistance and the equivalent reactance of Z o at the fundamental frequency; x o_3,Ro_3 is the equivalent resistance and equivalent reactance at the third harmonic frequency. Let the above formula be zero:
In order to adjust the input phase angle under different load conditions, an input phase angle adjusting unit needs to be added, as shown in fig. 4. The input phase angle adjustment unit X e may be composed of a single inductor, a single capacitor, or a combination of inductors and capacitors, and satisfies:
Wherein, X e_1 is the equivalent reactance of the input phase angle adjusting unit under the fundamental wave frequency, and X e_3 is the equivalent reactance of the input phase angle adjusting unit under the third harmonic frequency.
The input phase angle adjusting unit is added, so that under the condition of wide load range output, the whole input impedance of the system is pure in resistance, the realization of a soft switch of a switching tube of a primary side inverter circuit is facilitated, the waveform is improved, and the system efficiency is improved.
For the secondary resonant network shown in fig. 4, the circuit parameters of the 1-channel unit are denoted by subscript (1) and the circuit parameters of the 2-channel unit are denoted by subscript (2). The secondary side main winding L s(1) is cascaded with a resonance network and a fundamental wave frequency-selecting network, and then the output of the 1-channel unit is formed after rectification and filtering; the secondary side auxiliary winding L s(2), the resonance network and the third harmonic frequency selection network are cascaded, and then the channel output of the 2 units is formed after rectification and filtering. In the figure, C S(1)、Lr(1)、Cr(1) and C S(2)、Lr(2)、Cr(2) respectively form a compensation network of a1 channel unit and a 2 channel unit, wherein C S(1) and C S(2) are respectively resonance networks of the 1 channel unit and the 2 channel unit, and L r(1)、Cr(1) and L r(2)、Cr(2) respectively form a frequency selection network of the 1 channel unit and the 2 channel unit, so that the decoupling effect is achieved. The conditions for realizing decoupling operation of the fundamental wave and the third harmonic are as follows:
Because L r(1)、Cr(1) and L r(2)、CS(2) are parallel resonance, transmission of third harmonic wave in the 1-channel unit and fundamental wave in the 2-channel unit is respectively blocked, and energy decoupling transmission is realized in the secondary network. In addition, to meet the secondary constant voltage gain output should also meet:
Thus, the dual-channel constant-voltage output can be realized. And at this time, the ac voltage gain G vA is:
Wherein, V OS(1) is 1 channel rectifying and filtering circuit input voltage, V AB_1 is fundamental component of inverter circuit bridge arm midpoint output voltage, V OS(2) is 2 channel rectifying and filtering circuit input voltage, V AB_3 is third harmonic component of inverter circuit bridge arm midpoint output voltage, M PS(1) is transformer primary winding and secondary side main winding mutual inductance, I P_1 is primary side output current fundamental component, M PS(2) is primary side winding and secondary side auxiliary winding mutual inductance, I P_3 is primary side output current third harmonic component, G iP_1 is primary side double frequency resonant network output current gain under fundamental frequency, G iP_3 is primary side double frequency resonant network output current gain under third harmonic frequency.
In the constant voltage structure, the relationship between the input voltage V OS and the output voltage V o of the rectifying and filtering circuit is:
the dc voltage gain G vD is:
Embodiment two:
Fig. 5 shows a constant current type output dual channel system using a coupled inductor. The decoupling equivalent circuit of the primary side dual-frequency resonant network is shown in fig. 6, wherein in the figure, L A+M,LB +M is equivalent to C A in the formulas (1) - (4) after L A、LB,CA and-M are combined in series. Thus, the same characteristics as those of the primary side dual-frequency network in the first embodiment can be maintained, and meanwhile, the volume and the weight of passive devices are greatly reduced. The non-contact transformer adopts a rotary column type, as shown in fig. 9 and 10, the primary and secondary coils are radially opposite. The constant-current type double-channel system is different from the constant-voltage type double-channel system in that the resonance network in the secondary side compensation network is different, the constant-voltage type C S(1) and the constant-voltage type C S(2) are respectively connected in series in the respective channels, the constant-current type adopts parallel connection, in addition, in the figure, the inductor L d(1) and the inductor L d(2) play a role in regulating the input impedance of the transformer, and the constant-current type double-channel system can be added according to actual needs or not. At this time, the fundamental wave and harmonic decoupling and constant-current gain realization conditions of the constant-current type two-channel system are the same as those of the constant-voltage type. And the corresponding ac gain G iA is:
In the constant current structure, the relationship between the input current I OS and the output current I o of the rectifying circuit is:
The dc gain G iD is:
to verify the feasibility and theoretical analysis accuracy of the present invention, table 1 below shows the parameters of the actual measured air gap of 5mm between the primary and secondary sides of the dual-channel non-contact rotary transformer.
TABLE 1 Dual channel non-contact resolver parameters (@ 50 kHz)
The primary fundamental wave and third harmonic current gains are respectively: g _1＝-0.02,G_3 =0.02, the fundamental operating frequency f _1 =50 kHz. Substituting G _1、G_3 and f _1 into formula (4) can obtain: l A＝106.1μH,LB＝79.58μH,CA＝31.83nF,CB = 42.44nF. Taking L r1＝20μH,Lr2 = 50 μh, we can find from formulas (8) and (9): c S1＝36.78nF,Cr1＝56.29nF,CS2＝26.33nF,Cr2 = 202.64nF. The results are summarized in Table 2.
Table 2 two channel System Compensation network parameters (@ 50 kHz)
Fig. 17 shows a current gain curve of the primary side dual-frequency resonant network, and it can be seen from the graph that, at the fundamental wave frequency of 50kHz (the driving signal of the switching tube of the primary side inverter circuit is a 50% duty cycle square wave complementary to 50 kHz) and the third harmonic frequency of 150kHz, the current gain curves have intersection points, and the gain intersection point value is about 0.02, so as to satisfy the dual-frequency resonant characteristic.
The output curves of the constant voltage type two-channel system in the first example obtained by the sweep test of the load resistors of 30Ω, 40Ω and 55Ω are shown in fig. 18 and 19. The voltage gain intersection of the 1 channel is about 50kHz, and the voltage gain value is about 1.19; the 2-channel voltage gain intersection is about 49.5kHz and the voltage gain value is about 0.45. The 2-channel resonant frequency is about 49.5×3=148.5 kHz, and the third harmonic component in the square wave voltage output by the inverter circuit forms the actual input, so that the feasibility of the two-channel system is verified. In the example, as shown in fig. 20 and 21, the sweep frequency curve of the constant-current type output two-channel system has a 1-channel current gain intersection point of about 49.74kHz and a current gain value of about 0.015; the 2-channel current gain intersection is about 46kHz and the current gain value is about 0.005.
The sweep frequency curve shows that the built circuit has constant voltage and constant current characteristics, and is basically consistent with the theoretical analysis of the invention. It should be noted that the frequency and gain values at the 2-channel gain crossings are slightly offset, since the 2-channel gain crossings are particularly sensitive to parameter variations. In order to ensure that the 2 channels have good constant gain characteristics, the offset of the compensating network parameters should be as small as possible in practical application.
Embodiment III:
For the multi-channel system of the invention, the serial and parallel combination output can be carried out, and fig. 11 and 12 are respectively schematic diagrams of the constant-voltage type dual-channel output serial connection and constant-current type dual-channel output parallel connection structure of the invention. For a constant voltage output structure, the rectification circuit outputs can be combined in series; and the output of the rectifying circuit can be combined in parallel, and in addition, the series-parallel hybrid combination can be performed according to actual requirements. When the two channels of the secondary side are output in series, the following conditions are satisfied: v o＝Vo(1)+Vo(2), and distributing the power of each channel according to the voltage ratio; the two channels of the secondary side are output in parallel, and the following conditions are satisfied: i o＝Io(1)+Io(2), and each channel power P o is divided by the current ratio:
Constant pressure: Constant current: /(I)
Wherein R L is the system load.
Neglecting the loss of the rectifying circuit, the input and output power of the rectifying circuit are equal, so that the equivalent resistance R E of the rectifying and filtering circuit of each channel unit is respectively:
Constant pressure:
Constant current:
Wherein, I S(1) is the secondary side 1 channel input current, and I S(2) is the secondary side 2 channel input current.
To verify the feasibility of the invention, the maximum output power of the two-channel system is evaluated. The maximum output power is solved through the Thevenin equivalent circuit, and the maximum power transmission theorem shows that the load can obtain the maximum power when the load impedance modulus value is equal to the Thevenin equivalent internal impedance modulus value.
In contrast, a single channel system was first analyzed, and it was considered that the single channel system only delivered fundamental power. When the fundamental wave is utilized for power transmission, assuming that the fundamental wave voltage gain is G vA_1, the open circuit voltage V oc_1＝VAB_1·GvA_1 of the single channel system is set, and the maximum transmission power is P omax_1＝(VAB_1·GvA_1)2/4|Zi_1 I when the equivalent internal impedance of the Thevenin is Z i_1. When the third harmonic is used for power transmission, the switching frequency is reduced to 1/3 of the original fundamental frequency, and the resonance frequency is not changed, so that the voltage gain and the equivalent internal impedance are not changed, and the maximum transmission power which can be obtained when the third harmonic is used for power transmission is P omax_3＝(VAB_3·GvA_1)2/4|Zi_1. Since V AB_3 is 1/3 of V AB_1, the ratio of the third harmonic maximum transmission power to the fundamental maximum transmission power is 1/9.
Since the primary circuit of the dual-channel system has constant current output characteristic at the resonance frequency point, the primary circuit is subjected to current source equivalent as shown in fig. 13. In the figure, R ' P represents the sum of equivalent alternating current resistances of the primary coil and the resonance compensation network, R ' S′(1) represents the sum of equivalent alternating current resistances of the coil of the 1-channel unit and the resonance compensation network, and R ' S(2) represents the sum of equivalent alternating current resistances of the coil of the 2-channel unit and the resonance compensation network. The output open circuit voltage V oc of each channel of the secondary side is respectively as follows:
Voc(1)＝jω_1MPS(1)VAB_1GiP_1,Voc(2)＝jω_3MPS(2)VAB_3GiP_3 (19)
When solving the equivalent internal impedance of each channel, the constant current sources i P_1 and i P_3 are regarded as open circuits, so that the primary side loop impedance is approximately zero when being refracted to the secondary side, and the internal impedance of the 1 channel unit and the internal impedance of the 2 channel unit are respectively equal to the secondary side impedance, namely:
When working at the resonance frequency point, the upper imaginary part is zero, so the equivalent internal impedance of the 1, 2 channel units is approximately equal to the equivalent alternating current resistance of the secondary side. When the equivalent load resistance R E(1)、RE(2) of the rectifying circuit is respectively equal to the equivalent internal resistance of the Thevenin, the two channels can respectively output the maximum power:
the ratio of the third harmonic maximum transmission power to the fundamental wave is:
From the above, the two-channel system can distribute the power of the fundamental wave and the harmonic wave by adjusting the mutual inductance of the primary and secondary coils, the primary current gain, and the equivalent alternating current resistance of the coils and the compensation network. Compared with a single-channel system, the double-channel system not only can realize weak-inductive and constant-gain output of an input phase angle, but also greatly increases the power transmission capacity under the condition of not considering the current stress of the primary coil, and can flexibly distribute the duty ratio of fundamental wave and harmonic power by adjusting the primary current gain, transformer mutual inductance, coil and compensation network equivalent internal resistance and other modes, thereby realizing optimal power transmission.
Embodiment four:
The multi-channel system of the invention can also add closed-loop control strategy rate to further optimize the system. In fig. 14, the output voltage and current of multiple channels are sampled, the primary side inverter circuit is controlled in a closed loop manner, the output proportion relation among the secondary side channels can be regulated through strategies such as phase shifting and frequency conversion control, and meanwhile, the output is stable when the wide load changes. In addition, the outputs of the channels shown in fig. 14 may be combined in series, parallel or a hybrid combination of series and parallel to obtain a composite voltage source or current source module. Fig. 15 is a schematic diagram of a system in which multiple channels are output in parallel, and a closed-loop control relay is added to the input end of the secondary side of each channel, so that each channel of the secondary side can be switched according to the output power or the current, and the optimal power transmission is realized. Fig. 16 is a multi-channel series output with each harmonic channel rectifier circuit replaced by a controllable rectifier and closed loop controlled. If the fundamental wave channel is used as main power output, the whole output voltage of the system can be regulated by controlling the controllable rectifying network of each harmonic wave channel, so that the output voltage is maintained stable or the regulation of a wide output voltage range is realized. Compared with direct regulation of the output of the main power loop of the fundamental wave channel, the harmonic channel has smaller power, and the control and indirect regulation of the harmonic channel are more beneficial to the improvement of the overall efficiency of the system.
The foregoing is merely a preferred embodiment of the present invention and it should be noted that modifications and adaptations to those skilled in the art may be made without departing from the principles of the present invention, which are intended to be comprehended within the scope of the present invention.
Claims (6)
1. A multichannel non-contact power supply system with fundamental wave-harmonic wave parallel energy transmission is characterized in that: the transformer comprises a primary side circuit, a non-contact transformer and a secondary side circuit; the primary side circuit comprises a cascade inverter circuit and a primary side compensation network, and the primary side compensation network is a multi-frequency resonant circuit; the secondary side of the non-contact transformer is wound with a main winding and one or more auxiliary windings, and the main winding and the auxiliary windings share a magnetic core; the secondary side circuit comprises a plurality of channel units, each channel unit comprises a cascade secondary side compensation network and a rectifying and filtering circuit, the secondary side compensation network is formed by connecting a resonance network and a frequency selection network, and the main winding and the auxiliary winding are respectively connected with one channel unit; the frequency selection network is used for blocking other frequency currents except the resonant frequency of the channel from passing through, and the frequency selection network in each channel unit realizes decoupling of fundamental waves and odd harmonics;
The multi-frequency resonance circuit is an LC ladder network taking series inductance and parallel capacitance as basic units; in the LC ladder network, when the number of LC units is n, the resonance of n frequency points in fundamental wave and each odd harmonic frequency is realized, and the primary side output current gains are independent of the equivalent load of a primary side circuit through the design of LC network parameters;
if the multi-frequency resonant circuit is a four-order LC ladder type resonant network and the simultaneous resonance of a fundamental wave and a third harmonic is realized, the network parameters meet the following conditions:
Wherein, L A、CA、LB、CB is two inductances and two capacitances in the four-order LC ladder type resonant network respectively, omega _1 is fundamental wave frequency, and G _1、G_3 is fundamental wave and third harmonic constant current gain value respectively.
2. The fundamental wave-harmonic wave parallel energy transmission multichannel noncontact power supply system according to claim 1, characterized in that: the inductance elements in the multi-frequency resonance circuit adopt coupling inductances which are mutually coupled.
3. The fundamental wave-harmonic wave parallel energy transmission multichannel noncontact power supply system according to claim 1 or 2, characterized in that: the primary side circuit also comprises an input phase angle adjusting unit.
4. The fundamental wave-harmonic wave parallel energy transmission multichannel noncontact power supply system according to claim 1 or 2, characterized in that: the resonance network of the secondary circuit is a capacitor or an LC mixed network which is respectively connected with the main winding and the auxiliary winding in series or in parallel, and the frequency-selecting network is an LC mixed network.
5. The fundamental wave-harmonic wave parallel energy transmission multichannel noncontact power supply system according to claim 4, characterized in that: when the resonance networks of the secondary side circuits are all connected in series in each channel unit network to realize constant-voltage output of each channel unit, the multi-channel units are output in series combination; when the resonance network of the secondary side circuit is connected in parallel in each channel unit network, and constant current output of each channel unit is realized, the multichannel units are output in parallel.
6. The fundamental wave-harmonic wave parallel energy transmission multichannel noncontact power supply system according to claim 5, characterized in that: the switching tube of the inverter circuit of the primary side circuit is closed-loop controlled or the rectifying and filtering circuit of the secondary side circuit adopts a controllable rectifying circuit, and the controllable rectifying circuit is closed-loop controlled, so that the output voltage or power of the system is regulated and controlled.
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