CN110311562A - A kind of DC-DC converter - Google Patents
A kind of DC-DC converter Download PDFInfo
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- CN110311562A CN110311562A CN201910683692.7A CN201910683692A CN110311562A CN 110311562 A CN110311562 A CN 110311562A CN 201910683692 A CN201910683692 A CN 201910683692A CN 110311562 A CN110311562 A CN 110311562A
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- switch module
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The invention discloses a kind of DC-DC converters, comprising: current output circuit, reverse-filling switch module, inductance, load capacitance and ON-OFF control circuit；First end of the output end of current output circuit one by one through reverse-filling switch module, inductance connect the first end of load with the first end of load capacitance；The second end through load capacitance and the second end of load are grounded the second end of reverse-filling switch module one by one；Current output circuit, the voltage applied on benchmark voltage and load provide load current to load；ON-OFF control circuit, for detecting the voltage of reverse-filling switch module first end；When the voltage of reverse-filling switch module first end is greater than or equal to zero, control reverse-filling switch module shutdown has ended the reverse irrigated current on flow direction ground, has avoided the generation of electric current reverse irrigation, reduce the loss of power.
Description
Technical field
This application involves power electronics field more particularly to a kind of DC-DC converters.
Background technique
DC-DC (DC-DC) converter is the important component of Power Management Unit, due to its power switch plumber
Make in switch state, so being also referred to as Switching Power Supply.The basic principle of DC-DC converter is by regulation power switching tube
The time ratio (i.e. duty ratio) of turn-on and turn-off controls dynamic transmitting of the power from input power to output loading, thus
To stable output voltage.DC-DC converter has that high conversion efficiency, wide input voltage range, voltage stabilized range be wide, power density
Than it is big the advantages that, therefore be applied widely, being related to field includes data communication, computer, automation equipment, instrument instrument
The industries such as table, military affairs.
However, existing DC-DC converter has electric current reverse irrigation during inductive discharge, biggish function is generated
Rate loss, influences transfer efficiency.
Summary of the invention
In view of this, the embodiment of the present application provides a kind of stream-DC converter, it is able to solve electric current in the prior art and falls
The problem of filling.
A kind of DC-DC converter provided by the embodiments of the present application, comprising: current output circuit, reverse-filling switching molding
Block, inductance, load capacitance and ON-OFF control circuit；
First end, the inductance and institute of the output end of the current output circuit one by one through the reverse-filling switch module
State the first end of the first end connection load of load capacitance；The second end of the reverse-filling switch module is one by one through the load electricity
The second end of appearance and the second end of load ground connection；
The current output circuit, the voltage applied on benchmark voltage and the load are mentioned to the load
For load current；
The ON-OFF control circuit, for detecting the voltage of the reverse-filling switch module first end；When the reverse-filling
When the voltage of switch module first end is greater than or equal to zero, the reverse-filling switch module shutdown is controlled.
Optionally, the ON-OFF control circuit, comprising: comparison module and control module；
The first input end of the comparison module connects the first end of the reverse-filling switch module, the comparison module
The output end of second input end grounding, the comparison module connects the control module；The output end of the control module connects
The control terminal of the reverse-filling switch module；
Whether the comparison module, the voltage for the reverse-filling switch module first end are greater than zero；When described
When the voltage of reverse-filling switch module first end is greater than zero, the first comparison signal of output to the control module；
The control module, for when receiving first comparison signal, output first control signal to be prevented to described
Flow backward the control terminal of switch module, to control the reverse-filling switch module shutdown.
Optionally, the comparison module, comprising: current mirror, the first NMOS tube, the second NMOS tube and third NMOS tube；
The current mirror provides equal electric current for the drain electrode of first NMOS tube and the drain electrode of second NMOS tube；
The grid of first NMOS tube connects drain electrode and the grid of second NMOS tube of first NMOS tube, institute
State the source electrode ground connection of the first NMOS tube；
The source electrode of second NMOS tube connects the first end of the reverse-filling switch module；
The grid of the third NMOS tube connects the drain electrode of second NMOS tube, and the source electrode of the third NMOS tube connects
Ground, the drain electrode connection power supply of the third NMOS tube and the control module.
Optionally, the comparison module, further includes: logic amplifies submodule；
Two input terminals of logic amplification submodule are separately connected the drain electrode of the third NMOS tube and described anti-down
Fill the control terminal of switch module；
The logic amplifies submodule, for exporting the voltage amplification of the drain electrode output of the third NMOS tube.
Optionally, the logic amplifies submodule, comprising: the first phase inverter and with door；
The drain electrode of the third NMOS tube is through first phase inverter connection first input end with door；
The control terminal that the reverse-filling switch module is connect with the second input terminal of door.
Optionally, the ON-OFF control circuit, further includes: enabled module；
The enabled module enables the comparison module for the on off operating mode based on the reverse-filling switch module.
Optionally, the enabled module, comprising: first switch tube and/or second switch；
The first end of the first switch tube connects the source electrode of second NMOS tube, the second end of the first switch tube
Ground connection, the control terminal of the first switch tube connect the control terminal of the reverse-filling switch module；
The first end of the second switch connects the grid of the third NMOS tube, the second end of the second switch
Ground connection, the control terminal of the second switch connect the control terminal of the reverse-filling switch module.
Optionally, the enabled module, further includes: third switching tube；
The first end and second end of the third switching tube is separately connected first end and the institute of the reverse-filling switch module
The source electrode of the second NMOS tube is stated, the control terminal of the third switching tube connects the control terminal of the reverse-filling switch module.
Optionally, the comparison module, further includes: resistance；
The resistance is connected between the first end of the reverse-filling switch module and the source electrode of second NMOS tube.
Optionally, the current mirror be common-source common-gate current mirror structure, comprising: electric current input branch, the first mirror image branch,
Second mirror image branch and third mirror image branch；
The input terminal of the electric current input branch connects input current, by the input current mirror image to first mirror image
Branch, second mirror image branch and the third mirror image branch；
First mirror image branch, second mirror image branch and the third mirror image branch are separately connected described first
The drain electrode of NMOS tube, the drain electrode of second NMOS tube and the third NMOS tube drain electrode.
Compared with prior art, the application has at least the following advantages:
In the embodiment of the present application, prevent electric current when inductive discharge from falling using reverse-filling switch module and ON-OFF control circuit
Cause power loss with being poured into, during inductive discharge, inductance provides load to load output forward current first for load
Electric current, inductive current linear decline, the voltage of reverse-filling switch module first end is less than zero.Inductive current continues to decline, anti-down
The voltage for filling switch module first end declines therewith, when electric current continuous decrease switchs to reverse current on inductance, if reverse-filling is opened
It closes module to be still connected, then will appear the case where electric current flows backward through reverse-filling switch module to ground, at this time reverse-filling switch module
The voltage of first end is greater than zero, and ON-OFF control circuit controls the shutdown of reverse-filling switch module, has ended the reverse irrigated current on flow direction ground,
The generation for avoiding electric current reverse irrigation, reduces the loss of power.
Detailed description of the invention
In order to illustrate the technical solutions in the embodiments of the present application or in the prior art more clearly, to embodiment or will show below
There is attached drawing needed in technical description to be briefly described, it should be apparent that, the accompanying drawings in the following description is only this
The some embodiments recorded in application, for those of ordinary skill in the art, without creative efforts,
It can also be obtained according to these attached drawings other attached drawings.
Fig. 1 is a kind of structural schematic diagram of existing buck DC-DC converter；
Fig. 2 is a kind of structural schematic diagram of DC-DC converter provided by the embodiments of the present application；
Fig. 3 is the structural schematic diagram of current output circuit in a kind of DC-DC converter provided by the embodiments of the present application；
Fig. 4 is the structural schematic diagram of another DC-DC converter provided by the embodiments of the present application；
Fig. 5 is the structural schematic diagram of another DC-DC converter provided by the embodiments of the present application；
Fig. 6 is the structural schematic diagram of another DC-DC converter provided by the embodiments of the present application；
Fig. 7 is the structural schematic diagram of another DC-DC converter provided by the embodiments of the present application；
Fig. 8 is the structural schematic diagram of another DC-DC converter provided by the embodiments of the present application；
Fig. 9 is the structural schematic diagram of another DC-DC converter provided by the embodiments of the present application；
The specific electricity of ON-OFF control circuit in a kind of DC-DC converter that Figure 10 provides for the application specific embodiment
Road topology；
Figure 11 is the structural schematic diagram of another DC-DC converter provided by the embodiments of the present application；
Figure 12 is the structural schematic diagram of another DC-DC converter provided by the embodiments of the present application；
Figure 13 is a kind of structural schematic diagram for charging control circuit that the application specific embodiment provides；
Figure 14 is showing for the first clock signal in the application specific embodiment, second clock signal and corresponding control signal
It is intended to；
Figure 15 is a kind of structural schematic diagram for control signal output module that the application specific embodiment provides；
Figure 16 is the structural schematic diagram of another DC-DC converter provided by the embodiments of the present application；
Figure 17 is a kind of structural schematic diagram for benchmark output circuit that the application specific embodiment provides；
Figure 18 is a kind of structural schematic diagram for DC-DC converter that the application specific embodiment provides.
Specific embodiment
In order to make those skilled in the art more fully understand application scheme, below in conjunction in the embodiment of the present application
Attached drawing, the technical scheme in the embodiment of the application is clearly and completely described, it is clear that described embodiment is only this
Apply for a part of the embodiment, instead of all the embodiments.Based on the embodiment in the application, those of ordinary skill in the art exist
Every other embodiment obtained under the premise of creative work is not made, shall fall in the protection scope of this application.
It should be appreciated that in this application, " at least one (item) " refers to one or more, and " multiple " refer to two or two
More than a."and/or" indicates may exist three kinds of relationships, for example, " A and/or B " for describing the incidence relation of affiliated partner
It can indicate: only exist A, only exist B and exist simultaneously tri- kinds of situations of A and B, wherein A, B can be odd number or plural number.Word
Symbol "/" typicallys represent the relationship that forward-backward correlation object is a kind of "or"." at least one of following (a) " or its similar expression, refers to
Any combination in these, any combination including individual event (a) or complex item (a).At least one of for example, in a, b or c
(a) can indicate: a, b, c, " a and b ", " a and c ", " b and c ", or " a and b and c ", and wherein a, b, c can be individually, can also
To be multiple.
A kind of illustrated existing buck DC-DC converter structure of Fig. 1.The positive output end of supply voltage Vin by
It is connected to the positive input terminal of load R once power switch tube M, the cathode of sustained diode and inductance L, supply voltage Vin's is negative
Output end is connected to the negative input end of load R through the anode of sustained diode, and load capacitance C is in parallel with supply voltage Vin.
Its working principle is that: benchmark voltage controls the actual output voltage of DC-DC converter, is controlled using signal Vs
Power switch tube M turn-on and turn-off, so that output voltage maintains near reference voltage.When signal Vs leads power switch tube M
When logical, sustained diode is provided load current by input supply voltage Vin, simultaneously due to being not turned in reverse-biased
Electric current on inductance L starts linearly increasing, load capacitance C and starts energy storage；When signal Vs turns off power switch tube M, inductance L
Sustained diode is connected in the induced voltage at both ends, and the energy stored on inductance L at this time is provided negative by sustained diode
Electric current is carried, load capacitance C discharges, and the electric current on inductance L starts linearly to reduce.Signal Vs periodically controls converter and repeats
The process stated eventually makes output voltage Vout tend to reference voltage.
In inductance L discharge process, inductance L electric current linear decline, because sustained diode needs certain time can
Completely switched off, when the electric current of inductance L is down to reverse current from forward current, inductance L electric current can be flowed to by sustained diode
Ground occurs electric current and flows backward, and generates biggish power loss, influences the transfer efficiency of converter.
For this purpose, the embodiment of the present application provides a kind of DC-DC converter, freewheeling diode in the prior art is replaced
It is changed to reverse-filling switch module, utilizes the shutdown of ON-OFF control circuit control reverse-filling switch module.During inductive discharge,
When inductance to load discharge export forward current when, reverse-filling switch module is in the conductive state, first end voltage less than zero,
Inductance is normally to load discharge；Inductive current continues to decline, when inductive current is decreased to less than 0 output reverse current, reverse-filling
Switch module first end voltage is greater than zero, and ON-OFF control circuit controls the shutdown of reverse-filling switch module, and truncation inductance exports anti-
To electric current, the case where inductive current flows backward through reverse-filling switch module to ground is avoided, reduces the loss of power, ensure that change
The transfer efficiency of parallel operation.
Based on above-mentioned thought, in order to make the above objects, features, and advantages of the present application more apparent, below with reference to
Attached drawing is described in detail the specific embodiment of the application.
Referring to fig. 2, which is a kind of structural schematic diagram of DC-DC converter provided by the embodiments of the present application.
DC-DC converter provided by the embodiments of the present application, comprising: current output circuit 110, reverse-filling switch module
120, inductance L, load capacitance C and ON-OFF control circuit 130；
First end, inductance L and load electricity of the output end of current output circuit 110 one by one through reverse-filling switch module 120
Hold the first end of the first end connection load R of C；Second end of the second end of reverse-filling switch module 120 one by one through load capacitance C
With the second end ground connection of load R；
Current output circuit 110, the voltage applied on benchmark voltage Vrefs and load R, provides to load R
Load current；
ON-OFF control circuit 130, for detecting the voltage of 120 first end of reverse-filling switch module；When reverse-filling switching molding
When the voltage of 120 first end of block is greater than zero, control reverse-filling switch module 120 is turned off.
It is understood that in the embodiment of the present application, current output circuit 110 utilizes negative feedback mechanism, it is based on benchmark
Voltage Vrefs and voltage, output load current is to R is loaded, so that the voltage applied on load R tends to and stablizes in reference voltage
Near.
As an example, as shown in figure 3, current output circuit, can specifically include: power switch tube Mp, power supply electricity
Source Vin, the first feedback resistance Rf1, the second feedback resistance Rf2 and error amplifier.The output end of supply voltage Vin is opened through power
After the first end of pass pipe Mp connection reverse-filling switch module 120, the first feedback resistance Rf1 and the second feedback resistance Rf2 series connection simultaneously
The both ends of load R are associated in, the positive terminal of error amplifier OP connects reference voltage Vrefs, and the reverse side of error amplifier OP connects
It connects between the first feedback resistance Rf1 and the second feedback resistance Rf2, the output end of error amplifier OP is connected for controlling power
The logic control signal of switching tube Mp on-off.
After current output circuit 110 starts, to load R output load current, loads voltage Vout on R and be gradually increased, electricity
Pressure Vout obtains feedback voltage Vfb after the first feedback resistance Rf1 and the second feedback resistance Rf2 partial pressure and acts on error amplifier
The reverse side of OP is compared with the reference voltage Vrefs of positive terminal, and error amplifier OP exports comparison result by amplification
After generate error signal, error signal by adjusting logic control signal duty ratio, when adjusting the on-off of power switch tube Mp
Between, output or truncation load current are allowed to be intended to the mesh of the stable output of reference voltage Vrefs to reach adjusting voltage Vout
's.It is illustrated below in conjunction with a specific example, does not repeat first here.
When current output circuit 110 stops output load current, inductance L starts electric discharge and continues as load R offer load
Electric current, for the voltage of 120 first end of reverse-filling switch module less than zero, reverse-filling switch module 120 is in the conductive state at this time；Electricity
Feel L continuous discharge, when inductance L electric current becomes reverse current, electric current can flow to ground through reverse-filling switch module 120, and electric current falls
Filling causes power loss, at this point, the voltage of 120 first end of reverse-filling switch module is greater than zero, the control of ON-OFF control circuit 130 is anti-
Flow backward switch module 120 to turn off, end the electric current of inductance L, the generation for avoiding electric current from flowing backward reduces power loss, guarantees transformation
The transfer efficiency of device.
In practical applications, reverse-filling switch module 120 specifically can use one or more switching tubes and realize, as one
A example, as shown in figure 3, reverse-filling switch module can be NMOS tube Mn.Below in conjunction with a specific example to switch
Control circuit 130 is described in detail, and does not repeat first.
In the embodiment of the present application, prevent electric current when inductive discharge from falling using reverse-filling switch module and ON-OFF control circuit
Cause power loss with being poured into, during inductive discharge, inductance provides load to load output forward current first for load
Electric current, inductive current linear decline, reverse-filling switch module is in the conductive state, and the voltage of first end is less than zero.Inductance electricity
Stream continues to decline, and the voltage of reverse-filling switch module first end declines therewith, when electric current continuous decrease switchs to reversed electricity on inductance
When stream, if reverse-filling switch module is still connected, it will appear the case where electric current flows backward through reverse-filling switch module to ground, at this time
The voltage of reverse-filling switch module first end is greater than zero, and ON-OFF control circuit controls the shutdown of reverse-filling switch module, has ended stream
To the reverse irrigated current on ground, the generation of electric current reverse irrigation is avoided, the loss of power is reduced.
Referring to fig. 4, which is the structural schematic diagram of another DC-DC converter provided by the embodiments of the present application.Phase
Compared with Fig. 2, this figure provides a kind of more specifical DC-DC converter structures.
In some possible implementations of the embodiment of the present application, ON-OFF control circuit be can specifically include: comparison module
131 and control module 132；
The first end of the first input end connection reverse-filling switch module 120 of comparison module 131, the of comparison module 131
Two input end groundings, the output end link control module 132 of comparison module 131；The output end of control module 132 connects reverse-filling
The control terminal of switch module 120；
Whether comparison module 131, the voltage for comparing 120 first end of reverse-filling switch module are greater than zero；Work as reverse-filling
When the voltage of 120 first end of switch module is greater than zero, the first comparison signal Vzcs1 of output to control module 132；
Control module 132, for when receiving the first comparison signal Vzcs1, output first control signal Vn1 is to anti-down
The control terminal of switch module 120 is filled, to control the shutdown of reverse-filling switch module 120.
In the embodiment of the present application, when the voltage of 120 first end of reverse-filling switch module is less than zero, comparison module 131
The second comparison signal Vzcs2 different from the first comparison signal Vzcs1 can also be exported to control module 132, to avoid control
Logical mistake.Comparison module 131 is by comparing between the voltage and ground (i.e. zero potential) of 120 first end of reverse-filling switch module
Size relation, exports the first comparison signal Vzcs1 or the second comparison signal Vzcs2 to control module 132 according to the result of the comparison,
Control module 132 is allowed to export first control signal Vn1 control reverse-filling switch module according to the first comparison signal Vzcs1
120 shutdowns.It is understood that control module 132 can also be when receiving the second comparison signal Vzcs2, according to setting
Control model exports second control signal Vn2 control reverse-filling switch module 120 and is connected, so that converter works normally.
As an example, when reverse-filling switch module 120 is NMOS tube, first control signal Vn1 is low level letter
Number, second control signal Vn2 is high level signal.First comparison signal Vzcs1, the second comparison signal Vzcs2, the first control letter
Number Vn1 and second control signal Vn2 can specifically be set according to the actual situation, here without limiting.
In practical applications, comparison module 131 can use the realization of any one comparator configuration, as an example,
Comparison module 131 can be error amplifier.Below in conjunction with a specific example to the specific structure of comparison module 131 into
Row explanation.
In some possible implementations of the embodiment of the present application, as shown in figure 5, comparison module, can specifically include: electricity
Flow mirror 131a, the first NMOS tube M1, the second NMOS tube M2 and third NMOS tube M3；
Current mirror 131a provides equal electric current for the drain electrode of the first NMOS tube M1 and the drain electrode of the second NMOS tube M2
Iref2；
The grid of first NMOS tube M1 connects drain electrode and the grid of the second NMOS tube M2 of the first NMOS tube M1, the first NMOS
The source electrode of pipe M1 is grounded；
The first end of the source electrode connection reverse-filling switch module 120 of second NMOS tube M2；
The grid of third NMOS tube M3 connects the drain electrode of the second NMOS tube M2, the source electrode ground connection of third NMOS tube M3, third
The drain electrode connection power supply Vdd and control module 132 of NMOS tube M3.
In the embodiment of the present application, when current output module 110 stops being negative to when loading output load current by inductance
Output forward current is carried, reverse-filling switch module 120 is in the conductive state, and first end (hereinafter referred to as node SW) voltage is small
In zero, second NMOS tube M2 source voltage less than zero.Because the grid of the first NMOS tube M1 and the second NMOS tube M2 are connected, two
Person's grid voltage is equal, and the voltage difference between the grid and source electrode of the second NMOS tube M2 is equal to the grid voltage of the first NMOS tube M1
The voltage of node SW is subtracted, and the source electrode of the first NMOS tube M1 is grounded, the voltage between the grid and source electrode of the first NMOS tube M1
Grid voltage of the difference i.e. equal to the first NMOS tube M1, the voltage of node SW is less than zero, so the grid of the first NMOS tube M1 and source
The voltage difference between grid and source electrode of the voltage difference less than the second NMOS tube M2 between pole, the first NMOS tube M1 drain electrode and source electrode
Between electric current less than the electric current that the second NMOS tube M2 drains between source electrode.Then, because current mirror 131a is exported to first
NMOS tube M1 drain electrode it is equal with the electric current that the second NMOS tube M2 drain be Iref2, and the second NMOS tube M2 drain with source electrode it
Between electric current be greater than Iref2, the second NMOS tube M2 is in the conductive state, and the drain voltage of the second NMOS tube M2 is equal to node SW
Voltage, then the grid voltage of third NMOS tube M3 is less than zero, third NMOS tube M3 shutdown, and power supply Vdd is by the 3rd NMOS
The drain voltage of pipe M3 is pulled to high level, exports low level second comparison signal Vzcs2 to control module 132, so that control
Molding block 132 exports the control terminal of second control signal Vn2 to reverse-filling switch module 120, controls reverse-filling switch module 120
Conducting, guarantees the normal work of comparison module.
Then, inductance continuous discharge, electric current is reversed after inductive current is decreased to zero, and the reverse current of inductance flows to reverse-filling
The first end of switch module 120, so that first end (the i.e. node SW) voltage of reverse-filling switch module 120 is greater than zero, second
The source voltage of NMOS tube M2 is greater than zero, because the second NMOS tube M2 is in the conductive state, the drain voltage etc. of the second NMOS tube M2
In the voltage of node SW, then the grid voltage of third NMOS tube M3 is greater than zero, third NMOS tube M3 conducting, by third NMOS tube M3
Drain voltage be pulled down to zero, to control module 132 export high level the first comparison signal Vzcs1 so that control module 132
The control terminal of first control signal Vn1 to reverse-filling switch module 120 is exported, control reverse-filling switch module 120 turns off, cut-off
The reverse current of inductance avoids electric current from flowing backward through reverse-filling switch module 120 to ground, reduces power loss.
In some possible designs, comparison module, as shown in fig. 6, can also include: resistance R0；
Resistance R0 is connected between the first end of reverse-filling switch module 120 and the source electrode of the second NMOS tube M2, to reduce
Influence of the offset voltage to comparison module, allows first control signal Vn1 accurately to turn off reverse-filling switch module 120.
Furthermore it is also possible to pass through the operating lag for reducing comparison module to the fine tuning of resistance R0 resistance value.
It is understood that current mirror is a basic unit in analog circuit, it can be used for replica current, it can also be with
It generally may include cascade type (cascode) current mirror and Wilson's (Wilson) electric current as being loaded to differential pair
Mirror.In the embodiment of the present application, current mirror 131a can use the realization of any one current-mirror structure.As an example, electric
Flowing mirror 131a can be common-source common-gate current mirror structure, to improve the precision of current mirror.Because being the using current mirror 131a
One NMOS tube M1 drain electrode and the second NMOS tube M2 drain electrode provide electric current, it is ensured that the grid voltage of the first NMOS tube M1 and
The grid voltage of second NMOS tube M2 does not change with the variation of supply voltage, ensure that control precision.
In some possible designs, the gate charges that can also be third NMOS tube M3 using current mirror 131a, to draw
The grid voltage of high third NMOS tube M3, power supply Vdd provide operating voltage for current mirror 131a.Then, current mirror 131a has
Body may include: electric current input branch, the first mirror image branch, the second mirror image branch and third mirror image branch；
The input terminal that electric current inputs branch connects input current Iref2, by input current Iref2 mirror image to the first mirror image branch
Road, the second mirror image branch and third mirror image branch；
First mirror image branch, the second mirror image branch and third mirror image branch are separately connected the drain electrode of the first NMOS tube M1,
The drain electrode of two NMOS tube M2 and the drain electrode of third NMOS tube M3.The physical circuit topology of current mirror 131a can with as shown in fig. 6, this
In repeat no more.
In some possible implementations of the embodiment of the present application, as shown in fig. 7, comparison module, can also include: logic
Amplify submodule 131b；
Two input terminals of logic amplification submodule 131b are separately connected drain electrode and the reverse-filling switch of third NMOS tube M3
The control terminal of module 120；Logic amplifies submodule 131b, for the voltage amplification of the drain electrode output of third NMOS tube M3 is defeated
Out.
In the embodiment of the present application, logic amplification submodule 131b can play the role of signal amplification, improve control
Precision.
In some possible designs, logic amplify submodule 131b, can specifically include: the first phase inverter and with door；
First input end of the drain electrode of third NMOS tube through the first phase inverter connection and door；Reverse-filling is connect with the second input terminal of door to open
Close the control terminal of module.
In the embodiment of the present application, ON-OFF control circuit is realized using current-mirror structure to reverse-filling switch module first end
Voltage whether be greater than zero detection, can guarantee the control precision to reverse-filling switch module.
Referring to Fig. 8, which is the structural schematic diagram of another DC-DC converter provided by the embodiments of the present application.Phase
Compared with Fig. 5, this figure provides a kind of more specifical DC-DC converters.
In some possible implementations of the embodiment of the present application, it can also be controlled after control reverse-filling switch module shutdown
Comparison module processed stops working, to reduce power consumption.Specifically, ON-OFF control circuit can also include: enabled module 133；
Enabled module 133 enables comparison module 131 for the on off operating mode based on reverse-filling switch module 120.
In the embodiment of the present application, it when reverse-filling switch module 120 turns off, realizes to the reverse irrigated current on flow direction ground
Truncation stops working at this point, enabled module 133 controls comparison module 131, can reduce system power dissipation；And when reverse-filling switchs
When module 120 is connected, in order to avoid electric current reverse irrigation, enables module 133 and control the start-up operation of comparison module 131.
As an example, as shown in figure 9, enabled module can specifically include: first switch tube K1 and/or second switch
Pipe K2；
The first end of first switch tube K1 connects the source electrode of the second NMOS tube M2, and the second end of first switch tube K1 is grounded,
The control terminal of the control terminal connection reverse-filling switch module 120 of first switch tube K1；
The grid of the first end connection third NMOS tube M3 of second switch K2, the second end ground connection of second switch K2,
The control terminal of the control terminal connection reverse-filling switch module 120 of second switch K2.
In the embodiment of the present application, when reverse-filling switch module 120 turns off, control terminal inputs first control signal
Vn1, first switch tube K1 and second switch K2 are connected under the control of first control signal Vn1, respectively by the second NMOS tube
The source voltage of M2 and the grid voltage of third NMOS tube M3 are pulled down to ground, and comparison module stops working；When reverse-filling switching molding
When block 120 is connected, control terminal inputs second control signal Vn2, first switch tube K1 and second switch K2 in the second control
Turned off under the control of signal Vn2, the grid voltage of the source voltage connecting node SW of the second NMOS tube M2, third NMOS tube M3 by
The drain voltage of second NMOS tube M2 controls, and comparison module works normally.
What needs to be explained here is that when reverse-filling switch module 120 turns off, first switch tube K1 and second switch K2
Conducting, the place node SW no longer input voltage is to comparison module, and since second switch K2 is electric by the grid of third NMOS tube M3
Pressure is pulled to ground, and third NMOS tube M3 stops working, and comparison module does not export, and reverse-filling switch module 120 will not be misled
Logical situation avoids the hair that circuit interference causes comparison module output low level to make reverse-filling switch module conducting situation
It is raw.
In some possible designs, with continued reference to Fig. 9, module is enabled, can also include: third switching tube K3；
The first end and second end of third switching tube K3 is separately connected the first end and second of reverse-filling switch module 120
The source electrode of NMOS tube M2, the control terminal of the control terminal connection reverse-filling switch module 120 of third switching tube K3.
It is understood that control terminal inputs first control signal Vn1 when reverse-filling switch module 120 turns off, the
Three switching tube K3 are turned off under the control of first control signal Vn1, disconnect the first end and second of reverse-filling switch module 120
Connection between the source electrode of NMOS tube M2 avoids the waste of energy so that comparison module stops working；When reverse-filling switching molding
When block 120 is connected, control terminal inputs second control signal Vn2, and third switching tube K3 is under the control of second control signal Vn2
Conducting, so that the voltage of the second NMOS tube M2 source electrode is equal to the voltage of 120 first end of reverse-filling switch module, comparison module is normal
Work.
In practical applications, first switch tube K1, second switch K2 and third switching tube K3 can use NMOS tube
It realizes, here without limiting.
ON-OFF control circuit in a kind of DC-DC converter that the illustrated the application specific embodiment of Figure 10 provides
Physical circuit topology.Its working principle is referred to above-mentioned related content, and control logic is similar with above-mentioned related description, this
In repeat no more.
It should be noted that in the start-up course of buck convertor, since system can not be responded in time,
Its output voltage moment cannot reach stable state, and feedback voltage is caused to be far smaller than reference voltage, cause error amplifier not
It can work in equilibrium state, make system with absolutely duty cycle, cause inductance L and load capacitance C resonance, generate number
The overshoot voltage of times input voltage causes very big surge current to flow into load capacitance C, is most likely to damage power in this way and opens
Close pipe and other devices.
For this purpose, the embodiment of the present application provides a kind of DC-DC converter, it is charging using periodic charging current
Capacitor charges, to provide the reference voltage slowly risen as DC-DC converter using the voltage on charging capacitor, with
This come limit buck convertor work duty ratio, thus achieve the purpose that eliminate surge current.Also, due to subtracting accordingly
The small charging current to charging capacitor can also be provided using the lesser charging capacitor of capacitance for DC-DC transformer
Reference voltage reduces the capacitance of charging capacitor, achievees the effect that be conducive to circuit integration, reduces application cost.
Specifically, referring to Figure 11, which is the structure of another DC-DC converter provided by the embodiments of the present application
Schematic diagram.Compared to Fig. 2, this figure provides a kind of more specifical DC-DC converters.
In some possible implementations of the embodiment of the present application, which can also include: charging
Control circuit 200, charging capacitor C1 and benchmark output circuit 300；
Charging control circuit 200, for periodically providing charging current for charging capacitor C1；
Benchmark output circuit 300, for providing benchmark electricity to current output circuit 110 based on the voltage on charging capacitor C1
Press Vrefs.
In the present embodiment, since charging control circuit 200 periodically provides charging current for charging capacitor C1,
It enables to the voltage on charging capacitor C1 to be slowly increased after starting, is also just provided accordingly for current output circuit 110 slow
Slow increased reference voltage Vrefs, limits the voltage in start-up course between reference voltage Vrefs and output voltage Vout
Difference achievees the purpose that eliminate surge current to limit the duty ratio of startup control signal.Also, because periodically
For charging capacitor power supply, impact of the charging current to charging capacitor C1 is reduced, reduces and the height of charging capacitor C1 capacitance is wanted
It asks, the control to reference voltage Vrefs can be realized using the lesser charging capacitor C1 of capacitance, reduce circuit cost, it can be with
It realizes integrating on chip, achievees the effect that be conducive to circuit integration.
In the embodiment of the present application, charging current periodically is provided for charging capacitor using charging control circuit, so that
Voltage on charging capacitor slowly increases, and then, benchmark output circuit utilizes the voltage on charging capacitor to current output circuit
Reference voltage is provided, current output circuit benchmark voltage and its practical output voltage provided to load are carried out
Negative feedback control provides the output voltage after being depressured supply voltage for load.Since the voltage on charging capacitor slowly increases,
Output voltage is allowed to reach reference voltage in time, system can reach equilibrium state in time, avoid generating excessive surge
Electric current.Also, because periodically powering for charging capacitor, the impact to charging capacitor is reduced, then can use compared with little Rong
The capacitor of value realizes integrating on chip, reduces application cost as the charging capacitor.
Referring to Figure 12, which is the structural schematic diagram of another DC-DC converter provided by the embodiments of the present application.Phase
Compared with Figure 11, this figure provides a kind of more specifical DC-DC converters.
In some possible implementations of the embodiment of the present application, charging control circuit be can specifically include: current mirror
210 and control signal output module 220；
The first branch of current mirror 210 connects supply current I0, the second branch connection charging capacitor C1 of current mirror 210；
Current mirror 210 is used for supply current I0Mirror image to current mirror 210 second branch.
It is understood that current mirror is a basic unit in analog circuit, it can be used for replica current, it can also be with
It generally may include cascade type (cascode) current mirror and Wilson's (Wilson) electric current as being loaded to differential pair
Mirror.In the present embodiment, current mirror 210 is used for the supply current I that will be provided in the first branch0Second branch is copied to, is the
The charging capacitor C1 charging of two branches connection.
In practical applications, current mirror 210 can be realized using any one current-mirror structure.Such as shown in Figure 13, electricity
Stream mirror 210 can be cascade type current mirror.
Signal output module 220 is controlled, for exporting control signal VGIt is periodical with the second branch for controlling current mirror 210
Turn-on and turn-off.
It is understood that as control signal VGWhen controlling the second branch conducting of current mirror 210, mirror image to second branch
Supply current I0Output is to charging capacitor C1, to charge for charging capacitor C1；And when control signal VG controls current mirror 210
Second branch shutdown when, the charging current of cutting output to charging capacitor C1, to disconnect to the charging of charging capacitor C1 electricity
Stream stops the charging to charging capacitor C1.In this way, by the periodic turn-on and turn-off of second branch of control current mirror 210,
Periodic charging current is provided for charging capacitor C1, since charging capacitor C1 does not leak electricity, also allows for charging capacitor C1
On voltage gradually rise, allow output voltage to reach reference voltage in time, system can reach equilibrium state in time, keep away
Exempt to generate excessive surge current.
In some possible implementations of the embodiment of the present application, with continued reference to Figure 13, signal output module is controlled, specifically
It may include: the first signal output branch 221, second signal output branch 222 and logic gate branch 223；
First signal exports the input terminal and logic gate branch of the output end connection second signal output branch 222 of branch 221
The first input end on road 223；Second signal exports the second input terminal of the output end connection logic gate branch 223 of branch 222；It patrols
Collect the second branch of the output end connection current mirror 210 of door branch 223；
First signal exports branch 221, for exporting the first clock signal VABranch 222 and logic are exported to second signal
The first input end of door branch 223；
Second signal exports branch 222, is used for the first clock signal VAIt carries out delay and reversely, obtains second clock letter
Number VBIt exports to the second input terminal of logic gate branch 223；
Logic gate branch 223, for the first clock signal VAWith second clock signal VBNAND operation is carried out, is controlled
Signal V processedGIt exports to the second branch of current mirror 210, so that the second branch of current mirror 210 is in control signal VGControl under
On or off.
In the present embodiment, pass through the first clock signal VABe delayed and reversely after available with its opposite in phase and deposit
In the second clock signal V of a fixed response timeB, to the first clock signal VAWith second clock signal VBNAND Logic operation is carried out, it can
To control signal VGLow and high level output situation be adjusted, thus realize to 210 second branch of current mirror be connected and close
The adjustment of disconnected situation, controls the charging process to charging capacitor C1, can not only control the growth of voltage on charging capacitor C1
Journey reduces surge current, additionally it is possible to avoid impact of the charging current to charging capacitor C1, reduce to the capacitance of charging capacitor (such as
It 1pF) requires, realizes integrated on chip, reduction application cost.
Illustrated one kind the first clock signal V of Figure 14A, second clock signal VBAnd its corresponding control signal VG.?
In this example, as control signal VGWhen for high level, the second branch shutdown of current mirror 210；As control signal VGFor low level
When, the second branch conducting of current mirror 210.
In a specific example, as shown in figure 15, the first signal output branch may include: oscillator OSC and divide
Frequency circuit 221a.Second signal exports branch, may include: delay circuit 222a and phase inverter INV；Logic gate branch, comprising:
NAND gate NAND；
The input terminal of the divided circuit 221a connection delay circuit 222a of the output end of oscillator OSC and NAND gate NAND's
First input end；
The second input terminal of the inverted device INV connection NAND gate NAND of the output end of delay circuit 222a；
The second branch of the output end connection current mirror 210 of NAND gate NAND.
In the present embodiment, frequency dividing circuit 221a reduces signal for realizing the signal frequency split exported to oscillator OSC
Frequency obtains the first clock signal VA, the turn-on frequency of the second branch of current mirror 210 is reduced, is slowed down on charging capacitor C1
The growth rate of voltage achievees the effect that reduce surge current.As an example, frequency dividing circuit 221a specifically can be used for
Eight scaling down processings are carried out to the signal of oscillator OSC output.In practical applications, frequency dividing circuit 221a can use a D touching
It sends out device or multiple concatenated d type flip flops is realized, how using d type flip flop to realize that frequency dividing is the common knowledge of this field, here
It repeats no more.When it is implemented, can specifically be set to the d type flip flop quantity that frequency dividing circuit 221a includes according to actual needs
It is fixed.
It is understood that the first clock signal V that delay circuit 222a exports frequency dividing circuit 221aAAfter being delayed
Output to phase inverter INV carry out reversely to get arrive second clock signal VB.In practical applications, delay circuit 222a can benefit
Realize that n is positive integer with 2n concatenated phase inverters.In a kind of possible design, with continued reference to Figure 15, second signal output
Branch 222 can also include switching tube M0, resistance R0 and capacitor C0, to filter out the interference of burr voltage.Then, NAND gate is utilized
NAND can be to the first clock signal VAWith second clock signal VBNAND Logic operation is executed, control signal V is obtainedGIt reduces
The turn-on time of 210 second branch of current mirror.
Referring to Figure 16, which is the structural schematic diagram of another DC-DC converter provided by the embodiments of the present application.Phase
Compared with Figure 11, this figure provides a kind of more specifical DC-DC converters.
In some possible implementations of the embodiment of the present application, benchmark output circuit be can specifically include: the first output
Branch 310, second exports branch 320 and comparison circuit 330；
First output branch 310, under the control of comparison circuit 330, the voltage Vsoft on charging capacitor C1 to be made
It exports for benchmark voltage Vrefs to current output circuit 110；
Second output branch 320, under the control of comparison circuit 330, using reference voltage Vref as reference voltage
Vrefs is exported to current output circuit 110；
Comparison circuit 330, the voltage Vsoft on comparison reference voltage Vref and charging capacitor C1；It is also used to when ginseng
When examining the voltage Vsoft that voltage Vref is greater than on charging capacitor C1, control the first output branch 310 is exported on charging capacitor C1
Voltage Vsoft is as reference voltage Vrefs to current output circuit 110；When reference voltage Vref is less than on charging capacitor C1
When voltage Vsoft, the second output 320 output reference voltage Vref of branch of control exports electricity as reference voltage Vrefs to electric current
Road 110.
In the embodiment of the present application, reference voltage Vref is the voltage value that output is stablized in DC-DC transformer expectation.
What needs to be explained here is that although charging control circuit 200 periodically provides charging current for charging capacitor C1, so that charging
Voltage Vsoft on capacitor C1 is slowly increased, and can make the reference voltage provided based on the voltage Vsoft on charging capacitor C1
Vrefs is slowly increased, and reduces surge current on startup, but after starting a period of time, if still with charging capacitor C1
On voltage Vsoft current output circuit 110 is controlled as reference voltage Vrefs, the voltage on charging capacitor C1
Vsoft sustainable growth will affect the actual output situation of current output circuit 110, cause the output electricity of current output circuit 110
Pressure is undesirably.Therefore, in the present embodiment, the benchmark electricity of 330 pairs of comparison circuit outputs to current output circuit 110 is utilized
Pressure Vrefs is selected, will be on charging capacitor C1 when reference voltage Vref is greater than the voltage Vsoft on charging capacitor C1
Voltage Vsoft is exported as reference voltage Vrefs to current output circuit 110, ensure that the slow increasing of reference voltage Vrefs
Add；And when the voltage Vsoft on charging capacitor C1 increases to greater than reference voltage Vref, using reference voltage Vref as benchmark
Voltage Vrefs is exported to current output circuit 110 so that current output circuit 110 be based on reference voltage Vref stablize output with
It is expected that the voltage being consistent.
In some possible implementations of the embodiment of the present application, as shown in figure 17, the first output branch may include:
First switch module 311；Second output branch, may include: second switch module 321；Comparison circuit may include: to compare
Device COMP；
The high voltage end of the first end connection charging capacitor C1 of first switch module 311, the second of first switch module 311
The reference voltage input of end connection current output circuit 110；
The first end of second switch module 321 connects reference voltage Vref, and the second end of second switch module 321 connects electricity
Flow the reference voltage input of output circuit 110；
The positive input terminal of comparator COMP connects reference voltage Vref, and the negative input end of comparator COMP connects charging capacitor
The high voltage end of C1, the control terminal and second switch module 321 of the output end connection first switch module 311 of comparator COMP
Control terminal；
When comparator COMP exports high level, the conducting of first switch module 311, second switch module 321 are turned off；When than
When exporting low level compared with device COMP, the conducting of second switch module 321, first switch module 311 are turned off.
It is understood that the high voltage end of the connection charging capacitor C1 of first switch module 311, i.e. first switch module
The input of 311 first ends is the voltage Vsoft on charging capacitor C1；Similarly, the negative input end connection charging electricity of comparator COMP
Hold the high voltage end of C1, i.e. the input of comparator COMP negative input end is the voltage Vsoft on charging capacitor C1.Then, work as reference
When voltage Vref is greater than the voltage Vsoft on charging capacitor C1, comparator COMP output is high level, first switch module 311
Conducting, second switch module 321 turn off, and the first output branch conducting exports the voltage Vsoft on charging capacitor C1 as benchmark
Voltage Vrefs to reduction voltage circuit 100 reference voltage input；When reference voltage Vref is less than the voltage on charging capacitor C1
When Vsoft, comparator COMP output is low level, and the conducting of second switch module 321, first switch module 311 turn off, and second is defeated
Out branch conducting, output reference voltage Vref are inputted as the reference voltage of reference voltage Vrefs to current output circuit 110
End.
In practical applications, first switch module 311 and second switch module 321 can use any one switching device
It realizes.As an example, first switch module 311 and/or second switch module 321 can be transmission gate.
In some possible implementations of the embodiment of the present application, can also DC-DC converter stablize output after,
Charge closing control circuit is to reduce power consumption.
Specifically, comparison circuit, can be also used for the ratio according to voltage Vsoft in reference voltage Vref and charging capacitor C1
Compared with as a result, enabled charging control circuit.
It should be noted that comparison circuit control is filled when reference voltage Vref is greater than voltage Vsoft on charging capacitor C1
Electric control circuit works normally, and illustrates the related content for being referred to above-described embodiment, provides slowly above-mentioned benchmark electricity
Vrefs is pressed, surge current is reduced.And when reference voltage Vref is less than voltage Vsoft on charging capacitor C1, comparison circuit control
Charging control circuit stops working, so that reduction voltage circuit is stable to load output voltage under the control of reference voltage Vref.
In one example, it can turn off or open included by charging control circuit according to the comparison result of comparison circuit
Current mirror, such as control current mirror the first branch and/or second branch on or off.In some possible designs, when
It, can also be to the frequency dividing circuit included by charging control circuit when reference voltage Vref is less than voltage Vsoft on charging capacitor C1
Carry out reset operation.A kind of illustrated specific structure of charging control circuit and benchmark output circuit of Figure 18.
In some possible implementations of the embodiment of the present application, benchmark output circuit may include: enabled branch；
Enabled branch, for enabling benchmark output circuit under the control of enable signal EN.
As an example, as shown in figure 18, enabled branch may include the switching tube M4 in parallel with charging capacitor C1.When
When circuit does not power on, enable signal EN is high level, and switching tube M4 is connected, and voltage Vsoft is zero on charging capacitor C1, and benchmark is defeated
The reference voltage Vrefs that circuit 300 exports out is zero, and benchmark output circuit does not work；After circuit powers on, enable signal EN is low
Level, switching tube M4 shutdown start as charging capacitor C1 charging, benchmark output circuit normal work.
The above is only the preferred embodiment of the application, not makes any form of restriction to the application.Though
Right the application has been disclosed in a preferred embodiment above, however is not limited to the application.It is any to be familiar with those skilled in the art
Member, in the case where not departing from technical scheme ambit, all using the methods and technical content of the disclosure above to the application
Technical solution makes many possible changes and modifications or equivalent example modified to equivalent change.Therefore, it is all without departing from
The content of technical scheme, any simple modification made to the above embodiment of the technical spirit of foundation the application are equal
Variation and modification, still fall within technical scheme protection in the range of.
Claims (10)
1. a kind of DC-DC converter characterized by comprising current output circuit, inductance, is born reverse-filling switch module
Carry capacitor and ON-OFF control circuit；
First end of the output end of the current output circuit one by one through the reverse-filling switch module, the inductance and described negative
Carry the first end of the first end connection load of capacitor；The second end of the reverse-filling switch module is one by one through the load capacitance
Second end and the second end of load ground connection；
The current output circuit, the voltage applied on benchmark voltage and the load provide negative to the load
Carry electric current；
The ON-OFF control circuit, for detecting the voltage of the reverse-filling switch module first end；When the reverse-filling switchs
When the voltage of module first end is greater than or equal to zero, the reverse-filling switch module shutdown is controlled.
2. DC-DC converter according to claim 1, which is characterized in that the ON-OFF control circuit, comprising: ratio
Compared with module and control module；
The first input end of the comparison module connects the first end of the reverse-filling switch module, and the second of the comparison module
The output end of input end grounding, the comparison module connects the control module；Described in the output end connection of the control module
The control terminal of reverse-filling switch module；
Whether the comparison module, the voltage for the reverse-filling switch module first end are greater than zero；When described anti-down
When filling the voltage of switch module first end greater than zero, the first comparison signal of output to the control module；
The control module, for when receiving first comparison signal, exporting first control signal to the reverse-filling
The control terminal of switch module, to control the reverse-filling switch module shutdown.
3. DC-DC converter according to claim 2, which is characterized in that the comparison module, comprising: current mirror,
First NMOS tube, the second NMOS tube and third NMOS tube；
The current mirror provides equal electric current for the drain electrode of first NMOS tube and the drain electrode of second NMOS tube；
The grid of first NMOS tube connects drain electrode and the grid of second NMOS tube of first NMOS tube, and described the
The source electrode of one NMOS tube is grounded；
The source electrode of second NMOS tube connects the first end of the reverse-filling switch module；
The grid of the third NMOS tube connects the drain electrode of second NMOS tube, the source electrode ground connection of the third NMOS tube, institute
The drain electrode for stating third NMOS tube connects power supply and the control module.
4. DC-DC converter according to claim 3, which is characterized in that the comparison module, further includes: logic
Amplify submodule；
Two input terminals of the logic amplification submodule are separately connected the drain electrode of the third NMOS tube and the reverse-filling is opened
Close the control terminal of module；
The logic amplifies submodule, for exporting the voltage amplification of the drain electrode output of the third NMOS tube.
5. DC-DC converter according to claim 4, which is characterized in that the logic amplifies submodule, comprising:
First phase inverter and with door；
The drain electrode of the third NMOS tube is through first phase inverter connection first input end with door；
The control terminal that the reverse-filling switch module is connect with the second input terminal of door.
6. according to the described in any item DC-DC converters of claim 3 to 5, which is characterized in that the switch control electricity
Road, further includes: enabled module；
The enabled module enables the comparison module for the on off operating mode based on the reverse-filling switch module.
7. DC-DC converter according to claim 6, which is characterized in that the enabled module, comprising: first opens
Close pipe and/or second switch；
The first end of the first switch tube connects the source electrode of second NMOS tube, the second termination of the first switch tube
Ground, the control terminal of the first switch tube connect the control terminal of the reverse-filling switch module；
The first end of the second switch connects the grid of the third NMOS tube, the second termination of the second switch
Ground, the control terminal of the second switch connect the control terminal of the reverse-filling switch module.
8. DC-DC converter according to claim 7, which is characterized in that the enabled module, further includes: third is opened
Guan Guan；
The first end and second end of the third switching tube is separately connected the first end and described of the reverse-filling switch module
The source electrode of two NMOS tubes, the control terminal of the third switching tube connect the control terminal of the reverse-filling switch module.
9. according to the described in any item DC-DC converters of claim 3 to 5, which is characterized in that the comparison module, also
It include: resistance；
The resistance is connected between the first end of the reverse-filling switch module and the source electrode of second NMOS tube.
10. according to the described in any item DC-DC converters of claim 3 to 5, which is characterized in that the current mirror is total
Source source common-gate current mirror structure, comprising: electric current inputs branch, the first mirror image branch, the second mirror image branch and third mirror image branch；
The input terminal of the electric current input branch connects input current, by the input current mirror image to the first mirror image branch
Road, second mirror image branch and the third mirror image branch；
First mirror image branch, second mirror image branch and the third mirror image branch are separately connected first NMOS tube
Drain electrode, the drain electrode of second NMOS tube and the drain electrode of the third NMOS tube.
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Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN111969704A (en) * | 2020-08-10 | 2020-11-20 | 中山大学 | Photovoltaic cell control circuit and control method |
| CN112968518A (en) * | 2021-03-11 | 2021-06-15 | 湖南国科微电子股份有限公司 | Power supply system comprising backup power supply |
| CN114172366A (en) * | 2022-01-24 | 2022-03-11 | 澳门大学 | DC converter and electronic device |
| CN114185288A (en) * | 2021-11-25 | 2022-03-15 | 重庆川仪自动化股份有限公司 | Current output instrument, current transducer and control system |
| CN115328247A (en) * | 2022-08-16 | 2022-11-11 | 骏盈半导体(上海)有限公司 | Power supply module and voltage stabilizing circuit |
Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1992494A (en) * | 2005-12-26 | 2007-07-04 | 富士通株式会社 | Dc-dc converter and control circuit for dc-dc converter |
| CN101902215A (en) * | 2010-08-02 | 2010-12-01 | 中颖电子有限公司 | Four-input terminal comparator |
| WO2012144163A1 (en) * | 2011-04-20 | 2012-10-26 | ルネサスエレクトロニクス株式会社 | Dc-dc converter and method of controlling thereof |
| US20130127428A1 (en) * | 2011-11-17 | 2013-05-23 | Renesas Electronics Corporation | Dc-dc converter |
| US20160141959A1 (en) * | 2014-11-18 | 2016-05-19 | Rohm Co., Ltd. | Switching power supply |
| CN108063553A (en) * | 2016-11-07 | 2018-05-22 | 罗姆股份有限公司 | DC/DC converters |
| CN108258895A (en) * | 2018-02-05 | 2018-07-06 | 上海艾为电子技术股份有限公司 | Soft starting circuit and power-supply system |
-
2019
- 2019-07-26 CN CN201910683692.7A patent/CN110311562A/en active Pending
Patent Citations (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1992494A (en) * | 2005-12-26 | 2007-07-04 | 富士通株式会社 | Dc-dc converter and control circuit for dc-dc converter |
| CN101902215A (en) * | 2010-08-02 | 2010-12-01 | 中颖电子有限公司 | Four-input terminal comparator |
| WO2012144163A1 (en) * | 2011-04-20 | 2012-10-26 | ルネサスエレクトロニクス株式会社 | Dc-dc converter and method of controlling thereof |
| US20160065074A1 (en) * | 2011-04-20 | 2016-03-03 | Renesas Electronics Corporation | Dc-dc converter and control method for the same |
| US20130127428A1 (en) * | 2011-11-17 | 2013-05-23 | Renesas Electronics Corporation | Dc-dc converter |
| US20160141959A1 (en) * | 2014-11-18 | 2016-05-19 | Rohm Co., Ltd. | Switching power supply |
| CN108063553A (en) * | 2016-11-07 | 2018-05-22 | 罗姆股份有限公司 | DC/DC converters |
| CN108258895A (en) * | 2018-02-05 | 2018-07-06 | 上海艾为电子技术股份有限公司 | Soft starting circuit and power-supply system |
Non-Patent Citations (3)
| Title |
|---|
| 罗会彬: "《深水炸弹技术》", 30 September 2016 * |
| 美国RCA公司: "《实用电子电路62例》", 30 November 1986 * |
| 陈传元,等: "《超声波诊断仪的原理、应用及维修》", 31 October 1990 * |
Cited By (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN111969704A (en) * | 2020-08-10 | 2020-11-20 | 中山大学 | Photovoltaic cell control circuit and control method |
| CN111969704B (en) * | 2020-08-10 | 2021-07-20 | 中山大学 | Photovoltaic cell control circuit and control method |
| CN112968518A (en) * | 2021-03-11 | 2021-06-15 | 湖南国科微电子股份有限公司 | Power supply system comprising backup power supply |
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| CN114172366A (en) * | 2022-01-24 | 2022-03-11 | 澳门大学 | DC converter and electronic device |
| CN114172366B (en) * | 2022-01-24 | 2023-12-15 | 澳门大学 | DC converter and electronic device |
| CN115328247A (en) * | 2022-08-16 | 2022-11-11 | 骏盈半导体(上海)有限公司 | Power supply module and voltage stabilizing circuit |
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Application publication date: 20191008 |