CN109936318A - A kind of optimization method reducing motor electromagnetic loss - Google Patents
A kind of optimization method reducing motor electromagnetic loss Download PDFInfo
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- CN109936318A CN109936318A CN201910333145.6A CN201910333145A CN109936318A CN 109936318 A CN109936318 A CN 109936318A CN 201910333145 A CN201910333145 A CN 201910333145A CN 109936318 A CN109936318 A CN 109936318A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
- H02P21/02—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation specially adapted for optimising the efficiency at low load
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
- H02P21/24—Vector control not involving the use of rotor position or rotor speed sensors
- H02P21/28—Stator flux based control
- H02P21/30—Direct torque control [DTC] or field acceleration method [FAM]
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- Control Of Ac Motors In General (AREA)
- Iron Core Of Rotating Electric Machines (AREA)
Abstract
The present invention provides a kind of optimization methods of reduction motor electromagnetic loss, it is by considering the SVPWM Controlling model under magnetic saturation effect, establish the computation model of motor electromagnetic loss, to obtain reducing the optimization method of electromagnetic consumable in motor low speed high torque area, raising for motor peak torque provides theoretical foundation, realizes many effects not available in the prior art.
Description
Technical field
This application involves Motor Optimizing Design field more particularly to a kind of optimization methods for reducing motor electromagnetic loss.
Background technique
The peak torque of motor directly affects the acceleration capacity of motor, has vital work to motor power performance
With.The generation of motor electromagnetic loss and the interaction of motor built-in field are closely related, are to restrict motor peak torque
One key factor.Motor electromagnetic loss includes mainly winding copper loss, stator iron loss and rotor eddy current loss, due to rotor iron loss
In eddy-current loss be far longer than magnetic hystersis loss, rotor iron loss and permanent magnet eddy-current loss are collectively referred to as rotor eddy current loss.
Currently, SVPWM control is used widely in electric machines control technology.It is humorous that motor control generates a large amount of electric current
Wave, so that electromagnetic field harmonic components increase, electromagnetic consumable increases.Compared to traditional power frequency motor, the wide range speed control model of automobile motor
It encloses so that influence of the motor control mode to iron loss is deepened, the electromagnetic consumable calculating under causing motor SVPWM to control is necessary,
And the magnetic saturation effect of motor stator causes electromagnetic parameter nonlinear change, especially in low speed high torque area, magnetic saturation effect
It is more serious, so that the current harmonics that motor generates in SVPWM control process changes, and then influence the electromagnetism that motor generates
Loss.The electromagnetic consumable in motor low speed high torque area is higher simultaneously, causes the problem of temperature rise of motor prominent, limiting motor peak value turns
The promotion of square, and the optimization of electromagnetic consumable at present is primarily directed to declared working condition, there has been no in motor low speed high torque area
The research of electromagnetic consumable optimization aspect occurs.
Therefore, how on the basis of motor SVPWM Controlling model under considering magnetic saturation effect, a kind of reduction motor is proposed
The optimization method of electromagnetic consumable in low speed high torque area, the raising for motor peak torque provide theoretical foundation, are in this field
Urgent problem to be solved.
Summary of the invention
For technical problem present in above-mentioned this field, the present invention provides a kind of optimizations of reduction motor electromagnetic loss
Method, specifically includes the following steps:
Step 1: obtaining dq axis magnetic linkage data of the motor under different electric currents, established according to dq axis magnetic linkage and current relationship
Consider electric moter voltage, magnetic linkage and the electromagnetic torque equation of magnetic saturation effect.
Step 2: the motor SVPWM Controlling model under the non-linear magnetic linkage of the establishing equation established according to step, obtains
To phase current of the motor under low speed high torque operating condition.
Step 3: establishing motor based on the phase current obtained in the step 2 and considering that magnetic is full under SVPWM control
With the electromagnetic consumable computation model of effect.
Step 4: using the electromagnetic consumable computation model established in the step 3, to the motor stator facewidth and conducting wire
And the influence around radical to electromagnetic consumable under the low speed high torque operating condition is analyzed, and implements to reduce the excellent of the electromagnetic consumable
Change strategy.
Further, dq axis magnetic linkage data acquired in the step 1 are based on freezing magnetic conductivity method to the different electricity of motor
Dq axis magnetic linkage progress Nonlinear Simulation is flowed down to obtain.
Further, the dq axis magnetic linkage described in step 1 and electric current have following fit correlation:
Wherein,Respectively d, q axis magnetic linkage, KLd、KsdFor the curved shape for considering the total magnetic linkage of d axis under magnetic saturation effect
Shape coefficient, KsqdIt is q shaft current to the cross coupling effect coefficient of the total magnetic linkage of d axis, KLq、KsqTo consider q axis under magnetic saturation effect
The curve shape coefficient of total magnetic linkage, KsdqIt is d shaft current to the cross coupling effect coefficient of the total magnetic linkage of q axis,For different q axis electricity
Flow down the fixed value of d axis magnetic linkage, I0For d shaft current corresponding to fixed d axis magnetic linkage, id、iqRespectively d, q shaft current.
Further, the considerations of established in the step 1 magnetic saturation effect electric moter voltage, magnetic linkage and electromagnetic torque
Equation specifically includes:
Voltage equation:
Flux linkage equations:
Electromagnetic torque equation:
In formula, ω is angular rate, vd、vqRespectively d, q shaft voltage, RsFor phase resistance, p is number of pole-pairs.
Further, in the motor SVPWM Controlling model in the step 2, torque capacity electricity is respectively adopted according to operating condition
Motor stator dq shaft current can be obtained according to the flux linkage equations than control and weak magnetic control in stream are as follows:
Motor SVPWM system mainly includes control module and motor module two parts, and motor control module is referred to by revolving speed
It enables value, actual speed and dq shaft current that the instruction value of motor dq shaft voltage is calculated, modulates to obtain inverter IGBT through SVPWM
The control signal of switch.Motor module utilizes its mechanically and electrically characteristic, obtains electricity according to dq axis virtual voltage and actual speed
The working condition of machine obtains stator phase currents under the required different operating point of motor stator iron loss analysis.
Further, the electromagnetic consumable computation model is established in the step 3, is specifically included:
Winding copper loss is calculated based on motor individual harmonic current:
Wherein, m is number of motor phases, IkFor the virtual value of kth subharmonic current, RdcFor winding phase resistance；
Motor stator is divided into N number of subdivision by the finite element model that motor is established according to the geometry of motor and size
Unit obtains the tangential magnetic flux density of diameter of each subdivision unit of stator under permanent magnet and phase current common activation through finite element simulation,
The stator iron loss of motor, while the calculation method reference of rotor iron loss are obtained using the segmentation variable coefficient iron loss computation model of motor
Stator iron loss calculation method.The computation model of stator iron loss is as follows:
Wherein, PFeFor stator core loss, PhFor magnetic hystersis loss, PeFor eddy-current loss, PecxFor added losses, kh, α be magnetic
Stagnant loss factor, keFor eddy current loss factor, kecxFor added losses coefficient, kh、ke、kecx, α be classical loss separation model
Loss factor, can be fitted to obtain by the lossy data of actual measurement, f is electric machine frequency, krFor rotary magnetization loss factor, BnkFor
Kth time magnetic flux density harmonic amplitude, n1kBnk β1kMagnetic flux density low order item, n are added for magnetic hystersis loss2kBnk β2kIt is attached for eddy-current loss
Add magnetic flux density high-order term, n1k、β1k、n2k、β2kFor added losses coefficient, the orthogonal loss number under actual measurement different frequency can be passed through
It is obtained according to fitting, LaFor stator shaft orientation length, ρ is stator silicon steel sheet density, Ph (i)、Pe (i)、Pecx (i)Respectively i-th of stator list
Magnetic hysteresis, vortex and the added losses density of member, Δs (i)For the area of i-th of unit, NsFor the quantity of subdivision unit.
According to the phase current under motor low speed high torque operating point, permanent magnet is vortexed by three-dimensional Time-stepping FEM
Loss is accurately calculated:
Wherein, J is current density, and σ is conductivity, and V is the volume of permanent magnet blocks.
Further, electromagnetic consumable is optimized including suitably reducing tooth under low speed high torque operating condition in the step 4
Width increases the conductor in parallel radical in stator slot.
The above method provided by the present invention establishes motor electricity by considering the SVPWM Controlling model under magnetic saturation effect
The computation model of magnetic loss is motor peak to obtain the optimization method for reducing electromagnetic consumable in motor low speed high torque area
The raising of value torque provides theoretical foundation, realizes many effects not available in the prior art.
Detailed description of the invention
Fig. 1 is the flow chart of method provided by the present invention
Fig. 2 is variation relation of the total magnetic linkage of motor dq axis with dq shaft current
Fig. 3 is the motor correction module under motor consideration magnetic saturation effect in SVPWM Controlling model
Fig. 4 is the stator structure figure of internal permanent magnet synchronous motor
Fig. 5 is that internal permanent magnet synchronous motor difference facewidth structure is distributed in the phase current of peak value operating point
Fig. 6 is the electromagnetic consumable distribution before optimizing under the internal permanent magnet synchronous motor difference facewidth
Fig. 7 is the electromagnetic consumable distribution after optimizing under the internal permanent magnet synchronous motor difference facewidth
Specific embodiment
With reference to the accompanying drawing to a kind of optimization for reducing electromagnetic consumable in motor low speed high torque area provided by the present invention
Method is made and further being illustrated in detail.
As shown in Figure 1, method provided by the present invention specifically includes the following steps:
Step 1: obtaining dq axis magnetic linkage data of the motor under different electric currents, established according to dq axis magnetic linkage and current relationship
Consider electric moter voltage, magnetic linkage and the electromagnetic torque equation of magnetic saturation effect.
Step 2: the motor SVPWM Controlling model under the non-linear magnetic linkage of the establishing equation established according to step, obtains
To phase current of the motor under low speed high torque operating condition.
Step 3: establishing motor based on the phase current obtained in the step 2 and considering that magnetic is full under SVPWM control
With the electromagnetic consumable computation model of effect.
Step 4: using the electromagnetic consumable computation model established in the step 3, to the motor stator facewidth and conducting wire
And the influence around radical to electromagnetic consumable under the low speed high torque operating condition is analyzed, and implements to reduce the excellent of the electromagnetic consumable
Change strategy.
In the preferred embodiment of the application, the dq axis magnetic linkage data can be based on freezing magnetic conductivity method to motor not
It carries out Nonlinear Simulation with dq axis magnetic linkage under electric current to obtain, the fit correlation between magnetic linkage and electric current is as shown in table 1 and Fig. 2.
Table 1
Motor is considered that motor module is modified to as shown in figure 3, control strategy in the SVPWM Controlling model of magnetic saturation effect
It remains unchanged.Motor is obtained in the stator phase currents of low speed high torque operating point according to the SVPWM model.
In the preferred embodiment of the application, using a 370kW internal permanent magnet synchronous motor as research object, electricity
The stator structure of machine is as shown in figure 4, to study the stator facewidth and winding parameter for peak value operating point (1000rpm, 1660Nm)
Influence to electric machine phase current, electromagnetic field and electromagnetic consumable.When analyzing the facewidth, the 4~10mm that is dimensioned to of the facewidth is protected
Demonstrate,prove the high h of motor yokejIt is constant, and stator bottom and top facewidth ratio bt1/bt2It is constant.Based on the above principle, motor can be obtained not
With the stator slot parameter under the facewidth.Then different facewidth motors are obtained in the phase of peak value operating point according to the SVPWM Controlling model
Electric current, as shown in Figure 5.The inductance of motor, magnetic linkage parameter change with the variation of the facewidth, cause different facewidth motors in peak value
The phase current difference of operating point is larger.In the case where guaranteeing that winding parameter is constant, the facewidth is smaller, needs under same peak operation point
The phase current wanted is bigger.
According to phase current of the different facewidth motors under peak operation point, using in electromagnetic consumable computation model about each damage
The formula of consumption calculates separately to obtain the electromagnetic consumable under the motor difference facewidth, as shown in Figure 6.Found out by figure, motor total losses are equal
Increase with the reduction of the facewidth, wherein copper loss occupies significant proportion in total losses, and when the facewidth is smaller, higher phase current is led
The copper loss for sending a telegraph machine is larger, and the amplitude of variation of stator iron loss and rotor eddy current loss under same load behavior is little.Meanwhile
When the facewidth is smaller, copper factor is reduced, and can be had enough stator slot spaces to optimize winding parameter at this time, be realized copper loss
It reduces, to realize the reduction of motor electromagnetic loss.
For the influence that motor electromagnetic is lost in research winding parameter, realize that winding parameter exists by change conducting wire and around radical
The optimization of stator slot guarantees that the umber of turn of motor and line footpath are constant in the analysis process, ignore the voltage drop in phase resistance with
And conducting wire and change influence to induced electromotive force around radical.Winding conducting wire does not simultaneously generate shadow to phase current around the change of radical
It rings, but conducting wire and the sectional area for changing winding around the variation of radical, is in inverse relation with phase resistance, with conducting wire and around radical
Increase, phase resistance accordingly reduces.Therefore, conducting wire and the copper loss of winding can be changed around the variation of radical, but to stator iron loss
Influence with rotor eddy current loss can be ignored, and then influence the size of motor total losses.Assuming that conducting wire and around radical be Nt1,
Phase resistance is R, and stator copper factor is Sf1, now N is changed by conducting wire and around radicalt2, then stator phase resistance R '=(N at this timet1/
Nt2) R, copper factor Sf2=(Nt2/Nt1)Sf1, the winding copper loss of motor may be expressed as:
The winding copper loss under motor difference stator copper factor can be obtained with the change curve of the facewidth according to above formula, it is basic herein
On, obtain the total losses under motor difference copper factor with the change curve of the facewidth, as shown in Figure 7.For the certain electricity of internal-and external diameter
Machine, it is appropriate to reduce the stator facewidth, there are enough spaces that can increase the conducting wire of motor and around radical in stator slot, so that phase resistance
Reduce, winding copper loss reduces, and motor is caused to reduce in the total losses in low speed high torque area.In same stator slot, increase conducting wire
And around radical copper factor being increased, phase resistance reduces, and the copper loss and total losses of motor reduce, but embed the wire for convenience, stator
Copper factor should not be too large.Under same stator copper factor, the stator facewidth influences the loss under motor peak operation point.With the facewidth
Reduction, biggish stator slot space make conducting wire and around radical increase, phase resistance reduce, cause copper loss to reduce, but too small
The facewidth, phase current make greatly copper loss relatively large very much, cause the total losses of motor first to reduce with the reduction of the facewidth and increase afterwards.Cause
This, the reduction stator facewidth appropriate increases the conducting wire of winding and around radical, can reduce motor in the copper loss in low speed high torque area and
Total losses.
It although an embodiment of the present invention has been shown and described, for the ordinary skill in the art, can be with
A variety of variations, modification, replacement can be carried out to these embodiments without departing from the principles and spirit of the present invention by understanding
And modification, the scope of the present invention is defined by the appended.
Claims (7)
1. a kind of optimization method for reducing motor electromagnetic loss, it is characterised in that: specifically includes the following steps:
Step 1: obtaining dq axis magnetic linkage data of the motor under different electric currents, is established and considered according to dq axis magnetic linkage and current relationship
Electric moter voltage, magnetic linkage and the electromagnetic torque equation of magnetic saturation effect.
Step 2: the motor SVPWM Controlling model under the non-linear magnetic linkage of the establishing equation established according to step, obtains electricity
Phase current of the machine under low speed high torque operating condition.
Step 3: establishing motor based on the phase current obtained in the step 2 and considering magnetic saturation effect under SVPWM control
The electromagnetic consumable computation model answered.
Step 4: using the electromagnetic consumable computation model established in the step 3, to the motor stator facewidth and conducting wire and around
Influence of the radical to electromagnetic consumable under the low speed high torque operating condition is analyzed, and the optimization plan for reducing the electromagnetic consumable is implemented
Slightly.
2. the method as described in claim 1, it is characterised in that: acquired dq axis magnetic linkage data are based on freezing in the step 1
Knot magnetic conductivity method carries out Nonlinear Simulation to dq axis magnetic linkage under motor difference electric current and obtains.
3. the method as described in claim 1, it is characterised in that: the dq axis magnetic linkage described in step 1 and electric current have with
Lower fit correlation:
Wherein, φd、φqRespectively d, q axis magnetic linkage, KLd、KsdFor the curve shape system for considering the total magnetic linkage of d axis under magnetic saturation effect
Number, KsqdIt is q shaft current to the cross coupling effect coefficient of the total magnetic linkage of d axis, KLq、KsqTo consider the total magnetic of q axis under magnetic saturation effect
The curve shape coefficient of chain, KsdqIt is d shaft current to the cross coupling effect coefficient of the total magnetic linkage of q axis, φ0For under different q shaft currents
The fixed value of d axis magnetic linkage, I0For d shaft current corresponding to fixed d axis magnetic linkage, id、iqRespectively d, q shaft current.
4. method as claimed in claim 3, it is characterised in that: it is established in the step 1 the considerations of magnetic saturation effect electricity
Electromechanics pressure, magnetic linkage and electromagnetic torque equation, specifically include:
Voltage equation:
Flux linkage equations:
Electromagnetic torque equation:
In formula, ω is angular rate, vd、vqRespectively d, q shaft voltage, RsFor phase resistance, p is number of pole-pairs.
5. method as claimed in claim 4, it is characterised in that: in the motor SVPWM Controlling model in the step 2, according to
Maximum torque per ampere control and weak magnetic control is respectively adopted in operating condition, and motor stator dq axis electricity can be obtained based on the flux linkage equations
Stream are as follows:
The working condition of motor is obtained according to dq axis virtual voltage and actual speed, is obtained needed for the analysis of motor stator iron loss not
With stator phase currents under operating point.
6. method as claimed in claim 5, it is characterised in that: the electromagnetic consumable computation model is established in the step 3,
It specifically includes:
Winding copper loss is calculated based on motor individual harmonic current:
Wherein, m is number of motor phases, IkFor the virtual value of kth subharmonic current, RdcFor winding phase resistance；
Motor stator is divided into multiple subdivision lists by the finite element model that motor is established according to the geometry of motor and size
Member obtains the tangential magnetic flux density of diameter of each subdivision unit of stator under permanent magnet and phase current common activation through finite element simulation, benefit
The stator iron loss for obtaining motor with the segmentation variable coefficient iron loss computation model of motor is as follows:
Wherein, PFeFor stator core loss, PhFor magnetic hystersis loss, PeFor eddy-current loss, PecxFor added losses, kh, α be magnetic hysteresis damage
Consume coefficient, keFor eddy current loss factor, kecxFor added losses coefficient, f is electric machine frequency, krFor rotary magnetization loss factor, Bnk
For kth time magnetic flux density harmonic amplitude, n1kBnk β1kMagnetic flux density low order item, n are added for magnetic hystersis loss2kBnk β2kFor eddy-current loss
Additional magnetic flux density high-order term, LaFor stator shaft orientation length, ρ is stator silicon steel sheet density, Ph (i)、Pe (i)、Pecx (i)Respectively i-th
Magnetic hysteresis, vortex and the added losses density of a stator unit, Δs (i)For the area of i-th of unit, NsFor the quantity of subdivision unit；
Calculation method of the rotor iron loss referring to said stator iron loss；
According to the phase current under motor low speed high torque operating point, by three-dimensional Time-stepping FEM to permanent magnet eddy-current loss
It is accurately calculated:
Wherein, J is current density, and σ is conductivity, and V is the volume of permanent magnet blocks.
7. the method as described in claim 1, it is characterised in that: in the step 4 under low speed high torque operating condition electromagnetic consumable
It optimizes including suitably reducing the facewidth, increases the conductor in parallel radical in stator slot.
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| CN201810450290.8A CN108631675A (en) | 2018-05-11 | 2018-05-11 | A kind of optimization method reducing electromagnetic consumable in motor low speed high torque area |
| CN2018104502908 | 2018-05-11 |
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| WO2020258802A1 (en) * | 2019-06-28 | 2020-12-30 | 西安交通大学 | Method for calculating iron loss resistance of variable frequency motor while considering pwm harmonic waves |
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| CN110380651B (en) * | 2019-09-19 | 2020-01-31 | 潍柴动力股份有限公司 | Motor design method and device for new energy vehicles |
| CN110688804B (en) * | 2019-10-08 | 2021-02-09 | 哈尔滨工业大学 | Oil-filled motor loss multi-element inhibition method |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20160046247A1 (en) * | 2014-08-18 | 2016-02-18 | Hamilton Sundstrand Corporation | Electric system architecture for more-electric engine accessories |
| CN107482982A (en) * | 2017-09-25 | 2017-12-15 | 合肥工业大学 | A kind of Vector Control System of Induction Motor method based on iron loss model |
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- 2018-05-11 CN CN201810450290.8A patent/CN108631675A/en not_active Withdrawn
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20160046247A1 (en) * | 2014-08-18 | 2016-02-18 | Hamilton Sundstrand Corporation | Electric system architecture for more-electric engine accessories |
| CN107482982A (en) * | 2017-09-25 | 2017-12-15 | 合肥工业大学 | A kind of Vector Control System of Induction Motor method based on iron loss model |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2020258802A1 (en) * | 2019-06-28 | 2020-12-30 | 西安交通大学 | Method for calculating iron loss resistance of variable frequency motor while considering pwm harmonic waves |
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Effective date of registration: 20210624 Address after: 014060 east of Guangyao road and south of Duan Road, Binhe new area, Baotou Rare Earth Development Zone, Inner Mongolia Autonomous Region Patentee after: BAOTOU TIANGONG MOTOR Co.,Ltd. Address before: 100081 No. 5 South Main Street, Haidian District, Beijing, Zhongguancun Patentee before: BEIJING INSTITUTE OF TECHNOLOGY |