CN109831131B - Control device, rotating electrical machine including the same, and control method - Google Patents

Abstract

A control device, a rotary electric machine including the control device, and a control method, wherein the rotary electric machine includes a rotor and a stator. The rotor is rotatably connected to the engine. The stator is disposed around the rotor. The control device comprises an induced voltage detection unit, an electrifying control unit and a starting judgment unit. The induced voltage detection unit detects an induced voltage induced in a stator coil provided in the stator. The energization control unit controls energization of the field winding provided in the rotor. The start-up judging unit judges the start-up of the energization control unit based on the amount of time between at least two of a plurality of rising times at which the induced voltage exceeds the judgment threshold and a plurality of falling times at which the induced voltage falls below the judgment threshold.

Description

Control device, rotating electrical machine including the same, and control method

Technical Field

The present disclosure relates to a control device for a rotary electric machine, a rotary electric machine including the control device, and a control method.

Background

As described in japanese patent publication No. 3189149, a voltage detection circuit is known that detects rotation of an alternator based on a phase voltage difference in a stator winding.

In the voltage detection circuit described in japanese patent publication No. 3189149, when the phase voltage difference exceeds about 0.6 volt, a signal indicating the rotational speed (about 1500 rpm) required to reach the alternator in the non-excited state is output from the first threshold comparator to the regulator. Upon receiving the signal, the regulator performs readjustment of the phase voltage by supplying an excitation current to the rotor of the alternator.

As described above, the threshold for determining whether the rotational speed of the alternator has reached a phase voltage difference of about 1500rpm is low, about 0.6 volts. Therefore, when the detected phase voltage difference includes noise, the above signal may be erroneously output from the first threshold comparator to the regulator. As a result, the regulator supplies exciting current to the rotor. Therefore, power consumption may be increased.

Disclosure of Invention

Accordingly, it is desirable to provide a control device, a rotary electric machine including the control device, and a control method that suppress an increase in power consumption.

Exemplary embodiments of the present disclosure provide a control apparatus for a rotating electrical machine. The rotating electrical machine includes a rotor rotatably connected to an engine, and a stator disposed around the rotor. The control device comprises an induced voltage detection unit, an electrifying control unit and a starting judgment unit. The induced voltage detection unit detects an induced voltage induced in a stator coil provided in the stator. The energization control unit controls energization of a field winding provided in the rotor. The start-up judging unit judges start-up of the energization control unit based on an amount of time between two of a plurality of rising times at which the induced voltage detected by the induced voltage detecting unit exceeds a judgment threshold and a plurality of falling times at which the induced voltage falls below the judgment threshold.

As described above, in the present disclosure, the judgment about the energization control unit driving is performed based on the change over time of the line voltage related to the judgment threshold. As a result, unlike a configuration in which the determination regarding the energization control unit driving is performed simply based on the voltage value of the induced voltage, erroneous determination of the energization control unit driving based on noise waves or the like is suppressed. As a result, the energization of the rotor field winding due to erroneous determination is suppressed. An increase in power consumption is suppressed.

Any reference numerals in parentheses in the claims denote only correspondence with the configurations described according to the embodiments described below, and do not limit the technical scope of the present disclosure in any way.

Drawings

In the drawings:

fig. 1 is a block diagram of a motor and a motor control device according to a first embodiment;

fig. 2 is a circuit diagram of an induced voltage detection unit and a start-up judgment unit according to the first embodiment;

fig. 3 is a timing chart for explaining the operations of the induced voltage detection unit and the start judgment unit;

fig. 4 is a timing chart for explaining the operations of the induced voltage detection unit and the start judgment unit when noise wave is input to the start judgment unit;

Fig. 5 is a circuit diagram for explaining a first modification of the start judging unit;

fig. 6 is a circuit diagram for explaining a start judging unit according to the second embodiment;

fig. 7 is a timing chart for explaining the operations of the induced voltage detection unit and the start judgment unit;

fig. 8 is a circuit diagram for explaining a second modification of the start judging unit;

fig. 9 is a circuit diagram for explaining a start judging unit according to the third embodiment;

fig. 10 is a timing chart for explaining the operations of the induced voltage detection unit and the start judgment unit;

fig. 11 is a circuit diagram for explaining a third modification of the start judging unit;

fig. 12 is a circuit diagram for explaining a fourth modification of the start judging unit;

fig. 13 is a timing chart for explaining the operations of the induced voltage detection unit and the start judgment unit;

fig. 14 is a circuit diagram for explaining a fifth modification of the start judging unit.

Detailed Description

Embodiments of the present invention will be described below with reference to the accompanying drawings.

(first embodiment)

A motor control device 100 according to a first embodiment will be described with reference to fig. 1 to 4. The motor control device 100 controls the motor 200 based on a request command from a high-order Electronic Control Unit (ECU) (main ECU). The motor control device 100 and the motor 200 constitute a so-called Integrated Starter Generator (ISG). The motor control device 100 corresponds to a control device.

The motor control device 100 and the motor 200 are integrated. That is, the motor control device 100 and the motor 200 have a so-called electromechanical integrated structure. The motor control device 100 and the motor 200 are housed in the engine compartment.

Motor 200 is connected to a crankshaft of engine 300 via a strap 310. The engine 300 is mounted in a vehicle. Accordingly, the motor 200 rotates with the crankshaft string (in range). When the motor 200 rotates autonomously, rotation is transmitted to the crankshaft. As a result, the crankshaft rotates. Thereby achieving starting of engine 300 or assisting in running of the vehicle. Conversely, when the crankshaft rotates autonomously, rotation is transmitted to the motor 200. As a result, the motor 200 rotates. Thereby achieving the power generation of the motor 200.

< Structure of Motor >

As shown in fig. 1, motor 200 includes a rotor 201 and a stator 202. In addition, the motor 200 includes a shaft and a pulley (not shown). The shaft is rotatably provided in the motor control device 100. The pulley is disposed at the end of the shaft. The belt 310 is connected to a pulley. As a result, rotation of the crankshaft is transmitted to the pulley via the belt 310. Instead, the rotation of the shaft is transferred to the crankshaft via the band 310. The motor 200 corresponds to a rotating electric machine.

The rotor 201 includes rotor coils 203. The rotor 201 further includes a fixing portion (not shown) that fixes the rotor coil 203 to the shaft. The fixing part is cylindrical. The shaft is inserted into and fixed to the hollow portion of the fixing portion. The rotor coil 203 is disposed in the fixed portion. The rotor coil 203 is electrically connected to wiring provided in the shaft. The wiring is electrically connected to the slip ring on the shaft. The slip ring is formed in a ring shape around the axis of the shaft. The annular slip ring is in contact with a brush comprising a conductive material. The brushes are electrically connected to the motor control apparatus 100. Current is supplied from the motor control device 100 to the brushes. Current is supplied to the rotor coil 203 via brushes, slip rings, and wiring. As a result, a magnetic field is generated in the rotor coil 203. Rotor coil 203 corresponds to a magnetic field winding.

As described above, as a result of the energization, a magnetic field is generated by the rotor coil 203. The magnetic field penetrates each rotor coil 203 and a fixing portion that fixes the rotor coil 203 to the shaft. Thus, the rotor coil 203 and the fixing portion are partially magnetized. As a result, although the magnetic field is weak, the rotor 201 outputs the magnetic field even if the rotor coil 203 is not energized as described above. The weak magnetic field also penetrates the stator coil 204.

The stator 202 includes stator coils 204. Stator 202 also includes a stator core (not shown) in which stator coils 204 are disposed. The stator core is cylindrical. The rotor 201 is disposed in a hollow portion in the stator core together with the shaft. In this way, the stator 202 is disposed around the rotor 201. Stator coil 204 includes a U-phase stator coil 205, a V-phase stator coil 206, and a W-phase stator coil 207.

The U-phase stator coil 205, the V-phase stator coil 206, and the W-phase stator coil 207 are each integrally connected to the motor control device 100 via bus bars. Three-phase alternating currents are supplied from motor control device 100 to U-phase stator coil 205, V-phase stator coil 206, and W-phase stator coil 207. The U-phase stator coil 205, the V-phase stator coil 206, and the W-phase stator coil 207 are supplied with alternating currents whose phases are shifted from each other by 120 degrees in electrical angle. As a result, a three-phase rotating magnetic field is generated by the U-phase stator coil 205, the V-phase stator coil 206, and the W-phase stator coil 207.

When current flows to the respective rotor coils 203 and stator coils 204, a magnetic field is generated by each coil. As a result, a rotational torque is generated in the rotor coil 203. The direction of the generated rotational torque is continuously changed based on the phase change of the three-phase rotating magnetic field. As a result, the shaft rotates autonomously. The pulley also rotates with the shaft. Rotation is transferred to the crankshaft via the belt 310. As a result, the crankshaft also rotates.

Conversely, when the engine 300 is driven by combustion to autonomously rotate the crankshaft, rotation is transmitted to the pulley via the belt 310. In addition, when the crankshafts are rotated together by rotation of the wheels, rotation is transmitted to the pulleys via the belt 310. As a result, the shaft rotates with the pulley. As a result, the rotor coil 203 also rotates. The magnetic field emitted from the rotor coil 203 intersects the stator coil 204. As a result, a magnetic field is generated in the stator coil 204. As a result, current flows to the stator coil 204. The current is supplied to the battery 400 of the vehicle via the motor control device 100.

< Structure of Motor control device >

As shown in fig. 1, the motor control device 100 includes a positive terminal 100a and a negative terminal 100b for electrical connection to a battery 400. The positive terminal 100a is connected to the positive electrode of the battery 400. The negative terminal 100b is connected to the negative electrode of the battery 400. The smoothing capacitor 100c is connected between the positive terminal 100a and the negative terminal 100b.

As shown in fig. 1, motor control device 100 includes stator inverter 30 and rotor inverter 50. The stator inverter 30 and the rotor inverter 50 are connected in parallel between the positive terminal 100a and the negative terminal 100b. Further, the motor control device 100 includes an integrated starter-generator ECU (ISGECU) 10 and a current sensor 70. The ISGECU 10 controls driving of the stator inverter 30 and the rotor inverter 50. The current sensor 70 detects currents flowing through the stator inverter 30 and the rotor inverter 50.

The ISGECU 10 is electrically connected to each of the stator inverter 30 and the rotor inverter 50. As described in detail below, the ISGECU 10 includes a microcomputer 11. The microcomputer 11 can communicate with a high-order ECU and an engine ECU mounted in the vehicle via a bus bar or the like. A request command from a higher-order ECU is input to the microcomputer 11. The microcomputer 11 generates control signals based on an input request command, detection signals from the current sensor 70 and a rotation angle sensor 12 described below, and the like to control the stator inverter 30 and the rotor inverter 50. The microcomputer 11 outputs control signals to a stator driver 17 and a rotor driver 18 described below. The stator driver 17 and the rotor driver 18 thereby output driving signals to the stator inverter 30 and the rotor inverter 50. As a result, the driving of the stator inverter 30 and the rotor inverter 50 is controlled.

The stator inverter 30 includes a U-phase leg 31, a V-phase leg 32, and a W-phase leg 33. The U-phase leg 31, V-phase leg 32, and W-phase leg 33 are connected in parallel between the positive terminal 100a and the negative terminal 100 b. The U-phase leg 31, V-phase leg 32, and W-phase leg 33 each have a high-side switching element and a low-side switching element. The high-side switch element and the low-side switch element are connected in series in order from the positive terminal 100a toward the negative terminal 100 b.

Specifically, the U-phase leg 31 has a U-phase high-side switching element 34 and a U-phase low-side switching element 35. The V-phase leg 32 has a V-phase high-side switching element 36 and a V-phase low-side switching element 37. The W-phase leg 33 has a W-high side switching element 38 and a W-phase low side switching element 39.

The switching elements constituting the stator inverter 30 are Metal Oxide Semiconductor Field Effect Transistors (MOSFETs). Thus, the switching elements each have a parasitic diode. That is, the U-phase high-side switching element 34 has a U-phase high-side diode 34a. The U-phase low-side switching element 35 has a U-phase low-side diode 35a. The V-phase high-side switching element 36 has a V-phase high-side diode 36a. The V-phase low-side switching element 37 has a V-phase low-side diode 37a. The W-phase high-side switching element 38 has a W-phase high-side diode 38a. The W-phase low-side switching element 39 has a W-phase low-side diode 39a. The cathode electrode of each parasitic diode is located on the positive terminal 100a side. The anode electrode is located on the negative terminal 100b side.

As shown in fig. 1, the U-phase stator coil 205, the V-phase stator coil 206, and the W-phase stator coil 207 are connected to each other at one end. As a result, the U-phase stator coil 205, the V-phase stator coil 206, and the W-phase stator coil 207 are connected together by star connection.

The other end of the U-phase stator coil 205 is connected to a center point between the U-phase high-side switching element 34 and the U-phase low-side switching element 35. The other end of the V-phase stator coil 206 is connected to a center point between the V-phase high-side switching element 36 and the V-phase low-side switching element 37. The other end of the W-phase stator coil 207 is connected to a center point between the W-phase high-side switching element 38 and the W-phase low-side switching element 39.

As a result of the above-described electrical connection configuration, for example, when the U-phase high-side switching element 34, the V-phase low-side switching element 37, and the W-phase low-side switching element 39 are in a closed state by a drive signal from the stator driver 17, current flows to the stator coil 204. Specifically, the current flows from the positive terminal 100a to the negative terminal 100b via the U-phase high-side switching element 34, the U-phase stator coil 205, the V-phase stator coil 206, and the V-phase low-side switching element 37. Current flows from the positive terminal 100a to the negative terminal 100b via the U-phase high-side switching element 34, the U-phase stator coil 205, the W-phase stator coil 207, and the W-phase low-side switching element 39.

According to the present embodiment, a modularized power MOSFET is used as a switching element constituting the stator inverter 30. Therefore, the rated currents of the switching element and the parasitic diode are high. The switching element and parasitic diode are designed to withstand even the current flowing during reverse connection of the battery 400. A so-called one-sided cooling system is used as a switching element constituting the stator inverter 30.

The rotor inverter 50 includes an E-phase leg 51 and an F-phase leg 52. The E-phase leg 51 and the F-phase leg 52 are connected in parallel between the positive terminal 100a and the negative terminal 100 b. The E-phase leg 51 has an E-phase high-side switching element 54 and an E-phase low-side switching element 55. The E-phase high-side switch element 54 and the E-phase low-side switch element 55 are connected in series in order from the positive terminal 100a toward the negative terminal 100 b. The F-phase leg 52 has an F-phase high-side switching element 56 and an F-phase low-side switching element 57. The F-phase high-side switch element 56 and the F-phase low-side switch element 57 are connected in series in this order from the positive terminal 100a toward the negative terminal 100 b. Four switching elements constitute a full bridge circuit.

The switching elements constituting the rotor inverter 50 are MOSFETs. Thus, the switching elements each have a parasitic diode. That is, the E-phase high-side switching element 54 has an E-phase high-side diode 54a. The E-phase low-side switching element 55 has an E-phase low-side diode 55a. The F-phase high-side switching element 56 has an F-phase high-side diode 56a. The F-phase low-side switching element 57 has an F-phase low-side diode 57a. The cathode electrode of each parasitic diode is located on the positive terminal 100a side. The anode electrode is located on the negative terminal 100b side.

The brush is connected to: a center point between the E-phase high-side switching element 54 and the E-phase low-side switching element 55; and a center point between the F-phase high-side switching element 56 and the F-phase low-side switching element 57. The brushes are in contact with the slip rings of the shaft. The slip ring is electrically connected to the rotor coil 203 by wiring.

As shown in fig. 1, a center point between the E-phase high-side switching element 54 and the E-phase low-side switching element 55 is electrically connected to one end of the rotor coil 203. A center point between the F-phase high-side switching element 56 and the F-phase low-side switching element 57 is electrically connected to the other end of the rotor coil 203.

As a result of the above-described connection configuration, for example, when the E-phase high-side switching element 54 and the F-phase low-side switching element 57 are in a closed state by a drive signal from the rotor driver 18, current flows from one end to the other end of the rotor coil 203. That is, the current flows from the positive terminal 100a to the negative terminal 100b via the E-phase high-side switching element 54, the rotor coil 203, and the F-phase low-side switching element 57.

In addition, for example, when the F-phase high-side switching element 56 and the E-phase low-side switching element 55 are in the closed state, current flows from the other end to one end of the rotor coil 203. That is, the current flows from the positive terminal 100a to the negative terminal 100b via the F-phase high-side switching element 56, the rotor coil 203, and the E-phase low-side switching element 55.

The current sensor 70 detects the amount of current flowing through the stator coil 204 and the rotor coil 203. More specifically, the current sensor 70 includes shunt resistors provided in the stator inverter 30 and the rotor inverter 50. Current sensor 70 includes a U-phase shunt resistor 71, a V-phase shunt resistor 72, a W-phase shunt resistor 73, an E-phase shunt resistor 74, and an F-phase shunt resistor 75.

The U-phase shunt resistor 71 is disposed between the U-phase low-side switch element 35 and the negative terminal 100 b. The V-phase shunt resistor 72 is disposed between the V-phase low-side switch element 37 and the negative terminal 100 b. The W-phase shunt resistor 73 is disposed between the W-phase low-side switching element 39 and the negative terminal 100 b. The E-phase shunt resistor 74 is disposed between the E-phase low-side switch element 55 and the negative terminal 100 b. The F-phase shunt resistor 75 is disposed between the F-phase low-side switching element 57 and the negative terminal 100 b.

The microcomputer 11 stores the resistance value of the shunt resistor. The amount of current flowing to each low-side switching element of each branch is detected based on the resistance value stored in the microcomputer 11 and the voltage across the shunt resistor. Thereby estimating the amount of current flowing through each of the stator coil 204 and the rotor coil 203. The current sensor 70 is not limited to the above example. For example, a configuration may be used in which the amount of current is detected based on a magnetic field generated by the flow of current.

< ISGECU overview >

As shown in fig. 1, the ISGECU 10 includes a microcomputer 11, a rotation angle sensor 12, an induced voltage detection unit 13, and a start judgment unit 14. The ISGECU 10 further includes a stator driver 17, a rotor driver 18, and a constant voltage circuit 19. A plurality of elements constituting the ISGECU 10 are mounted on a single wiring board. These constituent elements are electrically connected by wiring patterns formed on the wiring board.

The microcomputer 11 is supplied with power by a start signal input from the start judging unit 14. Thereby starting the microcomputer 11. More specifically, the start judging unit 14 inputs a start signal to the constant voltage circuit 19. As a result, the constant voltage circuit 19 enters a start-up state, and generates a voltage necessary for driving the microcomputer 11. For example, the constant voltage circuit 19 generates a voltage of 5 volts. The generated voltage is then supplied to the microcomputer 11. As a result, the microcomputer 11 is started. The microcomputer 11 includes a failure detection unit 15 and a driver control unit 16. The respective signals from the rotation angle sensor 12 and the induced voltage detection unit 13 are input to the failure detection unit 15. The respective signals from the rotation angle sensor 12 and the induced voltage detection unit 13 are input to the driver control unit 16.

The failure detection unit 15 diagnoses a failure in the rotation angle sensor 12 based on the respective signals from the rotation angle sensor 12 and the induced voltage detection unit 13. The failure detection unit 15 then outputs the failure diagnosis result concerning the rotation angle sensor 12 to the driver control unit 16.

The driver control unit 16 generates a control signal based on the failure diagnosis result regarding the rotation angle sensor 12 input from the failure detection unit 15, the output from the rotation angle sensor 12, a request command input from the higher-order ECU, and the like. The control signal is a pulse signal, and the pulse width of the control signal is determined based on the output required by the motor 200.

The control signals generated by the driver control unit 16 are input to the stator driver 17 and the rotor driver 18. The stator driver 17 and the rotor driver 18 each amplify the input control signal. After that, the stator driver 17 and the rotor driver 18 output the amplified control signals as driving signals to the stator inverter 30 and the rotor inverter 50, respectively. The driver control unit 16 corresponds to an energization control unit.

The starter motor is mounted in the vehicle. When the engine 300 is initially started by the starter motor, the driver control unit 16 is started by a start signal input from the start judging unit 14. In addition, when engine 300 is restarted by motor 200, an ignition signal has been input to ISGECU 10, and ISGECU 10 is already in a started state.

< details of ISGECU >

Details of the ISGECU will be described below. In the description, emphasis is placed on the start-up of the driver control unit 16. The start of the driver control unit 16 corresponds to the behavior of the ISGECU 10 when the engine 300 is started by the starter motor.

The rotation angle sensor 12 detects the rotation angle of the shaft provided with the rotor 201. That is, the rotation angle sensor 12 detects the rotation angle of the motor 200. As described above, the pulley is provided on the end of the shaft. The belt 310 is attached to the pulley. The permanent magnet 208 shown in fig. 1 is fixed to the end of the shaft on the opposite side from the end where the pulley is provided.

The rotation angle sensor 12 has a plurality of Hall elements disposed opposite to the permanent magnet 208. The magnetic field emitted from the permanent magnet 208 penetrates each of the plurality of hall elements. The angle of the magnetic field penetrating each hall element continuously changes as the shaft rotates. As a result, a hall voltage whose phase is changed based on the rotation of the shaft is output from each hall element. The hall elements are arranged to be separated in the rotation direction of the shaft so that phases of the output hall voltages are different.

The rotation angle sensor 12 includes a counter. The count number of the counter is increased based on the phase change of the hall voltage from each hall element. The counted number is input to the driver control unit 16 and the failure detection unit 15. The counted number is cleared when the shaft makes a single rotation at a mechanical angle.

As described above, the shaft and crankshaft are capable of rotating with respect to the belt 310. The belt 310 is arranged on a pulley arranged on the shaft. The belt 310 is provided on a pulley of a crankshaft (crankshaft pulley). When the diameters of the two pulleys are the same, the number of revolutions of the crankshaft is the same as the number of revolutions of the shaft. Therefore, the number of revolutions of engine 300 is the same as that of motor 200. However, the diameters of the pulleys are typically different. Therefore, the number of rotations detected by the rotation angle sensor 12 is not equal to the number of rotations of the engine 300. The ratio of the number of revolutions detected by the rotation angle sensor 12 to the number of revolutions of the engine 300 is determined by the diameter ratio of the pulleys (pulley ratio).

The induced voltage detection unit 13 detects an induced electromotive force (induced voltage) from the rotor 201 generated by a change over time of a magnetic field penetrating the stator coil 204. The induced voltage detection unit 13 according to the present embodiment detects the respective induced voltages induced in the U-phase stator coil 205 and the V-phase stator coil 206. After that, the induced voltage detection unit 13 detects a voltage difference (line voltage) between the stator coils of the two phases.

Due to the rotation of the shaft, the line voltage varies in a sine wave manner. For example, when the rotor coil 203 has eight pole pairs, the line voltage generates a sine wave corresponding to eight cycles when the shaft rotates 360 degrees of the mechanical angle. Thus, when the shaft is rotated by 45 degrees of mechanical degrees, the line voltage generates a sine wave corresponding to a single cycle. In this way, a 360 degree electrical angle corresponds to a 45 degree mechanical angle. The sine wave line voltage is input to each of the fault detection unit 15 and the start judgment unit 14.

As described above, a part of the rotor coil 203 and a fixing portion that fixes the rotor coil 203 to the shaft are magnetized. Therefore, although weak, even when the rotor coil 203 is not energized, a magnetic field is output from the rotor 201. When engine 300 is started, rotor 201 emitting the weak magnetic field is rotated by the common rotation of the crankshaft. As a result, the change in the weak magnetic field across the stator coil 204 over time occurs more rapidly. The voltage level of the induced voltage generated in the stator coil 204 increases. The induced voltage detection unit 13 detects a change in the voltage level of the induced voltage.

The start determination unit 14 determines whether the engine 300 has been started and is in a driven state based on the behavior of the line voltage input from the induced voltage detection unit 13 over time. When it is determined that the engine 300 has started and is rotating at a rotational speed (engine speed) equal to or greater than the idling period, the start determination unit 14 outputs a high-level start signal to the driver control unit 16 based on the behavior of the line voltage over time. In contrast, when it is determined that the engine 300 is stopped, the start determination unit 14 outputs a low-level start signal to the driver control unit 16. The start judging unit 14 will be described in detail below.

The fault detection unit 15 compares the line voltage input from the induced voltage detection unit 13 with a stored fault determination threshold. The failure determination threshold value is a fixed value. As described above, when the number of magnetic pole pairs of the rotor coil 203 is eight pairs, the line voltage generates a sine wave corresponding to eight cycles when the shaft rotates by 360 degrees of the mechanical angle. Thus, when the shaft rotates 360 degrees of mechanical degrees, the line voltage exceeds the failure determination threshold eight times. In addition, the phase difference between the timings at which the line voltage exceeds the failure determination threshold value is a mechanical angle of 45 degrees. In other words, the phase difference between the timings at which the line voltage exceeds the failure determination threshold value is 360 degrees in electrical angle.

When the line voltage exceeds the failure determination threshold value, the failure detection unit 15 continuously acquires the count number detected by the rotation angle sensor 12. Thereafter, the failure detection unit 15 determines the difference in the number of counts acquired successively. The failure detection unit 15 determines whether the calculated difference is equal to a 45-degree mechanical angle. When the judgment difference is equal to 45 mechanical angles, the failure detection unit 15 judges that the rotation angle sensor 12 is normal. In contrast, when the determination difference does not indicate 45 the mechanical angle, the failure detection unit 15 determines that the rotation angle sensor 12 is abnormal.

The failure detection unit 15 outputs a diagnostic signal indicating whether there is an abnormality in the rotation angle sensor 12 to the driver control unit 16. For example, when the rotation angle sensor 12 is normal, the diagnostic signal is set to a low level signal, and when the rotation angle sensor 12 is abnormal, the diagnostic signal is set to a high level signal.

When a high-level start signal is input from the start judging unit 14, the driver control unit 16 is started. At the time of start-up, the driver control unit 16 starts transmitting and receiving information necessary for vehicle control with the in-vehicle ECU such as the higher-order ECU. In addition, the driver control unit 16 determines whether the diagnostic signal input from the failure detection unit 15 is a high level diagnostic signal.

When the diagnostic signal is judged to be a low-level diagnostic signal, the driver control unit 16 generates a control signal based on a detection signal from the rotation angle sensor 12, a request command input from the higher-order ECU, and the like. In contrast, when the diagnosis signal is judged to be a high-level diagnosis signal, the driver control unit 16 stops the output of the respective control signals of the stator driver 17 and the rotor driver 18.

Alternatively, the driver control unit 16 stops outputting the control signal to the stator driver 17 and continues outputting the control signal to the rotor driver 18. When the battery 400 is charged by the induced electromotive force generated in the stator coil 204, output of a control signal to the rotor driver 18 is performed. The induced electromotive force generated in the stator coil 204 is supplied to the battery 400 via a parasitic diode constituting a switching element of the stator inverter 30.

The stator driver 17 and the rotor driver 18 each include an amplifier circuit. The stator driver 17 and the rotor driver 18 each amplify the input control signal, and output the amplified control signal (drive signal) to the gate of the switching element of each inverter. As a result, the driving of each inverter is controlled.

< Structure of Start determination means >

Next, the start determination unit 14 will be described in detail with reference to fig. 2. Fig. 2 also shows an induced voltage detection unit 13.

As shown in fig. 2, the induced voltage detection unit 13 includes an amplifier 80 and a filter 81. The amplifier 80 has two input terminals and a single output terminal. One of the two input terminals is electrically connected to the U-phase stator coil 205 through an input wiring. The other of the two input terminals is electrically connected to the V-phase stator coil 206 through an input wiring. As a result, the induced voltage ULD induced in the U-phase stator coil 205 is input to one of the two input terminals. In addition, an induced voltage ULD induced in the V-phase stator coil 206 is input to the other of the two input terminals.

The filter 81 is provided in the two sets of input wirings. That is, the filter 81 includes: a first resistor 81a provided in one of the two sets of input wirings; and a second resistor 81b provided in the other group. The filter 81 further includes a capacitor 81c connected between the two sets of input wirings. As a result, the filter 81 constitutes a low-pass filter.

The cut-off frequency of the filter 81 is determined based on the maximum rotation speed of the engine 300 (maximum engine rotation speed). More specifically, the cut-off frequency of the filter 81 is determined based on the maximum rotational speed of the motor 200, which is based on the maximum rotational speed of the engine 300 and the pulley ratio. Therefore, the filter 81 removes noise waves having a frequency higher than the frequency based on the maximum rotation speed of the motor 200. Hereinafter, noise waves having a frequency higher than the frequency corresponding to the maximum rotation speed of the motor 200 will be simply referred to as high-frequency noise waves.

As a result of the above-described connection configuration, the induced voltage ULD of the U-phase stator coil 205 and the induced voltage VLD of the V-phase stator coil 206 are each input to the amplifier 80 via the filter 81. The amplifier 80 amplifies the difference between the induced voltage ULD of the U-phase stator coil 205 and the induced voltage VLD of the V-phase stator coil 206, wherein the high frequency noise wave has been removed by the filter 81. After that, the amplifier 80 outputs the amplified induced voltage difference as a line voltage to the respective start judging unit 14 and the failure detecting unit 15.

The start judging unit 14 includes a comparator 82, a first trigger 83, a second trigger 84, and a timer 85. The output terminal of the amplifier 80 is connected to the non-inverting input terminal of the comparator 82. The reference potential 82a is connected to an inverting input terminal of the comparator 82. The output terminal of the comparator 82 is connected to the respective clock terminals of the first flip-flop 83 and the second flip-flop 84.

In addition, the delay terminal of the first flip-flop 83 is connected to a power supply. The output terminal of the first flip-flop 83 is connected to the delay terminal of the second flip-flop 84. An output terminal of the second flip-flop 84 is connected to the driver control unit 16. The signal output from the output terminal of the second flip-flop 84 corresponds to the start signal.

The output terminal of the timer 85 is connected to the respective reset terminals of the first flip-flop 83 and the second flip-flop 84. An output terminal of the comparator 82 shown in fig. 2 is connected to a timer 85. However, the output terminal of the comparator 82 may not be directly connected to the timer 85. The comparator 82 and the timer 85 are shown connected to each other in fig. 2 to clearly show that the timer 85 operates based on the output from the comparator 82. For example, the following configuration may also be used: since the respective delay terminals of the first flip-flop 83 and the second flip-flop 84 are connected to the timer 85, the output terminal of the comparator 82 is indirectly connected to the timer 85.

The comparator 82 according to the present embodiment is a hysteresis comparator. Thus, the comparator 82 has two thresholds. Specifically, the comparator 82 has a first threshold Vth and a second threshold Vt1. The voltage level of the second threshold Vtl is lower than the voltage level of the first threshold Vth. The first threshold Vth and the second threshold Vtl are set based on the output voltage of the reference potential 82 a. The first threshold Vth and the second threshold Vt1 correspond to judgment thresholds.

The comparator 82 compares the input line voltage with a first threshold Vth. When the line voltage is judged to be lower than the first threshold Vth, the comparator 82 outputs a low-level signal. When the line voltage is judged to exceed the first threshold Vth, the comparator 82 outputs a high level signal. Subsequently, even when the line voltage falls below the first threshold Vth, the comparator 82 outputs a high-level signal. However, when the line voltage drops below the second threshold Vt1, the comparator 82 outputs a low level signal. As a result, the fluctuation of the output of the comparator 82 due to noise or the like is suppressed.

As described above, the line voltage exhibits a sinusoidal behavior. Therefore, when the line voltage is higher than the first threshold Vth, the comparator 82 outputs a high level signal. Subsequently, the line voltage exhibits a behavior in which the line voltage drops below the second threshold Vt 1. At this time, the comparator 82 outputs a low level signal. The comparator 82 repeats this operation based on the phase change of the line voltage. As a result, the comparator 82 continuously outputs a pulse signal based on the phase change of the line voltage.

The pulse signals are input to the respective clock terminals of the first flip-flop 83 and the second flip-flop 84. The timing at which the pulse in the pulse signal output from the comparator 82 changes from low to high corresponds to the rise time. The moment at which the pulse changes from high to low corresponds to the fall time.

The first flip-flop 83 and the second flip-flop 84 are both positive edge-triggered D flip-flops. Accordingly, when the signal input to the clock terminal changes from low to high, the first flip-flop 83 and the second flip-flop 84 each output the signal input to the delay terminal. In addition, in each of the first flip-flop 83 and the second flip-flop 84, when a high level reset signal is input to the reset terminal, the output is forcibly set to a low level. The outputs of the respective first flip-flop 83 and second flip-flop 84 in the reset state are low.

As described above, the delay terminal of the first flip-flop 83 is connected to the power supply. Therefore, the delay terminal of the first flip-flop 83 is fixed to a high level. Therefore, when the output of the comparator 82 changes from low to high due to the line voltage exceeding the first threshold Vth, the output from the first flip-flop 83 changes from low to high. The high level output is input to the delay terminal of the second flip-flop 84.

The output of the comparator 82 is input from low to high to the respective clock terminals of the first flip-flop 83 and the second flip-flop 84 at the same time. The output of the first flip-flop 83 then goes from low to high. However, the change in output may be delayed. Therefore, when a change from low to high of the output of the comparator 82 is input to the clock terminal of the second flip-flop 84, the output of the first flip-flop 83 is kept low. Thus, the output of the second flip-flop 84 remains unchanged at the low level. In this way, if the output of the comparator 82 changes from low to high only once, the output of the second flip-flop 84 remains low.

However, when the output of the comparator 82 changes from low to high again, the output of the second flip-flop 84 changes from low to high because the output of the first flip-flop 83 is already high. The high-level start signal is input to the driver control unit 16. As a result, the driver control unit 16 enters the start state.

As described above, when the output of the comparator 82 changes from low to high twice, the high-level start signal is output to the driver control unit 16. Here, as described above, the filter 81 removes high-frequency noise having a frequency higher than the frequency based on the maximum rotation speed of the motor 200. However, noise waves (low-frequency noise waves) having a frequency lower than the frequency based on the maximum rotation speed of the motor 200 are not removed. Thus, as a result of the low frequency noise wave, the signal input to the clock terminal of each flip-flop can be changed from low to high twice. Therefore, even if the engine 300 is not actually started, a high-level start signal may be output to the driver control unit 16.

In view of this, the timer 85 is connected to the respective reset terminals of the first flip-flop 83 and the second flip-flop 84. The timer 85 includes a capacitor, a logic circuit, and a switching element. The output of the timer 85 varies based on the amount of power stored in the capacitor. When the amount of power stored in the capacitor is greater than the capacity threshold Cth, the output of the timer 85 is low. However, when the amount of electric power storage in the capacitor falls below the capacity threshold Cth, the output of the timer 85 becomes high. In other words, when the voltage of the electrode of the capacitor related to the amount of electric power storage in the capacitor is greater than the voltage threshold Vth related to the capacitor threshold Cth, the output of the timer 85 is low. However, when the electrode voltage of the capacitor drops below the voltage threshold Vth, the output of the timer 85 becomes high.

The output of the timer 85 is input to the respective reset terminals of the first flip-flop 83 and the second flip-flop 84. When a high level signal is input from the timer 85 to the reset terminal, the first flip-flop 83 and the second flip-flop 84 are reset. As a result, the respective outputs of the first flip-flop 83 and the second flip-flop 84 are low.

The timer 85 includes a logic circuit and a switching element. The output from the logic circuit is input to the control electrode of the switching element. When the respective outputs of the first flip-flop 83 and the second flip-flop 84 are low level, the logic circuit outputs a low level signal. As a result, the switching element enters an off state. In this case, the power storage amount in the capacitor is unchanged.

However, when the output of the first flip-flop 83 becomes high and the output of the second flip-flop 84 becomes low due to the output of the comparator changing from low to high, the logic circuit outputs a high level signal. As a result, the switching element enters a closed state. The amount of power stored in the capacitor begins to decrease.

When the output of the comparator 82 changes from low to high again before the amount of power stored in the capacitor falls below the capacity threshold Cth, the respective outputs of the first flip-flop 83 and the second flip-flop 84 become high. In this case, the logic circuit outputs a low level signal. As a result, the switching element enters an off state. The amount of power stored in the capacitor begins to increase. In addition, the resetting of the first flip-flop 83 and the second flip-flop 84 is avoided. In this case, the output of the second flip-flop 84 becomes high. As a result, the driver control unit 16 is in the activated state.

As described above, the delay terminal of the first flip-flop 83 is fixed at the high level. Therefore, even if the output of the comparator 82 changes from low to high after the respective outputs of the first flip-flop 83 and the second flip-flop 84 change to high, the respective outputs of the first flip-flop 83 and the second flip-flop remain unchanged at the high level. As a result, the switching element is fixed in the off state. The amount of power stored in the capacitor is fixed. The output of the calculator 85 is fixed at a low level. As a result, the first flip-flop 83 and the second flip-flop 84 will not be reset. As a result, the start signal is fixed at the high level.

The determination discharge time from the full charge state to the capacity threshold Cth is determined based on the minimum rotational speed of the engine 300 (minimum engine rotational speed). More specifically, the determination of the discharge time is determined based on the minimum rotational speed of motor 200, which is based on the minimum rotational speed of engine 300 and the pulley ratio. Further more specifically, the determination of the discharge time is determined based on the amount of time required for the line voltage to change by 45 degrees mechanical angle (360 electrical degrees) when the motor 200 rotates at the minimum rotational speed.

In this way, the determination discharge time is the amount of time that the output of the comparator 82 changes from low to high twice when the engine 300 autonomously rotates at the minimum rotational speed. It goes without saying that the judgment discharge time may be set slightly longer than the amount of time for which the output of the comparator 82 changes from low to high twice when the engine 300 autonomously rotates at the minimum rotation speed, in consideration of the signal transmission delay and the like. The discharge time is determined to correspond to a time threshold.

During the judgment discharge time as described above, a noise wave that changes the signal input to the clock terminal of each flip-flop from low to high is unlikely to be input twice. In addition, as described above, after the judgment of the discharge time has elapsed, both the first flip-flop 83 and the second flip-flop 84 are reset. Therefore, even if noise is input twice with a time amount equal to or longer than the judgment discharge time therebetween, a high-level start signal is not input to the driver control unit 16. Thus, the driver control unit 16 constructs Cheng Kangzao waves.

< Signal of Start determination means >

Next, signals of the start-up determination unit will be described with reference to fig. 3. Fig. 3 shows the engine 300 when it is started by the starter motor.

At time t0, the rotational speed of engine 300 increases due to cranking. The shaft of the motor 200 rotates by being rotated together by the rotation of the engine 300. At this time, the driver control unit 16 is in a ready state. Therefore, the rotor coil 203 is not energized. As a result, the magnetic field generated by the energization is not outputted from the rotor coil 203.

However, as described above, although weak, a magnetic field is output from the magnetized portion of the rotor 201. Thus, when the shaft is rotated by the co-rotation of the motor 300, the weak magnetic field penetrating the stator coil 204 varies with time. Therefore, although weak, an induced electromotive force is generated in the stator coil 204. Therefore, at time t0, the generated line voltage is also limited. As a result, the output from the amplifier 80 is also limited.

However, the output of amplifier 80 is below the threshold of comparator 82. Thus, the output of comparator 82 is low. The signals input to the respective clock terminals of the first flip-flop 83 and the second flip-flop 84 are also low. At time t0, both the first flip-flop 83 and the second flip-flop 84 are in the reset state. Accordingly, the respective outputs of the first flip-flop 83 and the second flip-flop 84 are low. The amount of power storage in the capacitor provided in the timer 85 is also in a fully charged state and unchanged. In fig. 3, Q1 represents the output of the first flip-flop 83. Q2 represents the output of the second flip-flop 84.

As a period of time elapses from time t0, the engine speed increases. As a result, the rotation of the shaft becomes faster. The change in magnetic field of the rotor coil 203 penetrating the stator coil 204 occurs more rapidly with time. As a result, the induced electromotive force increases. Thereby, the output of the amplifier 80 increases.

After time t0, when time t1 is reached, the output of amplifier 80 exceeds the first threshold Vth of comparator 82. Thus, the output of comparator 82 changes from low to high. As a result, the output of the first flip-flop 83 changes from low to high. In addition, the amount of power storage in the capacitor provided in the timer 85 starts to decrease. The timer in fig. 3 indicates the change in the amount of power stored in the capacitor over time.

When time t2 is reached from time t1, the output of amplifier 80 drops below the second threshold Vt1. Thus, the output of comparator 82 changes from high to low.

When time t3 is reached from time t2, the output of amplifier 80 again exceeds the first threshold Vth. Thus, the output of comparator 82 changes from low to high. As a result, the output of the second flip-flop 84 changes from low to high. In addition, the amount of electric power storage in the capacitor provided in the timer 85 stops decreasing and starts increasing again. In this way, the high-level start signal is output from the second flip-flop 84 before the amount of electric power storage in the capacitor falls below the capacity threshold Cth.

As shown in fig. 4, when a noise wave is input from the amplifier 80 to the comparator 82, the output of the amplifier 80 exceeds the first threshold Vth of the comparator 82 at time t 4. As a result, the output of the first flip-flop 83 changes from low to high. In addition, the amount of power storage in the capacitor provided in the timer 85 starts to decrease.

When time t5 is reached, the output of amplifier 80 drops below the second threshold Vt1. Thus, the output of comparator 82 changes from high to low.

However, after time t5, the line voltage does not change. Therefore, the output of the amplifier 80 does not change. Therefore, the output of the comparator 82 does not change. The signal input to the clock terminal of each flip-flop does not change. As a result, the amount of power stored in the capacitor continues to decrease.

When the judgment discharge time passes from time t5 to time t6, the electric power storage amount in the capacitor provided in the timer 85 falls below the capacity threshold Cth. Thus, the output of the timer 85 changes from low to high. As a result, both the first flip-flop 83 and the second flip-flop 84 are reset. The output of the first flip-flop 83 is again low. Thus, the output of the second flip-flop 84 remains unchanged at the high level. The activation of the driver control unit 16 due to noise waves is prevented.

< working Effect >

Next, the operational effects of the motor control device 100 according to the present embodiment will be described. As described above, the start-up judging unit 14 judges whether to start up the driver control unit 16 based on the change over time of the line voltage related to the threshold value. More specifically, the start judging unit 14 judges whether to start the driver control unit 16 based on whether the line voltage detected by the induced voltage detecting unit 13 exceeds the threshold of the comparator 82 twice during a judgment discharge time based on the minimum rotation speed of the motor 200.

As described above, the magnetic field output from the non-energized rotor 201 is weak. Therefore, the voltage level of the line voltage detected by the induced voltage detecting unit 13 is also low. Therefore, as a result of the above-described configuration, erroneous determination of the driver control unit 16 based on noise waves or the like is suppressed as compared with a configuration in which the driver control unit is simply determined to be started based on whether or not the line voltage exceeds the threshold of the comparator. The robustness of the judgment about the driving of the driver control unit 16 is improved. As a result, the energization of the rotor coil 203 due to erroneous determination is suppressed. An increase in power consumption is suppressed.

The filter 81 removes high-frequency noise waves having a frequency higher than the frequency based on the maximum rotation speed of the motor 200. As described above, the shaft provided in the rotor 201 is rotated by the common rotation of the engine 300. Accordingly, a periodic variation in the line voltage is expected to occur based on the rotational speed of the motor 200. Therefore, it can be determined that the change in the line voltage at a frequency higher than the frequency based on the maximum rotation speed of the motor 200 is due to the noise wave. The filter 81 removes a change in line voltage (induced voltage) that is independent of the rotation of the motor 200. As a result, erroneous judgment concerning driving by the driver control unit 16 is suppressed.

(first modification)

According to the present embodiment, an example of a flip-flop in which both the first flip-flop 83 and the second flip-flop 84 are positive edge triggered is described. However, as shown in fig. 5, a negative edge triggered flip-flop may also be used as each of the first flip-flop 83 and the second flip-flop 84. In this case, the output level changes from high to low when a signal is input to the clock terminal of each flip-flop.

(second embodiment)

Next, a second embodiment will be described with reference to fig. 6 and 7. The motor control device according to the following embodiment shares a commonality with the motor control device 100 according to the first embodiment. Therefore, description of the common portions is omitted hereinafter. The differences will be mainly described. Elements identical to those according to the first embodiment are given the same reference numerals hereinafter.

According to the first embodiment, an example of a flip-flop in which both the first flip-flop 83 and the second flip-flop 84 are positive edge triggered is described. In view of this, according to the present embodiment, as shown in fig. 6, the configuration is such that the first flip-flop 83 is a negative edge-triggered flip-flop and the second flip-flop 84 is a positive edge-triggered flip-flop. In this configuration, the determination regarding the driving of the driver control unit 16 may be performed within the amount of time obtained by subtracting the pulse width from the pulse period.

In this configuration, a constituent element equivalent to that according to the first embodiment is also provided. Therefore, a similar working effect to that according to the first embodiment can be achieved.

(second modification)

According to the present embodiment, an example is described in which the first flip-flop 83 is a negative edge-triggered flip-flop and the second flip-flop 84 is a positive edge-triggered flip-flop. However, as shown in fig. 8, a configuration in which the first flip-flop 83 is a positive edge-triggered t-flip-flop and the second flip-flop 84 is a negative edge-triggered flip-flop may also be used.

(third embodiment)

Next, a third embodiment will be described with reference to fig. 9 and 10.

According to the first and second embodiments, an example in which the start judging unit 14 includes two triggers is described. However, the number of flip-flops is not limited to the number in this example. Any number of triggers may be used as appropriate as long as more than two triggers are used.

According to the present embodiment, as shown in fig. 9, a third trigger, that is, a third trigger 86 is provided in addition to the first trigger 83 and the second trigger 84. The connection configuration of the three triggers is similar to the configuration according to the above embodiment. The output of the logic circuit input to the timer 85 is the output of two flip-flops positioned on the ends of three flip-flops connected in series. That is, the outputs of the logic circuits input to the timer 85 are the outputs of the first flip-flop 83 and the third flip-flop 86.

However, the first flip-flop 83 is a positive edge-triggered flip-flop, the second flip-flop 84 is a negative edge-triggered flip-flop, and the third flip-flop 86 is a positive edge-triggered flip-flop.

As a result, as shown in fig. 10, the determination regarding the start of the driver control unit 16 can be performed based on whether or not the output of the comparator 82 continuously changes from low to high, from high to low, and from low to high during the determination discharge time. As a result of this configuration, the same operational effects as those according to the first embodiment can also be achieved.

(third modification)

According to the present embodiment, an example is described in which the first flip-flop 83 is a positive edge-triggered flip-flop, the second flip-flop 84 is a negative edge-triggered flip-flop, and the third flip-flop 86 is a positive edge-triggered flip-flop. However, as shown in fig. 11, a configuration may be used in which the first flip-flop 83 is a negative edge-triggered flip-flop, the second flip-flop 84 is a positive edge-triggered flip-flop, and the third flip-flop 86 is a negative edge-triggered flip-flop.

(fourth modification)

In yet another example, as shown in FIG. 12, for example, a configuration may be used in which all three or more triggers are positive edge-triggered triggers. Furthermore, in a similar manner, a configuration (not shown) in which all three or more flip-flops are negative edge-triggered may also be used.

With this configuration, as shown in fig. 13, the determination regarding the start of the driver control unit 16 is performed based on the amount of time between the rising edge of a single pulse in the pulse signal output from the comparator 82 due to the autonomous rotation of the engine 300 and the rising edge of the pulse that is two pulses after the single pulse. The determination regarding the start of the driver control unit 16 is performed based on whether or not three pulses are output during the determination discharge time.

In this case, the amount of time required for the judgment is expected to be approximately twice that of the configuration according to the first and second embodiments. Therefore, the amount of time twice the judgment discharge time according to the first and second embodiments can be set as the judgment discharge time in the present modification. This design can be suitably implemented by decreasing the capacity threshold Cth, increasing the capacity of the capacitor provided in the timer 85, and the like.

As described in accordance with the above-described embodiment and modification, the judgment about the start-up of the driver control unit 16 may be performed based on the behavior of the pulse signal output from the comparator 82 over time.

The preferred embodiments of the present disclosure have been described above. However, the present disclosure is not limited to the above-described embodiments. Various modifications may be made without departing from the spirit of the disclosure.

(fifth modification)

According to the above embodiment, an example in which the induced voltage detection unit 13 includes the filter 81 is described. However, for example, as shown in fig. 14 for simplicity, the start judging unit 14 may include a filter 81. In this case, the filter 81 may be interposed between the amplifier 80 and the comparator 82. That is, the filter 81 may be provided at a non-inverting input terminal of the comparator 82. In addition, the filter 81 may be provided at an output terminal of the comparator 82. All that is required is to provide a filter 81 in at least any one of the induced voltage detection unit 13 and the start-up determination unit 14.

(sixth modification)

According to the above embodiment, an example of the voltage of the output line of the induced voltage detection unit 13 is described. However, a configuration may be used in which the induced voltage detection unit 13 detects an induced voltage induced in one of the three-phase stator coils and outputs the detected induced voltage.

(other modifications)

According to the above embodiment, an example in which the motor 200 is connected to the crankshaft of the engine 300 mounted in the vehicle through the strap 310 is described. However, a configuration in which the motor 200 is connected to the crankshaft through a power transmission mechanism may also be used.

According to the above embodiment, an example in which the rotor inverter 50 constitutes a full-bridge circuit is described. However, the rotor inverter 50 may constitute a half-bridge circuit.

According to the above-described embodiment, an example in which the switching elements constituting the stator inverter 30 and the rotor inverter 50 are MOSFETs is described. However, the switching elements constituting the stator inverter 30 and the rotor inverter 50 are not limited to the above examples. For example, an Insulated Gate Bipolar Transistor (IGBT) may be used. In this case, an additional reflux diode is connected antiparallel to the switching element.

According to the above-described embodiment, an example in which a single-sided cooling system is used in the switching elements constituting the stator inverter 30 is described. However, the system for cooling the switching elements constituting the stator inverter 30 is not limited to the above example. For example, a double sided cooling system may be used. In addition, a cooling system using a fluid coolant may also be used.

According to the above-described embodiment, the materials for forming the stator inverter 30 and the rotor inverter 50 are not specifically mentioned. However, for example, silicon may be used as the formation material. In addition, for example, silicon carbide having a wider band gap than silicon may be used as another forming material.

In addition, the formation materials of the rotor inverter 50 and the stator inverter 30 may be different. For example, the rotor inverter 50 may include silicon carbide, and the stator inverter 30 may include silicon.

Claims (7)

1. A control apparatus for a rotating electrical machine including a rotor rotatably connected to an engine and a stator provided around the rotor, the control apparatus comprising:

an induced voltage detection unit that detects an induced voltage induced in a stator coil provided in the stator;

an energization control unit that controls energization of a field winding provided in the rotor; and

and a start judgment unit that judges start of the energization control unit based on an amount of time between at least two times of a plurality of rising times, which are times when the induced voltage detected by the induced voltage detection unit exceeds a first judgment threshold, and a plurality of falling times, which are times when the induced voltage falls below a second judgment threshold.

2. The control device of claim 1, wherein,

at least either one of the induced voltage detection unit and the start determination unit includes a filter that removes high-frequency noise waves having a frequency higher than a frequency corresponding to a maximum rotational speed of the engine.

3. The control device according to claim 1 or 2, wherein,

the start judgment unit outputs a drive signal to the energization control unit when either one of an amount of time between two rising times and an amount of time between two falling times is equal to or smaller than a time threshold based on a minimum rotational speed of the engine autonomous rotation, wherein between two rising times the induced voltage exceeds the judgment threshold and then exceeds the judgment threshold again; between two fall times, the induced voltage falls below the determination threshold and then falls below the determination threshold again.

4. The control device according to claim 1 or 2, wherein,

when any one of the amount of time between the rising time and the falling time and the amount of time between the falling time and the rising time is equal to or smaller than a time threshold value based on a minimum rotational speed at which the engine autonomously rotates, the start-up judging unit outputs a drive signal to the energization control unit, wherein between the rising time and the falling time, the induced voltage exceeds the judgment threshold value and then falls below the judgment threshold value; between a falling time and a rising time, the induced voltage falls below the judgment threshold and then exceeds the judgment threshold.

5. The control device according to claim 1 or 2, wherein,

the start judgment unit outputs a drive signal to the energization control unit when either one of an amount of time between two rising times and an amount of time between two falling times is equal to or smaller than a time threshold based on a minimum rotational speed of the engine autonomous rotation, wherein between the two rising times, the induced voltage exceeds the judgment threshold and then exceeds the judgment threshold again after falling below the judgment threshold; between two falling times, the induced voltage falls below the judgment threshold, and then falls below the judgment threshold again after exceeding the judgment threshold.

6. A rotating electrical machine, comprising:

a rotor rotatably connected to the motor, the rotor including a magnetic field winding;

a stator disposed around the rotor, the stator including a stator coil; and

a control device, wherein the control device comprises:

an induced voltage detection unit that detects an induced voltage induced in the stator coil;

An energization control unit that controls energization of the field winding; and

and a start-up judging unit that judges start-up of the energization control unit based on an amount of time between at least two of a plurality of rising times at which the induced voltage detected by the induced voltage detecting unit exceeds a first judgment threshold and a plurality of falling times at which the induced voltage falls below a second judgment threshold.

7. A control method for a rotary electric machine including a rotor rotatably connected to an engine and a stator provided around the rotor, the control method comprising:

detecting an induced voltage induced in the stator coil, the stator coil being disposed in the stator;

controlling energization of a field winding disposed in the rotor; and

the method includes determining a start of energization of the field winding based on an amount of time between at least two of a plurality of rise times at which a detected induced voltage exceeds a first determination threshold and a plurality of fall times at which the induced voltage falls below a second determination threshold.