CN109728756B - Double-reference-voltage single-vector open winding permanent magnet motor prediction control method and equipment - Google Patents
Double-reference-voltage single-vector open winding permanent magnet motor prediction control method and equipment Download PDFInfo
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Abstract
The invention discloses a double-reference-voltage-based single-vector open winding permanent magnet motor prediction control method and equipment. The method comprises the steps of firstly calculating a reference voltage vector of a motor through a current dead beat principle, determining a voltage vector of a first inverter according to the position of the reference voltage vector, then obtaining a reference voltage vector of a second inverter through the relation between the voltage of the inverter and the voltage of the motor, and determining a candidate vector range of the second inverter according to the position of the reference voltage vector of the second inverter. Finally, a voltage vector of the second inverter is determined. And finally, outputting the voltage vector of the first inverter and the voltage vector of the second inverter. Compared with the traditional open winding permanent magnet motor model prediction control method, the method reduces the calculation burden brought by a vector enumeration method. The timeliness is stronger, and the test cost is reduced.
Description
Technical Field
The invention relates to the field of motor control, in particular to a double-reference-voltage-based single-vector open winding permanent magnet motor prediction control method and device.
Background
Bilateral controllable open winding permanent magnet synchronous generator systems (OW-PMSG) are receiving more and more attention because of their good fault tolerance, flexible control modes and multilevel modulation effect. However, the common dc bus topology provides a zero sequence current path, so that zero sequence current exists in the system. Zero sequence current can increase system loss and increase torque ripple, reduces the efficiency of whole system. Therefore, to eliminate the zero sequence current as much as possible, it is necessary to directly suppress the zero sequence current.
In the traditional vector control method, the PI controller parameters are adjusted more and complexly, and the model prediction method can omit a zero sequence current loop and avoid complex parameter adjustment. In general, the current prediction is to predict the current at the next moment through a mathematical model by using the current value. For a two-level inverter, there are eight switching states corresponding to eight voltage vectors, including six non-zero voltage vectors and two zero voltage vectors. Therefore, the double inverter has 8 × 8 switching state combinations of 64 kinds, and has the same voltage vector distribution as the three-level inverter. Since some of the combinations form the same voltage vector, the dual inverter has 19 different voltage vectors, 18 non-zero vectors and 1 zero vector. If the optimal vector is selected from the 19 voltage vectors by an enumeration method, the calculation amount of the whole control algorithm in practical application is increased.
Disclosure of Invention
In view of the foregoing deficiencies in conventional open-winding permanent magnet motor model prediction. The invention aims to provide a double-reference-voltage-based single-vector open winding permanent magnet motor prediction control method and equipment. Therefore, the calculation data amount is reduced, the parameter adjustment complexity of the PI controller is reduced, and the test control difficulty is reduced.
Based on the above purpose, the invention provides a double-reference-voltage-based single-vector open winding permanent magnet motor prediction control method, which comprises the following steps:
calculating a motor reference voltage vector on a synchronous rotating coordinate system according to a current dead beat control principle;
calculating an angle of the motor reference voltage vector according to the motor reference voltage vector so as to obtain a position of the motor reference voltage vector, and determining a voltage vector of a first inverter according to the position of the motor reference voltage vector;
calculating a reference voltage vector of a second inverter according to the voltage vector of the first inverter and the motor reference voltage vector;
determining the range and the quantity of candidate voltage vectors of a second inverter according to the positions of the reference voltage vectors of the second inverter in a vector hexagon formed by all vectors of the second inverter;
selecting a voltage vector of the second inverter from the candidate voltage vector range of the second inverter;
inputting the voltage vector of the first inverter and the voltage vector of the second inverter to the first inverter and the second inverter, respectively.
The equation of the motor reference voltage vector of the d-axis, the q-axis and the 0-axis on the synchronous rotating coordinate system is as follows:
wherein u isdref,uqrefAnd u0refRespectively representing reference voltage vectors of the motor on a d axis, a q axis and a 0 axis on a synchronous rotating coordinate system; i.e. id,iqAnd i0Respectively representing current components of the motor on a d axis, a q axis and a 0 axis on a synchronous rotation coordinate system; i.e. id *,iq *And i0 *Respectively indicate setting in synchronizationReference current components on d-axis, q-axis and 0-axis on a rotating coordinate system; r, L and M respectively represent stator winding resistance, self inductance and mutual inductance; l isd,LqRespectively representing the inductance components on the d-axis and the q-axis in a rotating coordinate system, and for a salient pole motor, Ld＝Lq＝L；L0L-2M represents a zero sequence inductance; ω, θ, Ψf1，Ψf3K is the electrical angular velocity, the rotor position angle, the fundamental rotor flux linkage, the third harmonic component of the rotor flux linkage and the time point respectively; t issRepresenting the sampling time.
The equation of the reference voltage vector of the motor on the d axis and the q axis transformed into the reference voltage vector of the two-phase static coordinate system by Clark is as follows:
wherein u isαrefAnd uβrefRespectively representing reference voltage vectors of the motor on an alpha axis and a beta axis on a static coordinate system; u. ofdrefAnd uqrefRespectively representing reference voltage vectors of the motor on a d axis and a q axis on a synchronous rotating coordinate system; θ is the rotor position angle.
According to the reference voltage vectors of the alpha axis and the beta axis of the motor on the static coordinate system, the calculation formula of the position angle of the reference voltage vector of the motor is as follows:
wherein, theta1The position angle of the motor reference voltage vector is used; u. ofαrefAnd uβrefRespectively representing the reference voltage vectors of the motor on the alpha and beta axes of the stationary coordinate system.
Dividing the whole plane of the double-inverter voltage vector distribution into six sectors according to the position angle theta of the motor reference voltage vector1Determining the located sector; based on the motor reference voltage vector urefThe nearest non-zero vector is determined as the first inverseVoltage vector u of converter1。
Obtaining a parameter u of a reference voltage vector of a second inverter according to an equation of the motor reference voltage vectorref2(ii) a Recombined with the voltage vector u of the first inverter1According to the formula uref2＝u1-urefAnd obtaining a reference voltage vector of the second inverter.
According to the reference voltage vector u of the second inverterref2And determining candidate voltage vectors for the second inverter, including a non-zero vector and two zero vectors.
Calculating each candidate voltage vector by the following formula to obtain a predicted current correspondingly,
idq0(k+1)＝F(k)idq0(k)+G[udq0-1(k)-udq0-2(k)]+H(k)
in the formula
udq0-1(k) Representing the 8 voltage vectors generated by the first inverter at time k; u. ofdq0-2(k) Represents the 8 voltage vectors generated by the second inverter at time k; t issRepresenting the sampling time.
The d-axis and q-axis currents and the zero-sequence current predicted on the synchronous rotating coordinate system are designed into the following objective functions:
wherein id，iqAnd i0Respectively representing current components on a d axis, a q axis and a 0 axis under a rotating coordinate system; i.e. id *，iq *And i0 *Respectively representing the set reference current components on a d axis, a q axis and a 0 axis under a rotating coordinate system; the k +1 time indicates the next time.
When the value of the objective function is minimum, the voltage vector corresponding to the used predicted current is selected as the voltage vector of the second inverter.
An apparatus for predictive control of a dual reference voltage based single vector open winding permanent magnet machine, comprising:
the motor reference voltage vector module is used for calculating a motor reference voltage vector on the synchronous rotating coordinate system according to the current dead beat control principle;
the voltage vector module of the first inverter calculates the angle of the motor reference voltage vector according to the motor reference voltage vector so as to obtain the position of the motor reference voltage vector, and determines the voltage vector of the first inverter according to the position of the motor reference voltage vector;
the reference voltage vector module of the second inverter calculates the reference voltage vector of the second inverter according to the voltage vector of the first inverter and the motor reference voltage vector;
the candidate voltage vector module of the second inverter determines the range and the quantity of the candidate voltage vectors of the second inverter at the positions in a hexagon formed by all the voltage vectors of the second inverter according to the reference voltage vector of the second inverter;
the voltage vector module of the second inverter selects a voltage vector of the second inverter from the candidate voltage vector range of the second inverter;
and an output module which inputs the voltage vector of the first inverter and the voltage vector of the second inverter to the first inverter and the second inverter, respectively.
From the above, the invention provides a method and a device for predictive control of a double-reference-voltage-based single-vector open winding permanent magnet motor. Compared with the traditional open winding permanent magnet motor model prediction control method, the method reduces the calculation burden brought by a vector enumeration method. The timeliness is stronger, and the test cost is reduced.
Drawings
In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings used in the description of the embodiments or the prior art will be briefly described below, it is obvious that the drawings in the following description are only some embodiments of the present invention, and for those skilled in the art, other drawings can be obtained according to the drawings without creative efforts.
FIG. 1 is a schematic flow chart of an embodiment of a double-reference voltage single-vector open winding permanent magnet motor prediction control method according to the present invention;
FIG. 2 is a schematic diagram of the spatial distribution of inverter voltage vectors according to an embodiment of the present invention;
FIG. 3 is a schematic diagram of a dual inverter voltage vector distribution according to an embodiment of the present invention;
fig. 4 is a schematic diagram of voltage vector distribution of a second inverter according to an embodiment of the present invention;
FIG. 5 is a schematic diagram of DC voltage measurement, rotational speed, phase current and zero sequence current of an embodiment of the present invention;
FIG. 6 is a diagram illustrating dq-axis currents according to an embodiment of the present invention.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is described in further detail below with reference to specific embodiments and the accompanying drawings.
It should be noted that all expressions using "first" and "second" in the embodiments of the present invention are used for distinguishing two entities with the same name but different names or different parameters, and it should be noted that "first" and "second" are merely for convenience of description and should not be construed as limitations of the embodiments of the present invention, and they are not described in any more detail in the following embodiments.
The current prediction is to predict the current at the next moment through a mathematical model by the current value. The embodiment is a prediction control method for a double-reference-voltage-based single-vector open winding permanent magnet motor, and as shown in fig. 2, for a two-level inverter, eight switching states correspond to eight voltage vectors, including six non-zero voltage vectors and two zero voltage vectors. Therefore, the double inverter has 8 × 8-64 switching state combinations, and has the same voltage vector distribution as the three-level inverter. Two-level inverter: electricity generated by the first inverter (INV1) and the second inverter (INV2)The pressure vectors are distributed in the same space. Since some of the combinations form the same voltage vector, the dual inverter has 19 different voltage vectors, 18 non-zero vectors and 1 zero vector. The zero vector is located at the origin O, and the other 18 non-zero vectors are located at the vertices of the three hexagons ABCDEF, HJLNQS and GIKMPR, respectively, and the vector magnitudes are 2U respectively, as shown in FIG. 3dc/3,
And 4Udc/3. The specific process flow is shown in fig. 1, and is detailed as follows:
wherein u isdref,uqrefAnd u0refRespectively representing reference voltage vectors of the motor on a d axis, a q axis and a 0 axis on a synchronous rotating coordinate system; i.e. id,iqAnd i0Respectively representing current components of the motor on a d axis, a q axis and a 0 axis on a synchronous rotation coordinate system; i.e. id *,iq *And i0 *Respectively representing reference current components arranged on a d-axis, a q-axis and a 0-axis on a synchronous rotation coordinate system; r, L and M respectively represent stator winding resistance, self inductance and mutual inductance; l isd,LqRespectively representing the inductance components on the d-axis and the q-axis in a rotating coordinate system, and for a salient pole motor, Ld＝Lq＝L；L0L-2M represents a zero sequence inductance; ω, θ, Ψf1，Ψf3K is the electrical angular velocity, the rotor position angle, the fundamental rotor flux linkage, the third harmonic component of the rotor flux linkage and the time point respectively; t issRepresenting the sampling time.
wherein u isαrefAnd uβrefRespectively representing reference voltage vectors of the motor on an alpha axis and a beta axis on a static coordinate system; u. ofdrefAnd uqrefRespectively representing reference voltage vectors of the motor on a d axis and a q axis on a synchronous rotating coordinate system; θ is the rotor position angle.
Calculating the reference voltage of the motor on the alpha axis and the beta axis according to the above 2 formulas, and then the formula of the position angle of the motor reference voltage vector is:
wherein, theta1The position angle of the motor reference voltage vector is used; u. ofαrefAnd uβrefRespectively representing the reference voltage vectors of the motor on the alpha and beta axes of the stationary coordinate system.
Calculating the angle of the motor reference voltage vector according to the formula, obtaining the position of the motor reference voltage vector in the figure 3, and determining the voltage vector of the first inverter according to the position of the motor reference voltage vector. For example, when reference voltage vector u of the motorrefLocated in sector I, as shown in FIG. 3, it is apparent that within the hexagonal shape ABCDEF containing all of the voltage vectors of INV1, a non-zero vector u1Closer to the reference vector, therefore, the first inverter selects u1(100). When the motor reference voltage vectors are respectively located in the sectors II, III and … VI, the first inverter respectively selects the voltage vector u2(100)，u3(010)，u4(011)，u5(001)，u6(101). In this way, it can be seen that,determining a voltage vector u of a first inverter1。
103, obtaining a reference voltage vector u of the second inverter (INV2) by a first formularef2Reference voltage vector of the second inverter according to uref2＝u1-urefTo obtain u1Indicating the determined voltage vector of the first inverter.
104, according to the reference voltage vector u of INV2ref2And determining a second inverter candidate voltage vector. For example, when uref2In the position shown in FIG. 3, the hexagonal GHBOFS contains all the voltage vectors of INV2, and is divided into six sectors, as shown in FIG. 4, when uref2Is within the sector shown in fig. 4, three voltage vectors, namely a non-zero vector AF and two zero vectors 000 and 111 located at the origin of the hexagonal GHBOFS, are selected as candidate voltage vectors for INV2, and the optimal vector for INV2 is selected from the three voltage vectors. When u isref2Has a non-zero vector and two zero vectors as its candidate vectors in the other sectors in fig. 4.
idq0(k+1)＝F(k)idq0(k)+G[udq0-1(k)-udq0-2(k)]+H(k)
in the formula
udq0-1(k) Representing the 8 voltage vectors generated by the first inverter at time k; u. ofdq0-2(k) Represents the 8 voltage vectors generated by the second inverter at time k; t issRepresenting the sampling time.
The d-axis and q-axis currents and the zero-sequence current predicted on the synchronous rotating coordinate system are designed into the following objective functions:
wherein id，iqAnd i0Respectively representing current components on a d axis, a q axis and a 0 axis under a rotating coordinate system; i.e. id *，iq *And i0 *Respectively representing the set reference current components on a d axis, a q axis and a 0 axis under a rotating coordinate system; the k +1 time indicates the next time.
When the value of the objective function is minimum, the voltage vector corresponding to the used predicted current is selected as the voltage vector of the second inverter.
Step 106 of inputting the voltage vector of the first inverter and the voltage vector of the second inverter to the first inverter and the second inverter, respectively.
An apparatus for predictive control of a dual reference voltage based single vector open winding permanent magnet machine, comprising:
the motor reference voltage vector module is used for calculating a motor reference voltage vector on the synchronous rotating coordinate system according to a formula according to a current dead beat control principle;
the voltage vector module of the first inverter introduces the motor reference voltage vector into a static coordinate system, calculates the angle of the motor reference voltage vector according to a formula, determines the position of the motor reference voltage vector in 6 fan-shaped areas according to the angle of the reference voltage vector, and further determines the voltage vector of the first inverter;
the reference voltage vector module of the second inverter obtains the voltage vector parameter of the second inverter according to a first formula, and then the difference between the voltage vector of the first inverter and the motor reference voltage vector parameter obtains the reference voltage vector of the second inverter;
the candidate voltage vector module of the second inverter determines the range of the candidate voltage vectors of the second inverter according to the reference voltage vector of the second inverter and the positions in a hexagon formed by all the voltage vectors of the second inverter, wherein the range comprises 2 zero vectors and a non-zero vector;
the voltage vector module of the second inverter selects a voltage vector of the second inverter from the candidate voltage vector range of the second inverter; calculating according to the candidate voltage vector and a formula to obtain a predicted current; introducing an objective function to minimize the value of the objective function, wherein a voltage vector corresponding to the used predicted current is selected as a voltage vector of the second inverter;
and an output module which inputs the voltage vector of the first inverter and the voltage vector of the second inverter to the first inverter and the second inverter, respectively.
In one embodiment, an OW-PMSG system experiment platform with 1.25KW power level is built, OW-PMSG parameters are shown in a table 1,
wherein the system sampling frequency is set to 10 KHz. The experimental condition is that the DC bus voltage u is given* dcThe motor speed n is 500r/min when the voltage is 90V. As shown in fig. 5, the dc voltage measurement, the rotational speed, the phase current and the zero sequence current under the method of the present invention. As shown in fig. 6, the dq axis current under the method of the present invention.
The apparatus of the foregoing embodiment is used to implement the corresponding method in the foregoing embodiment, and has the beneficial effects of the corresponding method embodiment, which are not described herein again.
The embodiments of the invention are intended to embrace all such alternatives, modifications and variances that fall within the broad scope of the appended claims. Therefore, any omissions, modifications, substitutions, improvements and the like that may be made without departing from the spirit and principles of the invention are intended to be included within the scope of the invention.
Claims (3)
1. A double-reference-voltage-based single-vector open winding permanent magnet motor prediction control method is characterized by comprising the following steps:
calculating a motor reference voltage vector on a synchronous rotating coordinate system according to a current dead beat control principle;
calculating an angle of the motor reference voltage vector according to the motor reference voltage vector so as to obtain a position of the motor reference voltage vector, and determining a voltage vector of a first inverter according to the position of the motor reference voltage vector;
calculating a reference voltage vector of a second inverter according to the voltage vector of the first inverter and the motor reference voltage vector;
determining the range and the number of candidate voltage vectors of the second inverter according to the positions of the reference voltage vectors of the second inverter in a hexagon formed by all voltage vectors of the second inverter;
selecting a voltage vector of the second inverter from the candidate voltage vector range of the second inverter;
inputting a voltage vector of the first inverter and a voltage vector of the second inverter to the first inverter and the second inverter, respectively;
the equation of the motor reference voltage vector of the d-axis, the q-axis and the 0-axis on the synchronous rotating coordinate system is as follows:
wherein u isdref,uqrefAnd u0refRespectively representing reference voltage vectors of the motor on a d axis, a q axis and a 0 axis on a synchronous rotating coordinate system; i.e. id,iqAnd i0Respectively representing current components of the motor on a d axis, a q axis and a 0 axis on a synchronous rotation coordinate system; i.e. id *,iq *And i0 *Respectively representing reference current components arranged on a d-axis, a q-axis and a 0-axis on a synchronous rotation coordinate system; r, L and M respectively represent stator winding resistance, self inductance and mutual inductance; l isd,LqRespectively representing the inductance components on the d-axis and the q-axis in a rotating coordinate system, and for a salient pole motor, Ld＝Lq＝L；L0L-2M represents a zero sequence inductance; ω, θ, Ψf1，Ψf3K is the electrical angular velocity, the rotor position angle, the fundamental rotor flux linkage, the third harmonic component of the rotor flux linkage and the time point respectively; t issRepresents a sampling time; the equation of the reference voltage vector of the motor on the d axis and the q axis transformed into the reference voltage vector of the two-phase static coordinate system by Clark is as follows:
wherein u isαrefAnd uβrefRespectively representing reference voltage vectors of the motor on an alpha axis and a beta axis on a static coordinate system; u. ofdrefAnd uqrefRespectively representing reference voltage vectors of the motor on a d axis and a q axis on a synchronous rotating coordinate system; theta is a rotor position angle; according to the reference voltage vectors of the alpha axis and the beta axis of the motor on the static coordinate system, the calculation formula of the position angle of the reference voltage vector of the motor is as follows:
wherein, theta1The position angle of the motor reference voltage vector is used; u. ofαrefAnd uβrefRespectively representing reference voltage vectors of the motor on an alpha axis and a beta axis on a static coordinate system;
dividing the whole plane of the double-inverter voltage vector distribution into six sectors according to the position angle theta of the motor reference voltage vector1Determining the located sector; then according to the reference voltage vector u of the motorrefDetermining the voltage vector u of the first inverter from the nearest non-zero vector1；
Obtaining the parameter u of the reference voltage vector of the motor according to the equation of the reference voltage vector of the motorref(ii) a Recombined with the voltage vector u of the first inverter1According to the formula uref2＝u1-urefObtaining a reference voltage vector of the second inverter;
according to the reference voltage vector u of the second inverterref2Determining candidate voltage vectors of the second inverter, including a non-zero vector and two zero vectors;
wherein, each candidate voltage vector is calculated by the following formula to correspondingly obtain a predicted current,
idq0(k+1)＝F(k)idq0(k)+G[udq0-1(k)-udq0-2(k)]|+H(k)
in the formula
udq0-1(k) Representing the 8 voltage vectors generated by the first inverter at time k; u. ofdq0-2(k) Represents the 8 voltage vectors generated by the second inverter at time k; t issRepresenting the sampling time.
2. The double-reference-voltage-based single-vector open-winding permanent magnet motor predictive control method according to claim 1, characterized in that d-axis and q-axis currents and zero-sequence currents predicted on a synchronous rotating coordinate system are designed with the following objective functions:
wherein id，iqAnd i0Respectively representing current components on a d axis, a q axis and a 0 axis under a rotating coordinate system; i.e. id *，iq *And i0 *Respectively representing the set reference current components on a d axis, a q axis and a 0 axis under a rotating coordinate system; the k +1 time represents the next time;
when the value of the objective function is minimum, the voltage vector corresponding to the used predicted current is selected as the voltage vector of the second inverter.
3. An apparatus for predictive control of a dual reference voltage based single vector open winding permanent magnet machine, comprising:
the motor reference voltage vector module is used for calculating a motor reference voltage vector on the synchronous rotating coordinate system according to the current dead beat control principle;
the voltage vector module of the first inverter calculates the angle of the motor reference voltage vector according to the motor reference voltage vector so as to obtain the position of the motor reference voltage vector, and determines the voltage vector of the first inverter according to the position of the motor reference voltage vector;
the reference voltage vector module of the second inverter calculates the reference voltage vector of the second inverter according to the voltage vector of the first inverter and the motor reference voltage vector;
the candidate voltage vector module of the second inverter determines the range and the quantity of the candidate voltage vectors of the second inverter at the positions in a hexagon formed by all the voltage vectors of the second inverter according to the reference voltage vector of the second inverter;
the voltage vector module of the second inverter selects a voltage vector of the second inverter from the candidate voltage vector range of the second inverter;
an output module that inputs a voltage vector of the first inverter and a voltage vector of the second inverter to the first inverter and the second inverter, respectively;
the equation of the motor reference voltage vector of the d-axis, the q-axis and the 0-axis on the synchronous rotating coordinate system is as follows:
wherein u isdref,uqrefAnd u0refRespectively representing reference voltage vectors of the motor on a d axis, a q axis and a 0 axis on a synchronous rotating coordinate system; i.e. id,iqAnd i0Respectively representing current components of the motor on a d axis, a q axis and a 0 axis on a synchronous rotation coordinate system; i.e. id *,iq *And i0 *Respectively representing reference current components arranged on a d-axis, a q-axis and a 0-axis on a synchronous rotation coordinate system; r, L and M respectively represent stator winding resistance, self inductance and mutual inductance; l isd,LqRespectively representing the inductance components on the d-axis and the q-axis in a rotating coordinate system, and for a salient pole motor, Ld＝Lq＝L；L0L-2M represents a zero sequence inductance; ω, θ, Ψf1，Ψf3K is the electrical angular velocity, the rotor position angle, the fundamental rotor flux linkage, the third harmonic component of the rotor flux linkage and the time point respectively; t issRepresents a sampling time; the equation of the reference voltage vector of the motor on the d axis and the q axis transformed into the reference voltage vector of the two-phase static coordinate system by Clark is as follows:
wherein u isαrefAnd uβrefRespectively representing reference voltage vectors of the motor on an alpha axis and a beta axis on a static coordinate system; u. ofdrefAnd uqrefRespectively representing reference voltage vectors of the motor on a d axis and a q axis on a synchronous rotating coordinate system; theta is a rotor position angle; according to the reference voltage vectors of the alpha axis and the beta axis of the motor on the static coordinate system, the calculation formula of the position angle of the reference voltage vector of the motor is as follows:
wherein, theta1The position angle of the motor reference voltage vector is used; u. ofαrefAnd uβrefRespectively representing reference voltage vectors of the motor on an alpha axis and a beta axis on a static coordinate system;
dividing the whole plane of the double-inverter voltage vector distribution into six sectors according to the position angle theta of the motor reference voltage vector1Determining the located sector; then according to the reference voltage vector u of the motorrefNearest non-zero vectorDetermining a voltage vector u of the first inverter1；
Obtaining the parameter u of the reference voltage vector of the motor according to the equation of the reference voltage vector of the motorref(ii) a Recombined with the voltage vector u of the first inverter1According to the formula uref2＝u1-urefObtaining a reference voltage vector of the second inverter;
according to the reference voltage vector u of the second inverterref2Determining candidate voltage vectors of the second inverter, including a non-zero vector and two zero vectors;
wherein, each candidate voltage vector is calculated by the following formula to correspondingly obtain a predicted current,
idq0(k+1)＝F(k)idq0(k)+G[udq0-1(k)-udq0-2(k)|+H(k)
in the formula
udq0-1(k) Representing the 8 voltage vectors generated by the first inverter at time k; u. ofdq0-2(k) Represents the 8 voltage vectors generated by the second inverter at time k; t issRepresenting the sampling time.
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| CN111711397B (en) * | 2020-05-27 | 2021-11-02 | 东南大学 | Predictive current control method for semi-centralized open-winding permanent magnet synchronous motor system |
| CN112117941A (en) * | 2020-08-01 | 2020-12-22 | 南通长江电器实业有限公司 | Fault-tolerant control method of open-winding permanent magnet synchronous motor based on model prediction current control |
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| CN108123649B (en) * | 2017-12-01 | 2019-09-06 | 北方工业大学 | A kind of unilateral controllable parallel open magneto alternator control method of winding |
| CN108418502B (en) * | 2018-01-19 | 2020-05-05 | 江苏大学 | Permanent magnet synchronous motor open winding fault-tolerant direct torque control method based on improved SVPWM |
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