CN109617844A - A kind of method and system of carrier synchronization - Google Patents
A kind of method and system of carrier synchronization Download PDFInfo
- Publication number
- CN109617844A CN109617844A CN201910020334.8A CN201910020334A CN109617844A CN 109617844 A CN109617844 A CN 109617844A CN 201910020334 A CN201910020334 A CN 201910020334A CN 109617844 A CN109617844 A CN 109617844A
- Authority
- CN
- China
- Prior art keywords
- pilot signal
- carrier wave
- signal
- doppler
- value
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/0014—Carrier regulation
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L1/00—Arrangements for detecting or preventing errors in the information received
- H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
- H04L1/0056—Systems characterized by the type of code used
- H04L1/0059—Convolutional codes
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L1/00—Arrangements for detecting or preventing errors in the information received
- H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
- H04L1/0056—Systems characterized by the type of code used
- H04L1/0059—Convolutional codes
- H04L1/006—Trellis-coded modulation
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
- H04L27/20—Modulator circuits; Transmitter circuits
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L5/00—Arrangements affording multiple use of the transmission path
- H04L5/003—Arrangements for allocating sub-channels of the transmission path
- H04L5/0048—Allocation of pilot signals, i.e. of signals known to the receiver
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/0014—Carrier regulation
- H04L2027/0024—Carrier regulation at the receiver end
- H04L2027/0026—Correction of carrier offset
Landscapes
- Engineering & Computer Science (AREA)
- Signal Processing (AREA)
- Computer Networks & Wireless Communication (AREA)
- Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
Abstract
The embodiment of the invention discloses a kind of method and system of carrier synchronization；This method comprises: the single bit of information of input is carried out the convolution coding that code rate is 1/2 by transmitting terminal, the encoded output sequence that length is L is obtained；And encoded output sequence is modulated to obtain the modulation data that length is L+N；Receiving end according to receive signal in pilot signal Instantaneous phase estimation pilot signal in the Doppler shift of carrier wave and the doppler changing rate of carrier wave；And it is compensated according to the Doppler shift estimated value of carrier wave and the doppler changing rate estimated value of carrier wave to signal is received；Viterbi Viterbi decoding is carried out to compensated signal, and during decoding, it is handled as follows for each current time until the L moment: obtaining the survivor path of the current time corresponding each state of subsequent time, obtain the instantaneous phase value of current time corresponding subsequent time；For the l-th moment, the smallest survivor path of path metric value is selected to be recalled, obtains the sequence closest to encoded output sequence.
Description
Technical field
The present embodiments relate to wireless communication technology field more particularly to a kind of method and system of carrier synchronization.
Background technique
In the high dynamic environments such as mobile communication or military communication, since the relatively high speed movement of communicating pair can produce
It gives birth to Doppler shift and Algorithm for Doppler Frequency Rate-of-Change and causes communication quality so as to cause the sharply deterioration of receiving end error performance
Degradation.How based on this, Doppler shift and doppler changing rate are accurately estimated and eliminated under high dynamic environment, into
And it obtains ideal carrier synchronization and is a problem to be solved.
It should be pointed out that traditional carrier synchronization method may include: data auxiliary (Data-Aided, DA) algorithm,
Unbound nucleus (Non Data-Aided, NDA) algorithm and coding auxiliary (Code aided, CA) algorithm three classes.DA algorithm
Estimation range is wide, and estimated accuracy is related to known array length, occupies extra bandwidth, in short burst communication, system effectiveness is low；
NDA algorithm includes phaselocked loop, and two kinds of approach of blind estimate, band efficiency is high, but needs high s/n ratio, and locking range is narrow；CA is calculated
Method realizes parameter Estimation using soft-decision, requires signal-to-noise ratio lower, computational complexity height, and estimation range is limited.
For the defect of the carrier synchronization method of above-mentioned three quasi-tradition, some scholars propose maximal possibility estimation
(Maximum likelihood, ML) method, this method is equivalent to using Fourier Transform of Fractional Order, to Doppler shift and change
Rate carries out two-dimensional search, computationally intensive although this method estimated accuracy is very high.In addition, also thering are some scholars to propose out
Ring capture auxiliary phase-locked loop method, i.e., open-loop acquisition reduces parameter area to be estimated first, recycle phaselocked loop realize signal with
Track；However this method, under Low SNR, when input signal power is lower than loop thresholding, phaselocked loop is difficult to restrain, nothing
Method correctly works.There are also some scholars to be utilized convolutional code in the carrier synchronization stage, and receiving end by phaselocked loop tracking and
Encoded information is effectively utilized in Viterbi (Viterbi) decoding, this method, but due to being related to demodulating firmly twice and failing to fill
Divide and utilize convolutional code decoding characteristic, causes the receiver bit error rate higher.
Summary of the invention
In order to solve the above technical problems, an embodiment of the present invention is intended to provide a kind of method and system of carrier synchronization, it can
Phase Tracking precision is improved, error rate of system is reduced.
The technical scheme of the present invention is realized as follows:
In a first aspect, the embodiment of the invention provides a kind of methods of carrier synchronization, which comprises
The single bit of information of input is carried out the convolution coding that code rate is 1/2 by transmitting terminal, and it is defeated to obtain the coding that length is L
Sequence out；
The encoded output sequence is modulated obtained length as L according to the modulation strategy set by the transmitting terminal
The modulation data of+N；
Receiving end is according to the Doppler for receiving carrier wave in pilot signal described in the Instantaneous phase estimation of pilot signal in signal
The doppler changing rate of frequency deviation and carrier wave；
The receiving end is carried according in the Doppler shift estimated value and the pilot signal of carrier wave in the pilot signal
The doppler changing rate estimated value of wave compensates the reception signal, obtains compensated signal；
The receiving end carries out Viterbi Viterbi decoding to the compensated signal, and during decoding, for
Each current time is handled as follows until the L moment:
The survivor path of the current time each state of corresponding subsequent time is obtained,
Obtain the instantaneous phase value of the current time corresponding subsequent time；
For the l-th moment, the receiving end selection the smallest survivor path of path metric value is recalled, and is most connect
The sequence of the nearly encoded output sequence.
Second aspect, the embodiment of the invention provides a kind of systems of carrier synchronization, the system comprises transmitting terminal and connect
Receiving end；
The transmitting terminal includes the first communication interface, first memory and first processor；Wherein,
First communication interface, during for being received and sent messages between other ext nal network elements, signal is connect
It receives and sends；
The first memory, for storing the computer program that can be run on the first processor；
The first processor, for executing following steps when running the computer program:
The single bit of information of input is subjected to the convolution coding that code rate is 1/2, the coding that length is L is obtained and exports sequence
Column；And the encoded output sequence is modulated obtained length as the modulation number of L+N according to the modulation strategy set
According to；
The receiving end includes: the second communication interface, second memory and second processor；
Wherein, second communication interface, during for being received and sent messages between other ext nal network elements, signal
Send and receive；
The second memory, for storing the computer program that can be run in second processor；
The second processor, for executing following steps when running the computer program:
According to receive described in the Instantaneous phase estimation of pilot signal in signal in pilot signal the Doppler shift of carrier wave and
The doppler changing rate of carrier wave；And
According to the Doppler of carrier wave in the Doppler shift estimated value and the pilot signal of carrier wave in the pilot signal
Change rate estimated value compensates the reception signal, obtains compensated signal；And
Viterbi Viterbi decoding is carried out to the compensated signal, and during decoding, for it is each current when
It is handled as follows at quarter until the L moment:
The survivor path of the current time each state of corresponding subsequent time is obtained,
Obtain the instantaneous phase value of the current time corresponding subsequent time；And
For the l-th moment, the smallest survivor path of path metric value is selected to be recalled, obtained closest to the coding
The sequence of output sequence.
The embodiment of the invention provides a kind of method and system of carrier synchronization；By combined pilot signal and
Viterbi decoding carries out carrier synchronization, can reach and improve Phase Tracking precision, reduce the effect of error rate of system.
Detailed description of the invention
Fig. 1 is a kind of baseband model schematic diagram of communication system provided in an embodiment of the present invention；
Fig. 2 is a kind of method flow schematic diagram of carrier synchronization provided in an embodiment of the present invention；
Fig. 3 is a kind of concrete signal stream flow diagram of Viterbi decoding provided in an embodiment of the present invention；
Fig. 4 is a kind of design diagram of third order pll provided in an embodiment of the present invention；
Fig. 5 is a kind of system composition schematic diagram of carrier synchronization provided in an embodiment of the present invention；
Fig. 6 is the system composition schematic diagram of another carrier synchronization provided in an embodiment of the present invention；
Fig. 7 is a kind of simulation performance contrast schematic diagram provided in an embodiment of the present invention；
Fig. 8 is another simulation performance contrast schematic diagram provided in an embodiment of the present invention；
Fig. 9 is another simulation performance contrast schematic diagram provided in an embodiment of the present invention.
Specific embodiment
Following will be combined with the drawings in the embodiments of the present invention, and technical solution in the embodiment of the present invention carries out clear, complete
Site preparation description.
Referring to Fig. 1, it illustrates a kind of baseband model signals for communication system that the embodiment of the present invention proposes, therefrom can be with
Find out, transmitting terminal Tx, which is generated, to be sent sequence or send signal x, and will be sent sequence or sent signal x and be sent to communication channel H.
In embodiments of the present invention, communication channel H has high dynamic characteristic, that is to say, that communicating pair is in relatively high speed movement
State, such as satellite communication, high-speed maneuver Platform communication etc. sends sequence x after by communication channel H, receiving end Rx
Reception signal y can be expressed as y=Hx+n, wherein n indicate communication channel brought by noise.
Embodiment one
Illustrated based on baseband model shown in FIG. 1, a kind of method of carrier synchronization provided in an embodiment of the present invention, this method
It can be applied to the transmitting terminal Tx and receiving end Rx in baseband model as shown in Figure 1, referring to fig. 2, this method may include:
S201: the single bit of information of input is carried out the convolution coding that code rate is 1/2 by the transmitting terminal, is obtained length and is
The encoded output sequence of L；
For S201, in one possible implementation, the transmitting terminal carries out code in the single bit of information that will be inputted
The convolution coding that rate is 1/2 obtains encoded output sequence, may include:
The convolution coding that code rate is 1/2 is carried out to the single bit of information of the input, obtains dibit coded sequence；Its
In, the dibit coded sequence length is L, and the output expression formula of the dibit coded sequence is respectively g1(x)=1+x+x2
And g2(x)=1+x2, wherein x indicates the time lag of first order of the single bit of information of the input, x2Indicate the single-bit letter of the input
The secondary delay of breath.
S202: the encoded output sequence is modulated obtained tune according to the modulation strategy of setting by the transmitting terminal
Data processed；
For S202, in one possible implementation, the transmitting terminal is by the encoded output sequence according to setting
Modulation strategy be modulated obtained length be L+N modulation data, may include:
The full null sequence that length is N is added before encoded output sequence, obtains the addition pilot frequency sequence that length is L+N
Signal；
QPSK modulation is carried out to the signal of the addition pilot frequency sequence, obtains four phase modulated signals；Wherein " 00 " sequence is reflected
It is mapped to 1/4 π, " 01 " sequence is mapped to 3/4 π, and " 10 " sequence is mapped to 5/4 π, and " 11 " sequence is mapped to 7/4 π.
S203: receiving end carrier wave in the pilot signal according to the Instantaneous phase estimation of pilot signal in reception signal
Doppler shift and carrier wave doppler changing rate；
For S203, in one possible implementation, the receiving end is according to the wink for receiving pilot signal in signal
When phase estimation described in the Doppler shift of carrier wave and the doppler changing rate of carrier wave in pilot signal, comprising:
The pilot signal for receiving signal is extracted in the receiving end, obtains the instantaneous phase of the pilot signal；
For the instantaneous phase of the pilot signal, the pilot tone is estimated according to minimum mean square error criterion in the receiving end
The doppler changing rate of the Doppler shift of carrier wave and carrier wave in signal, obtains the Doppler shift of carrier wave in the pilot signal
The doppler changing rate estimated value of estimated value and carrier wave.
It should be noted that the reception signal is the modulation data received by the receiving end by communication letter
Signal after road, in embodiments of the present invention, it is fixed with ideal symbol that the reception signal can be expressed as communication system
When synchronous and intersymbol interference it is negligible, the receiving end can export sampled value by matched filtering, be based on this, described to connect
It collects mail and number is
For this implementation, it is preferable that the pilot signal for receiving signal is extracted in the receiving end, obtains the pilot tone letter
Number instantaneous phase, may include:
To the reception signalTop n data carry out -1/4 π phase rotation, obtain
Pilot signal after to phase rotation；Wherein, ckIndicate the modulated signal of energy normalized；The period of T expression symbol；nk
Indicate the introduced zero-mean complex Gaussian white noise of communication channel, in-phase component is mutually indepedent with quadrature component, and variance is equal
Value is N0/2；△ fT indicates unknown normalization carrier Doppler frequency offset；△aT2Indicate that how general unknown normalization carrier wave is
Strangle change rate offset；It is to be appreciated that changing in pilot signal after the phase rotation containing Doppler shift and Doppler
Rate；
Calculus of differences is carried out according to formula 1 to the pilot signal after the phase rotation, obtains the instantaneous of the pilot signal
Phase；
rk+1e-π/4*conj(rke-π/4) (1)
Wherein, conj (rke-π/4) indicate rke-π/4Complex conjugate.
For this implementation, it is preferable that the instantaneous phase for the pilot signal, according to least mean-square error
Criterion estimates the doppler changing rate of the Doppler shift of carrier wave and carrier wave in the pilot signal, obtains in the pilot signal
The doppler changing rate estimated value of carrier wave in the Doppler shift estimated value and the pilot signal of carrier wave may include:
For the instantaneous phase of the pilot signal, the Doppler shift of carrier wave in the pilot signal is obtained using formula 2
Estimated value and the doppler changing rate estimated value of carrier wave in the pilot signal is obtained using formula 3:
Wherein,For instantaneous phase, design factor αN, βN, γNIt respectively indicates as follows:
It should be noted that the minimum mean square error criterion (MMSE, Minimum Mean Squared Error) belongs to
In a kind of pilot signal open-loop acquisition method.When there are the high dynamic environments of Doppler shift and doppler changing rate offset
Under, the baseband signal phase of receiving endIt can indicate are as follows:
Wherein,Indicate the carrier phase value of t moment；The Doppler shift of △ f expression carrier wave；△ a indicates to carry
The doppler changing rate of wave deviates；For residual term R (t, △ t), when △ t tends to 0, then three ranks that this is △ t are infinitely small.
It can thus be appreciated that: although there may be the frequency change rate of higher order, it is relatively small to ignore.Therefore, very in short-term
In, it can be by three rank multinomials of baseband signal phase approximation come to phase, Doppler frequency and doppler changing rate
Estimation.That is, being respectively t for the time1,t2,...,tN(t1<t2<...<tN) moment phase sample valueThe Difference Calculation of phase is carried out, after eliminating phase ambiguity, available phase error computation formula are as follows:
Based on MMSE criterion, minimal error e (N), enables e (N) right respectively in order to obtainWithSeeking local derviation and enabling it is 0,
Arrangement can obtain:
Wherein,
S204: receiving end is carried according in the Doppler shift estimated value and the pilot signal of carrier wave in the pilot signal
The doppler changing rate estimated value of wave compensates the reception signal, obtains compensated signal；
For S204, in one possible implementation, Doppler's frequency according to carrier wave in the pilot signal
The doppler changing rate estimated value of carrier wave compensates the reception signal in inclined estimated value and the pilot signal, is mended
Signal after repaying may include:
Pass through compensation formulaThe reception signal is compensated, compensated signal is obtained.
S205: receiving end carries out Viterbi Viterbi decoding to the compensated signal, and during decoding, needle
Step is handled as follows to each current time until the L moment:
The survivor path of the current time each state of corresponding subsequent time is obtained,
Obtain the instantaneous phase value of the current time corresponding subsequent time；
It is in one possible implementation, described to obtain corresponding lower a period of time at the current time for S205
The survivor path for carving each state may include:
Setting sequence ..., ck-3,ck-2,ck-1It is expressed as transmission information sequence until current time kT, Sk∈{0,
1 ..., Q-1 } it is expressed as the state node set at current time, it altogether include Q node；
SettingIt is expressed as entering the information sequence of m node from certain survivor path, obtain from current
Some node branch of the m node at moment to subsequent time, which is measured, is
According to the branched measurement value of each stateObtain stateful to subsequent time path since decoding
Metric
A smallest value is selected from the path metric value of each state, other route deletions are obtained to next
Stateful survivor path until moment.
It should be noted that Viterbi decoding is the maximum-likelihood decoding algorithm of convolutional code, in embodiments of the present invention,
The concrete signal stream process of Viterbi decoding may refer to shown in Fig. 3.Under the influence of no synchronous error, signal is by adding
Property white Gaussian noise (AWGN, Additive White Gaussian Noise) channel reach receiving end, what receiving end received
Complex baseband signal is expressed as r (t)=s (t | α)+n (t)；
Wherein, α is expressed as sending symbol sebolic addressing；N (t) is that double-side band power spectral density is N0White complex gaussian noise letter
Number.
In the case where sending waveform is s (t), the prior probability of signal is received are as follows:
By maximizing priori probability information, can be obtained by maximum likelihood (ML, Maximum Likelihood) thought
It is to symbol sebolic addressing estimated value is sent
It is available that the simplification of symbol sebolic addressing estimated value will be sent:
When estimating transmission sequence, complexity increases with the increase exponentially of sequence length L, to simplify meter
Calculation amount can reduce computation complexity by way of iteration.Defining path metric isThen
Within the nth symbol period, the calculating of path metric are as follows:
Wherein,The referred to as branch metric at current time, its calculation formula is:
The state path measurement of each state is reached by constantly calculating each moment, and choose each state there is maximum
The path record of path metric is saved, i.e. preservation survivor path, and all survivals have been recorded in LT moment, that is, finish time
Recalled behind path, the Viterbi decoding for sending symbol sebolic addressing can be completed, so that the code sequence for obtaining demodulation is one
There is the sequence of maximum prior probability.
It is in one possible implementation, described to obtain corresponding lower a period of time at the current time for S205
The instantaneous phase value at quarter may include:
The phase pushing figure at the current time is determined as
By the phase pushing figure after third order pll, the instantaneous phase value of subsequent time is obtainedIts
In, the instantaneous phase value calculation formula of subsequent time indicates are as follows:γ is third order pll increasing
Benefit.
It should be noted that since traditional second-order PLL has stable state difference, this hair under high dynamic environment
Bright embodiment is eliminated stable state under high dynamic environment using third order pll and differs problem, the lock of three ranks described in the embodiment of the present invention
Phase ring can be used for the tracking to remaining carrier wave skew.
In the embodiment of the present invention, the system function of used third order pll structure are as follows:
Wherein, ωnFor loop natural angular frequency, a and b are phaselocked loop loop filter design parameter.
It is in the concrete realization, shown in Figure 4 to the design of third order pll namely to the design of loop filter,
It is realized using Bilinear transformation method from analog domain and transforms to numeric field, the parameter of available loop filter is as follows:
Wherein, KdFor phase detector gain, K0For numerically-controlled oscillator (NCO, Numerically Controlled
Oscillator) gain.
S206: for the l-th moment, the receiving end selection the smallest survivor path of path metric value is recalled, and is obtained most
Close to the sequence of the encoded output sequence.
It is to be appreciated that the code sequence for obtaining demodulation, which is one, to be had most until S206, Viterbi decode process and complete
The sequence of big prior probability, so that receiving end can complete carrier synchronization according to the sequence closest to the encoded output sequence.
Due to carrier synchronization method shown in Fig. 2 combined pilot signal and Viterbi decoding, can reach improve phase with
Track precision reduces the effect of error rate of system.
Embodiment two
Based on the identical inventive concept of previous embodiment, referring to Fig. 5, it illustrates a kind of loads provided in an embodiment of the present invention
The synchronous system 5 of wave forms, and the system 5 includes transmitting terminal 51 and receiving end 52；Wherein, the transmitting terminal 51 includes coding unit
Divide 511 and modulating part 512；Wherein,
The coded portion 511 is configured to carry out the convolution coding that code rate is 1/2 in the single bit of information that will be inputted,
Obtain the encoded output sequence that length is L；
The modulating part 512 is configured to the encoded output sequence being modulated institute according to the modulation strategy of setting
Obtained length is the modulation data of L+N；
The receiving end 52 includes: estimating part 521, compensation part 522 and decoding portion 523；Wherein, the estimator
Divide 521, is configured to according to the Doppler's frequency for receiving carrier wave in pilot signal described in the Instantaneous phase estimation of pilot signal in signal
Inclined and carrier wave doppler changing rate；
The compensation part 522 is configured to according to the Doppler shift estimated value of carrier wave in the pilot signal and described
The doppler changing rate estimated value of carrier wave compensates the reception signal in pilot signal, obtains compensated signal；
The decoding portion 523 is configured to carry out Viterbi Viterbi decoding to the compensated signal, and is translating
During code, it is handled as follows for each current time until the L moment:
The survivor path of the current time each state of corresponding subsequent time is obtained,
Obtain the instantaneous phase value of the current time corresponding subsequent time；
For the l-th moment, the receiving end selection the smallest survivor path of path metric value is recalled, and is most connect
The sequence of the nearly encoded output sequence.
For above scheme, in one possible implementation, the coded portion 511 is configured to the input
Single bit of information carry out code rate be 1/2 convolution coding, obtain dibit coded sequence；Wherein, the dibit coding
Sequence length is L, and the output expression formula of the dibit coded sequence is respectively g1(x)=1+x+x2And g2(x)=1+x2,
Middle x indicates the time lag of first order of the single bit of information of the input, x2Indicate the secondary delay of the single bit of information of the input.
For above scheme, in one possible implementation, the modulating part 512 is configured to export in coding
The full null sequence that length is N is added before sequence, obtains the signal for the addition pilot frequency sequence that length is L+N；
QPSK modulation is carried out to the signal of the addition pilot frequency sequence, obtains four phase modulated signals；Wherein " 00 " sequence is reflected
It is mapped to 1/4 π, " 01 " sequence is mapped to 3/4 π, and " 10 " sequence is mapped to 5/4 π, and " 11 " sequence is mapped to 7/4 π.
For above scheme, in one possible implementation, the estimating part 521 is configured that
The pilot signal for receiving signal is extracted, the instantaneous phase of the pilot signal is obtained；
For the instantaneous phase of the pilot signal, carrier wave in the pilot signal is estimated according to minimum mean square error criterion
Doppler shift and carrier wave doppler changing rate, obtain the Doppler shift estimated value and load of carrier wave in the pilot signal
The doppler changing rate estimated value of wave.
In above-mentioned implementation, it is preferable that the estimating part 521 is configured that
To the reception signalTop n data carry out -1/4 π phase rotation, obtain
Pilot signal after to phase rotation；Wherein, ckIndicate the modulated signal of energy normalized；The period of T expression symbol；nk
Indicate the introduced zero-mean complex Gaussian white noise of communication channel, in-phase component is mutually indepedent with quadrature component, and variance is equal
Value is N0/2；△ fT indicates unknown normalization carrier Doppler frequency offset；△aT2Indicate that how general unknown normalization carrier wave is
Strangle change rate offset；It is to be appreciated that changing in pilot signal after the phase rotation containing Doppler shift and Doppler
Rate；
Calculus of differences is carried out according to formula 1 to the pilot signal after the phase rotation, obtains the instantaneous of the pilot signal
Phase；
rk+1e-π/4*conj(rke-π/4) (1)
Wherein, conj (rke-π/4) indicate rke-π/4Complex conjugate.
In above-mentioned implementation, it is preferable that the estimating part 521 is configured that
For the instantaneous phase of the pilot signal, the Doppler shift of carrier wave in the pilot signal is obtained using formula 2
Estimated value and the doppler changing rate estimated value of carrier wave in the pilot signal is obtained using formula 3:
Wherein,For instantaneous phase, design factor αN, βN, γNIt respectively indicates as follows:
For above scheme, in one possible implementation, the compensation part 522 is configured that
Pass through compensation formulaThe reception signal is compensated, compensated signal is obtained.
For above scheme, in one possible implementation, the decoding portion 523 is configured that
Setting sequence ..., ck-3,ck-2,ck-1It is expressed as transmission information sequence until current time kT, Sk∈{0,
1 ..., Q-1 } it is expressed as the state node set at current time, it altogether include Q node；
SettingIt is expressed as entering the information sequence of m node from certain survivor path, obtain from current
Some node branch of the m node at moment to subsequent time, which is measured, is
According to the branched measurement value of each stateObtain stateful to subsequent time path since decoding
Metric
A smallest value is selected from the path metric value of each state, other route deletions are obtained to next
Stateful survivor path until moment.
For above scheme, in one possible implementation, the decoding portion 523 is configured that
The phase pushing figure at the current time is determined as
By the phase pushing figure after third order pll, the instantaneous phase value of subsequent time is obtainedIts
In, the instantaneous phase value calculation formula of subsequent time indicates are as follows:γ is third order pll increasing
Benefit.
It is to be appreciated that in the present embodiment, " part " can be partial circuit, segment processor, subprogram or soft
Part etc., naturally it is also possible to be unit, can also be that module is also possible to non-modularization.
In addition, each component part in the present embodiment can integrate in one processing unit, it is also possible to each list
Member physically exists alone, and can also be integrated in one unit with two or more units.Above-mentioned integrated unit both can be with
Using formal implementation of hardware, can also be realized in the form of software function module.
If the integrated unit realizes that being not intended as independent product is sold in the form of software function module
Or in use, can store in a computer readable storage medium, based on this understanding, the technical side of the present embodiment
Substantially all or part of the part that contributes to existing technology or the technical solution can be produced case in other words with software
The form of product embodies, which is stored in a storage medium, including some instructions are used so that one
Platform computer equipment (can be personal computer, server or the network equipment etc.) or processor (processor) execute sheet
The all or part of the steps of embodiment the method.And storage medium above-mentioned includes: USB flash disk, mobile hard disk, read-only memory
(ROM, Read Only Memory), random access memory (RAM, Random Access Memory), magnetic or disk
Etc. the various media that can store program code.
Based on 5 composed structure of above system, referring to Fig. 6, it illustrates another carrier wave provided in an embodiment of the present invention is same
The system 5 of step forms, and the system 5 includes transmitting terminal 51 and receiving end 52；
The transmitting terminal 51 includes the first communication interface 601, first memory 602 and first processor 603；Various components
It is coupled by the first bus system 604.It is understood that the first bus system 804 is for realizing the company between these components
Connect letter.First bus system 804 further includes that power bus, control bus and status signal are total in addition to including data/address bus
Line.But for the sake of clear explanation, the various buses in transmitting terminal 51 are all designated as the first bus system 804 in Fig. 5；Its
In,
First communication interface 601, during for being received and sent messages between other ext nal network elements, signal
It sends and receivees；
The first memory 602, for storing the computer program that can be run on the first processor 603；
The first processor 603, for executing following steps when running the computer program:
The single bit of information of input is subjected to the convolution coding that code rate is 1/2, the coding that length is L is obtained and exports sequence
Column；And the encoded output sequence is modulated obtained length as the modulation number of L+N according to the modulation strategy set
According to；
And the receiving end 52 includes: the second communication interface 605, second memory 606 and second processor 607；It is each
Component is coupled by the second bus system 608.It is understood that the second bus system 608 is for realizing between these components
Connection communication.Second bus system 608 further includes power bus, control bus and state letter in addition to including data/address bus
Number bus.But for the sake of clear explanation, the various buses in receiving end 52 are all designated as the second bus system in Fig. 6
608；
Wherein, second communication interface 605, during for being received and sent messages between other ext nal network elements,
Signal sends and receivees；
The second memory 606, for storing the computer program that can be run in second processor 607；
The second processor 607, for executing following steps when running the computer program:
According to receive described in the Instantaneous phase estimation of pilot signal in signal in pilot signal the Doppler shift of carrier wave and
The doppler changing rate of carrier wave；And
According to the Doppler of carrier wave in the Doppler shift estimated value and the pilot signal of carrier wave in the pilot signal
Change rate estimated value compensates the reception signal, obtains compensated signal；And
Viterbi Viterbi decoding is carried out to the compensated signal, and during decoding, for it is each current when
It is handled as follows at quarter until the L moment:
The survivor path of the current time each state of corresponding subsequent time is obtained,
Obtain the instantaneous phase value of the current time corresponding subsequent time；And
For the l-th moment, the smallest survivor path of path metric value is selected to be recalled, obtained closest to the coding
The sequence of output sequence.
It is appreciated that the first memory 602 and second memory 606 in the embodiment of the present invention can be volatile storage
Device or nonvolatile memory, or may include both volatile and non-volatile memories.Wherein, nonvolatile memory can be with
Be read-only memory (Read-Only Memory, ROM), programmable read only memory (Programmable ROM, PROM), can
Erasable programmable read-only memory (EPROM) (Erasable PROM, EPROM), electrically erasable programmable read-only memory
(Electrically EPROM, EEPROM) or flash memory.Volatile memory can be random access memory (Random
Access Memory, RAM), it is used as External Cache.By exemplary but be not restricted explanation, many forms
RAM is available, such as static random access memory (Static RAM, SRAM), dynamic random access memory (Dynamic
RAM, DRAM), Synchronous Dynamic Random Access Memory (Synchronous DRAM, SDRAM), Double Data Rate synchronous dynamic
Random access memory (Double Data Rate SDRAM, DDRSDRAM), enhanced Synchronous Dynamic Random Access Memory
(Enhanced SDRAM, ESDRAM), synchronized links dynamic random access memory (Synchlink DRAM, SLDRAM) and straight
Meet rambus random access memory (Direct Rambus RAM, DRRAM).The first of system and method described herein
Memory 602 and second memory 606 are intended to include but are not limited to the memory of these and any other suitable type.
And first processor 603 and second processor 607 may be a kind of IC chip, the processing energy with signal
Power.During realization, each step of the above method can pass through the hardware in first processor 603 and second processor 607
Integrated logic circuit or software form instruction complete.Above-mentioned first processor 603 and second processor 607 can be
General processor, digital signal processor (Digital Signal Processor, DSP), specific integrated circuit
(Application Specific Integrated Circuit, ASIC), ready-made programmable gate array (Field
Programmable Gate Array, FPGA) either other programmable logic device, discrete gate or transistor logic,
Discrete hardware components.It may be implemented or execute disclosed each method, step and the logic diagram in the embodiment of the present invention.It is general
Processor can be microprocessor or the processor is also possible to any conventional processor etc..In conjunction with institute of the embodiment of the present invention
The step of disclosed method, can be embodied directly in hardware decoding processor and execute completion, or with the hardware in decoding processor
And software module combination executes completion.Software module can be located at random access memory, and flash memory, read-only memory may be programmed read-only
In the storage medium of this fields such as memory or electrically erasable programmable memory, register maturation.The storage medium is located at
First memory 602 and second memory 606, first processor 603 and second processor 607 read 602 He of first memory
Information in second memory 606, in conjunction with the step of its hardware completion above method.
It is understood that embodiments described herein can with hardware, software, firmware, middleware, microcode or its
Combination is to realize.For hardware realization, processing unit be may be implemented in one or more specific integrated circuit (Application
Specific Integrated Circuits, ASIC), digital signal processor (Digital Signal Processing,
DSP), digital signal processing appts (DSP Device, DSPD), programmable logic device (Programmable Logic
Device, PLD), field programmable gate array (Field-Programmable Gate Array, FPGA), general processor,
In controller, microcontroller, microprocessor, other electronic units for executing herein described function or combinations thereof.
For software implementations, it can be realized herein by executing the module (such as process, function etc.) of function described herein
The technology.Software code is storable in memory and is executed by processor.Memory can in the processor or
It is realized outside processor.
Specifically, it is right when first processor 603 and second processor 607 are additionally configured to run the computer program
Step performed by transmitting terminal and receiving end in technical solution shown in earlier figures 2 should be executed, is not discussed here.
Embodiment three
The system of method and/or carrier synchronization based on carrier synchronization documented by previous embodiment, the present embodiment pass through
Specific simulation example verifies technical solution documented by previous embodiment.
In this simulation example, simulated conditions and content are as follows:
Simulation analysis comparison is carried out to previous embodiment and existing carrier track algorithm with Matlab.Simulation parameter setting
As follows: general communication signal, QPSK modulation, the convolution coding that code rate is 1/2, code length 1000, cycle-index are
100000, SNR ranges are between 2dB~8dB.Specific emulation content is as follows:
A. for simulation analysis previous embodiment when normalizing Doppler shift is zero, error rate of system performance is more with normalizing
General Le change rate change curve, parameter setting are normalization Doppler frequency △ fT=0, and normalization Doppler-shift rate takes respectively
△aT2=10-4, △ aT2=2 × 10-4, △ aT2=3 × 10-4, △ aT2=4 × 10-4, △ aT2=5 × 10-4。
B. for simulation analysis previous embodiment when normalizing doppler changing rate is zero, error rate of system performance is with normalization
Doppler shift change curve, parameter setting are normalization Doppler-shift rate △ aT2=0, normalization Doppler shift difference
Take fT=1 × 10 △-3, fT=2 × 10 △-3, fT=4 × 10 △-3, fT=6 × 10 △-3, fT=8 × 10 △-3。
C. carrier synchronization method and existing carrier synchronization method bit error rate performance that simulation analysis previous embodiment proposes.
Parameter setting is normalization fT=1 × 10 Doppler shift △-3, normalize doppler changing rate △ aT2=10-4。
It specific simulation result and is analyzed as follows:
A. referring to Fig. 7, abscissa indicates that SNR ranges, ordinate indicate error rate of system, it can be seen that works as normalization
When Doppler shift is zero, the bit error rate performance for the carrier synchronization method that previous embodiment proposes is with normalization Doppler's variation
The increase of rate and be deteriorated, that is to say when normalization doppler changing rate be greater than 4 × 10-3When, loop tracks are easy losing lock, so with
Track can newly deteriorate.
B. referring to Fig. 8, abscissa indicates that SNR ranges, ordinate indicate error rate of system, it can be seen that works as normalization
When doppler changing rate is zero, the bit error rate performance for the carrier synchronization method that previous embodiment proposes is with normalization Doppler's frequency
Inclined increase and be deteriorated, that is to say when normalize Doppler shift be greater than when, Doppler shift has been more than the loop band of phaselocked loop
Width, so tracking performance deteriorates.
C. referring to Fig. 9, abscissa indicates that SNR ranges, ordinate indicate error rate of system, the symbol M MSE in figure
PLL indicates that traditional MMSE algorithm assists the carrier wave tracing method of single phaselocked loop, and ML PLL indicates that traditional maximum likelihood is estimated
Meter assists the carrier wave tracing method of single phaselocked loop, and MMSE PSP indicates the carrier synchronization method that previous embodiment proposes, QPSK
The theoretical ber curve of IDEL expression QPSK signal.The carrier synchronization method error code that previous embodiment proposes as can be seen from Fig.
Rate curve always situated in conventional method ber curve under, and work as the bit error rate 10-5When, method proposed by the present invention is than tradition side
Method signal-to-noise ratio improves 4dB.It can be seen that the carrier synchronization method that previous embodiment proposes is substantially better than conventional method.
It should be understood that between technical solution documented by the embodiment of the present invention, in the absence of conflict, Ke Yiren
Meaning combination.
The above description is merely a specific embodiment, but scope of protection of the present invention is not limited thereto, any
Those familiar with the art in the technical scope disclosed by the present invention, can easily think of the change or the replacement, and should all contain
Lid is within protection scope of the present invention.Therefore, protection scope of the present invention should be based on the protection scope of the described claims.
Claims (10)
1. a kind of method of carrier synchronization, which is characterized in that the described method includes:
The single bit of information of input is carried out the convolution coding that code rate is 1/2 by transmitting terminal, is obtained the coding that length is L and is exported sequence
Column；
The encoded output sequence is modulated obtained length as L+N's according to the modulation strategy set by the transmitting terminal
Modulation data；
Receiving end is according to the Doppler shift for receiving carrier wave in pilot signal described in the Instantaneous phase estimation of pilot signal in signal
With the doppler changing rate of carrier wave；
The receiving end is according to carrier wave in the Doppler shift estimated value and the pilot signal of carrier wave in the pilot signal
Doppler changing rate estimated value compensates the reception signal, obtains compensated signal；
The receiving end carries out Viterbi Viterbi decoding to the compensated signal, and during decoding, for each
Current time is handled as follows until the L moment:
The survivor path of the current time each state of corresponding subsequent time is obtained,
Obtain the instantaneous phase value of the current time corresponding subsequent time；
For the l-th moment, the receiving end selection the smallest survivor path of path metric value is recalled, and is obtained closest to institute
State the sequence of encoded output sequence.
2. the method according to claim 1, wherein the receiving end is according to the wink for receiving pilot signal in signal
When phase estimation described in the Doppler shift of carrier wave and the doppler changing rate of carrier wave in pilot signal, comprising:
The pilot signal for receiving signal is extracted in the receiving end, obtains the instantaneous phase of the pilot signal；
For the instantaneous phase of the pilot signal, the pilot signal is estimated according to minimum mean square error criterion in the receiving end
The Doppler shift of middle carrier wave and the doppler changing rate of carrier wave obtain the Doppler shift estimation of carrier wave in the pilot signal
The doppler changing rate estimated value of value and carrier wave.
3. according to the method described in claim 2, it is characterized in that, the pilot signal of receiving end extraction reception signal, is obtained
Obtain the instantaneous phase of the pilot signal, comprising:
The receiving end is to the reception signalTop n data carry out -1/4 π phase rotation
Turn, the pilot signal after obtaining phase rotation；Wherein, ckIndicate the modulated signal of energy normalized；The week of T expression symbol
Phase；nkIndicate the introduced zero-mean complex Gaussian white noise of communication channel, in-phase component is mutually indepedent with quadrature component, variance
It is N for mean value0/2；△ fT indicates unknown normalization carrier Doppler frequency offset；△aT2Indicate unknown normalization carrier wave
Doppler changing rate offset；
The receiving end carries out calculus of differences according to formula 1 to the pilot signal after the phase rotation, obtains the pilot signal
Instantaneous phase；
rk+1e-π/4*conj(rke-π/4) (1)
Wherein, conj (rke-π/4) indicate rke-π/4Complex conjugate.
4. according to the method described in claim 2, it is characterized in that, the instantaneous phase for the pilot signal, described
Estimate that the Doppler of the Doppler shift of carrier wave and carrier wave becomes in the pilot signal according to minimum mean square error criterion in receiving end
Rate obtains the Doppler shift estimated value of carrier wave in the pilot signal and the doppler changing rate estimated value of carrier wave, comprising:
For the instantaneous phase of the pilot signal, estimated using the Doppler shift that formula 2 obtains carrier wave in the pilot signal
Value and the doppler changing rate estimated value of carrier wave in the pilot signal is obtained using formula 3:
Wherein,For instantaneous phase, design factor αN, βN, γNIt respectively indicates as follows:βN=(2N+1) (8N+11), γN=(N+1) (N+2).
5. the method according to claim 1, wherein the receiving end according in the pilot signal carrier wave it is more
The general doppler changing rate estimated value for strangling carrier wave in offset estimation value and the pilot signal compensates the reception signal,
Obtain compensated signal, comprising:
Pass through compensation formulaThe reception signal is compensated, compensated signal is obtained.
6. the method according to claim 1, wherein the acquisition current time corresponding subsequent time is every
The survivor path of a state, comprising:
Setting sequence ..., ck-3,ck-2,ck-1It is expressed as transmission information sequence until current time kT, Sk∈{0,1,...,
Q-1 } it is expressed as the state node set at current time, it altogether include Q node；
SettingIt is expressed as entering the information sequence of m node from certain survivor path, obtain from current time
M node to subsequent time some node branch measurement be
According to the branched measurement value of each stateObtain stateful to subsequent time path metric since decoding
Value
A smallest value is selected from the path metric value of each state, other route deletions are obtained to subsequent time
Until stateful survivor path.
7. the method according to claim 1, wherein current time corresponding subsequent time of obtaining
Instantaneous phase value, comprising:
The phase pushing figure at the current time is determined as
By the phase pushing figure after third order pll, the instantaneous phase value of subsequent time is obtainedWherein, under
The instantaneous phase value calculation formula at one moment indicates are as follows:γ is third order pll gain.
8. the method according to claim 1, wherein the single bit of information of input is carried out code rate by the transmitting terminal
For 1/2 convolution coding, encoded output sequence is obtained, comprising:
The convolution coding that code rate is 1/2 is carried out to the single bit of information of the input, obtains dibit coded sequence；Wherein,
The dibit coded sequence length is L, and the output expression formula of the dibit coded sequence is respectively g1(x)=1+x+x2With
g2(x)=1+x2, wherein x indicates the time lag of first order of the single bit of information of the input, x2Indicate the single bit of information of the input
Secondary delay.
9. a kind of system of carrier synchronization, which is characterized in that the system comprises transmitting terminals and receiving end；
The transmitting terminal includes the first communication interface, first memory and first processor；Wherein,
First communication interface, during for being received and sent messages between other ext nal network elements, the reception of signal and
It sends；
The first memory, for storing the computer program that can be run on the first processor；
The first processor, for executing following steps when running the computer program:
The single bit of information of input is subjected to the convolution coding that code rate is 1/2, obtains the encoded output sequence that length is L；With
And the encoded output sequence is modulated obtained length as the modulation data of L+N according to the modulation strategy set；
The receiving end includes: the second communication interface, second memory and second processor；
Wherein, second communication interface, during for being received and sent messages between other ext nal network elements, signal is connect
It receives and sends；
The second memory, for storing the computer program that can be run in second processor；
The second processor, for executing following steps when running the computer program:
According to the Doppler shift and carrier wave for receiving carrier wave in pilot signal described in the Instantaneous phase estimation of pilot signal in signal
Doppler changing rate；And
According to Doppler's variation of carrier wave in the Doppler shift estimated value and the pilot signal of carrier wave in the pilot signal
Rate estimated value compensates the reception signal, obtains compensated signal；And
Viterbi Viterbi decoding is carried out to the compensated signal, and during decoding, for each current time into
The following processing of row is until the L moment:
The survivor path of the current time each state of corresponding subsequent time is obtained,
Obtain the instantaneous phase value of the current time corresponding subsequent time；And
For the l-th moment, the smallest survivor path of path metric value is selected to be recalled, obtains and exported closest to the coding
The sequence of sequence.
10. system according to claim 9, which is characterized in that the second processor is also used to running the calculating
When machine program, perform claim requires 2 to 7 described in any item steps；
The first processor is also used to when running the computer program, step described in perform claim requirement 8.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201910020334.8A CN109617844B (en) | 2019-01-09 | 2019-01-09 | Carrier synchronization method and system |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201910020334.8A CN109617844B (en) | 2019-01-09 | 2019-01-09 | Carrier synchronization method and system |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN109617844A true CN109617844A (en) | 2019-04-12 |
| CN109617844B CN109617844B (en) | 2020-08-07 |
Family
ID=66018382
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201910020334.8A Active CN109617844B (en) | 2019-01-09 | 2019-01-09 | Carrier synchronization method and system |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN109617844B (en) |
Cited By (9)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110768919A (en) * | 2019-09-11 | 2020-02-07 | 武汉船舶通信研究所（中国船舶重工集团公司第七二二研究所） | Carrier synchronization method and device for satellite communication system |
| CN111510411A (en) * | 2019-11-25 | 2020-08-07 | 南京中科晶上通信技术有限公司 | Carrier phase synchronization processing method, device, terminal and storage medium |
| CN111600628A (en) * | 2020-05-12 | 2020-08-28 | 北京理工大学 | Self-adaptive filtering narrow-band interference suppression method with Doppler first-order change rate |
| CN111624402A (en) * | 2020-05-31 | 2020-09-04 | 西南电子技术研究所（中国电子科技集团公司第十研究所） | Method for accurately estimating carrier frequency of weak PM signal |
| CN113055327A (en) * | 2019-12-26 | 2021-06-29 | 鹤壁天海电子信息***有限公司 | Signal demodulation method and device and signal demodulator |
| CN113721270A (en) * | 2021-07-28 | 2021-11-30 | 江苏师范大学 | Satellite signal carrier synchronization method and system |
| CN113852581A (en) * | 2021-09-16 | 2021-12-28 | 电子科技大学 | Phase noise estimation and elimination method for single carrier THP-FTN system |
| CN114189417A (en) * | 2021-12-07 | 2022-03-15 | 北京零壹空间电子有限公司 | Carrier frequency synchronization method and device, computer equipment and storage medium |
| CN116155668A (en) * | 2023-04-20 | 2023-05-23 | 北京中天星控科技开发有限公司 | Anti-frequency offset carrier recovery method, system and storage medium |
Citations (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1367591A (en) * | 2002-02-26 | 2002-09-04 | 东南大学 | Ruike and equalization cascade receiving method under the code division multiple address low band-spreading ratio and its equipment |
| CN1494794A (en) * | 2001-01-19 | 2004-05-05 | �����ɷ� | Frequency searcher and frequency-locked data demodulator using programmable rotor |
| US20060285482A1 (en) * | 2005-06-21 | 2006-12-21 | Hideo Kasami | OFDM demodulation apparatus, method and computer readable medium |
| CN101692661A (en) * | 2009-10-19 | 2010-04-07 | 上海奇微通讯技术有限公司 | High-efficient differential interference rejection circuit and high-efficient differential interference rejection method |
| CN101984562A (en) * | 2010-11-09 | 2011-03-09 | 大连工业大学 | Narrow-band signal gain estimation method |
| CN105763500A (en) * | 2014-12-20 | 2016-07-13 | 西安飞东电子科技有限责任公司 | Frequency deviation, time delay and phase deviation combined synchronization method of continuous phase modulation signals |
-
2019
- 2019-01-09 CN CN201910020334.8A patent/CN109617844B/en active Active
Patent Citations (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1494794A (en) * | 2001-01-19 | 2004-05-05 | �����ɷ� | Frequency searcher and frequency-locked data demodulator using programmable rotor |
| CN1367591A (en) * | 2002-02-26 | 2002-09-04 | 东南大学 | Ruike and equalization cascade receiving method under the code division multiple address low band-spreading ratio and its equipment |
| US20060285482A1 (en) * | 2005-06-21 | 2006-12-21 | Hideo Kasami | OFDM demodulation apparatus, method and computer readable medium |
| CN101692661A (en) * | 2009-10-19 | 2010-04-07 | 上海奇微通讯技术有限公司 | High-efficient differential interference rejection circuit and high-efficient differential interference rejection method |
| CN101984562A (en) * | 2010-11-09 | 2011-03-09 | 大连工业大学 | Narrow-band signal gain estimation method |
| CN105763500A (en) * | 2014-12-20 | 2016-07-13 | 西安飞东电子科技有限责任公司 | Frequency deviation, time delay and phase deviation combined synchronization method of continuous phase modulation signals |
Non-Patent Citations (1)
| Title |
|---|
| JIANGBO SI: "Carrier synchronisation for multiple symbol Trellis-coded CPFSK in burst-mode transmission", 《IET COMMUNICATIONS》 * |
Cited By (15)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110768919B (en) * | 2019-09-11 | 2022-09-16 | 武汉船舶通信研究所（中国船舶重工集团公司第七二二研究所） | Carrier synchronization method and device for satellite communication system |
| CN110768919A (en) * | 2019-09-11 | 2020-02-07 | 武汉船舶通信研究所（中国船舶重工集团公司第七二二研究所） | Carrier synchronization method and device for satellite communication system |
| CN111510411A (en) * | 2019-11-25 | 2020-08-07 | 南京中科晶上通信技术有限公司 | Carrier phase synchronization processing method, device, terminal and storage medium |
| CN111510411B (en) * | 2019-11-25 | 2023-05-30 | 南京中科晶上通信技术有限公司 | Carrier phase synchronization processing method, device, terminal and storage medium |
| CN113055327A (en) * | 2019-12-26 | 2021-06-29 | 鹤壁天海电子信息***有限公司 | Signal demodulation method and device and signal demodulator |
| CN113055327B (en) * | 2019-12-26 | 2022-11-29 | 鹤壁天海电子信息***有限公司 | Signal demodulation method and device and signal demodulator |
| CN111600628A (en) * | 2020-05-12 | 2020-08-28 | 北京理工大学 | Self-adaptive filtering narrow-band interference suppression method with Doppler first-order change rate |
| CN111624402A (en) * | 2020-05-31 | 2020-09-04 | 西南电子技术研究所（中国电子科技集团公司第十研究所） | Method for accurately estimating carrier frequency of weak PM signal |
| CN111624402B (en) * | 2020-05-31 | 2022-09-02 | 西南电子技术研究所（中国电子科技集团公司第十研究所） | Method for accurately estimating carrier frequency of weak PM signal |
| CN113721270A (en) * | 2021-07-28 | 2021-11-30 | 江苏师范大学 | Satellite signal carrier synchronization method and system |
| CN113852581A (en) * | 2021-09-16 | 2021-12-28 | 电子科技大学 | Phase noise estimation and elimination method for single carrier THP-FTN system |
| CN114189417A (en) * | 2021-12-07 | 2022-03-15 | 北京零壹空间电子有限公司 | Carrier frequency synchronization method and device, computer equipment and storage medium |
| CN114189417B (en) * | 2021-12-07 | 2023-10-17 | 北京零壹空间电子有限公司 | Carrier frequency synchronization method, carrier frequency synchronization device, computer equipment and storage medium |
| CN116155668A (en) * | 2023-04-20 | 2023-05-23 | 北京中天星控科技开发有限公司 | Anti-frequency offset carrier recovery method, system and storage medium |
| CN116155668B (en) * | 2023-04-20 | 2023-07-14 | 北京中天星控科技开发有限公司 | Anti-frequency offset carrier recovery method, system and storage medium |
Also Published As
| Publication number | Publication date |
|---|---|
| CN109617844B (en) | 2020-08-07 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN109617844A (en) | A kind of method and system of carrier synchronization | |
| Morelli et al. | Feedforward frequency estimation for PSK: A tutorial review | |
| JP3100447B2 (en) | Adaptive equalizer and receiver | |
| US6266361B1 (en) | Method and architecture for correcting carrier frequency offset and spreading code timing offset in a direct sequence spread spectrum communication system | |
| US5311523A (en) | Carrier phase synchronous type maximum likelihood decoder | |
| US9461773B2 (en) | Method and a node for detecting phase noise in MIMO communication systems | |
| US20170180171A1 (en) | Frequency synchronization of convolutionally coded gfsk signals | |
| US11073545B2 (en) | Kalman filter for phase noise tracking | |
| CN105763500A (en) | Frequency deviation, time delay and phase deviation combined synchronization method of continuous phase modulation signals | |
| De Gaudenzi et al. | Analysis and design of an all-digital demodulator for trellis coded 16-QAM transmission over a nonlinear satellite channel | |
| US20010046270A1 (en) | Adaptive array communication system and receiver | |
| JP3206574B2 (en) | Signal estimation device and storage medium storing program | |
| US20050111603A1 (en) | Process for providing a pilot aided phase synchronization of carrier | |
| US7366256B2 (en) | Method and modem for phase synchronization and tracking | |
| US7042925B2 (en) | Correlation detection improvement by averaging spread spectrum signals | |
| CN101404633A (en) | Carrier wave tracing method for single carrier system based on block transmission | |
| CN105262505B (en) | Signal-noise ratio estimation method under frequency hopping communications disturbed condition | |
| Giugno et al. | Carrier frequency and frequency rate-of-change estimators with preamble-postamble pilot symbol distribution | |
| CN111654308A (en) | Precision frequency offset estimation method for burst spread spectrum weak signal | |
| US8811546B2 (en) | Adaptive reference symbol method and apparatus for a receiver | |
| CN115632923A (en) | OQPSK (offset quadrature phase shift keying) -based unmanned aerial vehicle and satellite ultra-wideband communication method and related equipment | |
| WO2004019579A1 (en) | Noise-adaptive decoding | |
| JP4970283B2 (en) | High memory efficiency sliding window addition | |
| Yang et al. | Smoothing PLLs for QAM dynamical phase estimation | |
| Lang et al. | Blind joint timing and carrier phase estimation in burst-type CPM |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |