CN109239678A - A kind of portable high frequency groundwave radar radio frequency interference suppressing method - Google Patents
A kind of portable high frequency groundwave radar radio frequency interference suppressing method Download PDFInfo
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
- G01S7/28—Details of pulse systems
- G01S7/285—Receivers
- G01S7/292—Extracting wanted echo-signals
- G01S7/2923—Extracting wanted echo-signals based on data belonging to a number of consecutive radar periods
- G01S7/2927—Extracting wanted echo-signals based on data belonging to a number of consecutive radar periods by deriving and controlling a threshold value
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
- G01S7/35—Details of non-pulse systems
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- G01S7/354—Extracting wanted echo-signals
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Abstract
The invention proposes a kind of portable high frequency groundwave radar radio frequency interference suppressing methods.The present invention is divided by radar return data, obtains the single order peak region of radar return, and the target echo data in associative array normal direction realize the calibration of radar return data；Radar return data after smothing filtering are obtained according to radar return data after calibration, by radar return data after smothing filtering and thresholding multilevel iudge with the presence or absence of jump, and further judge whether this radar return data are disturbed；Intersect the array manifold in six channel of loop antenna by monopole and radar return data after calibration carry out six channel datas and synthesize, six channel datas after synthesis are constantly changed into beam position, the maximum beam position of signal interference ratio is selected as wave beam by detection signal interference ratio and is eventually pointed to；Angle is carried out according to the maximum beam position of signal interference ratio to adjust to obtain the data of three Beam Domains, and the super-resolution Direction-of-arrival of Beam Domain is realized according to Beam Domain multiple signal classification algorithm.
Description
Technical Field
The invention belongs to the technical field of radar signal processing, and particularly relates to a portable high-frequency ground wave radar radio frequency interference suppression method.
Background
The high-frequency ground wave radar is effective sea state monitoring equipment, has the characteristics of large area, all weather, strong real-time property, high resolution, high reliability and the like, and is widely applied to detection of near-sea wind, wave, flow and low-altitude targets. The portable high-frequency ground wave radar adopts the monopole crossed loop antenna as a receiving sensor, has the characteristics of small occupied area, convenience in erection and maintenance and the like under the condition of not losing measurement precision, and is the widest radar system occupying the market. However, the high frequency band is an open radio frequency band, and a large number of radio devices operate in the high frequency band, so that the electromagnetic environment in which the radar operates is very poor. Severe radio frequency interference can not only overwhelm ocean echoes, but can also make target detection more difficult, thereby reducing radar performance in several ways. Therefore, radio frequency interference has become one of the important factors that restrict the performance of high frequency ground wave radar.
The suppression of radio frequency interference is particularly important in order to ensure the operational performance of the radar. For a large phased array, the methods of adaptive beam forming, sidelobe cancellation, polarization filtering and the like can effectively realize interference suppression, and higher angle estimation accuracy can still be obtained after suppression. However, for a portable high-frequency ground wave radar using a single monopole cross-loop antenna or a plurality of monopole cross-loop antennas as receiving sensors, the antenna beam is wide, so that the arrival angle estimation algorithm based on beam forming cannot meet the requirement of spatial resolution, and the null point provided by antenna beam forming is limited, so that the method commonly used for large arrays is not applicable. The algorithm based on subspace projection can improve the suppression effect to a certain extent, and can obtain higher angle estimation accuracy by combining with a super-resolution algorithm. However, the estimation accuracy of the interference subspace directly affects the interference suppression effect, and the large amount of subspace calculation greatly increases the amount of calculation.
Therefore, an interference suppression algorithm suitable for a portable high-frequency ground wave radar, capable of avoiding the estimation of an interference subspace, having higher estimation angle precision, and reducing the calculation amount is urgently needed. It is known that the monopole cross-loop antenna can form deep nulls although the beam width is wide, and the nulls are just 180 ° away from the main beam direction, so that the beam nulls can be used for interference suppression.
Disclosure of Invention
The invention aims to provide a radio frequency interference suppression algorithm of a portable high-frequency ground wave radar, so that the data quality of the radar is optimized, and the performance of the radar in the aspects of oceanographic parameter detection and target detection is improved.
The technical scheme of the invention is as follows:
a portable high-frequency ground wave radar radio frequency interference suppression method comprises the following steps:
step 1: dividing a first-order peak area of radar echo through radar echo data, calculating the calibration values of the amplitude and the phase between three channels of the monopole crossed loop antenna in the first-order peak area of the radar echo, and further calculating the calibration values of the amplitude and the phase between monopoles according to a target echo to obtain calibrated radar echo data;
step 2: obtaining radar echo data formed by logarithm according to the calibrated radar echo data obtained in the step 1, selecting radar echo data formed by long-distance logarithm to carry out smooth filtering to obtain radar echo data after smooth filtering, comparing the radar echo data after smooth filtering with a threshold to judge whether jumping exists, and further judging whether the radar echo data of the field is interfered;
and step 3: carrying out six-channel data synthesis through an array flow pattern of six channels of the monopole crossed loop antenna and calibrated radar echo data, continuously changing beam pointing of the synthesized six-channel data, and selecting the beam pointing with the largest signal-to-interference ratio as the final pointing of a beam by detecting the signal-to-interference ratio;
and 4, step 4: adjusting the angle of the beam direction with the maximum signal-to-interference ratio in the step 3 to obtain data of a three-field beam domain, and further realizing super-resolution signal arrival angle estimation of the beam domain according to a beam domain multiple signal classification algorithm;
preferably, the radar echo data in step 1 is expressed as:
[xk，1(n，d)，xk，2(n，d)，xk，3(n，d)]k∈[1，2]n∈[1，N]d∈[l，D]
wherein,k denotes the monopole cross-loop antenna serial number, N denotes the number of radar echo points in frequency, D denotes the number of radar echo points in distance, xk,1(n, d) denotes radar echo data of a monopole channel of a kth monopole cross-loop antenna, xk,2(n, d) denotes radar echo data of a-ring in the k-th monopole cross-loop antenna, xk,3(n, d) denotes radar echo data of b-loop in the kth monopole crossed-loop antenna;
the first-order peak area of the radar echo in the step 1 is obtained by adopting a difference spectrum method:
will return radar [ x ]k,1(n,d),xk,2(n,d),xk,3(n,d)]Inputting the data into a difference spectrum algorithm, and calculating to obtain a first-order peak area of the radar echo as follows:
wherein k represents the serial number of the monopole cross-loop antenna, M represents the point number of the first-order peak echo,data representing a first-order peak region of a monopole channel of a kth monopole cross-loop antenna,data representing the first-order peak region of the a-loop in the kth monopole cross-loop antenna,data representing the first-order peak region of the b-loop in the kth monopole cross-loop antenna.
Radar echo at first order peakRespectively calculating the first-order peak amplitude of the radar echo by a modulus method, averaging the calculated amplitudes to obtain the average value of the first-order peak amplitudes, wherein the average value is as follows:
[ampk,1,ampk,2,ampk,3]k∈[1,2]
wherein ,ampk,1Represents the average, amp, of the amplitudes of the monopole channels of the kth monopole cross-loop antennak,2Represents the average value, amp, of the amplitude of the a-loop in the kth monopole crossed-loop antennak,3Represents an average value of the amplitude of the b-loop in the kth monopole cross-loop antenna;
calculating the phase by the method of solving the argument, and averaging all the phases to obtain the average value of the first-order peak phases, which is:
[phasek,1,phasek,2,phasek,3]k∈[1,2]
wherein, phasek,1Represents the average value, phase, of the phases of the monopole channels of the kth monopole cross-loop antennak,2Represents the average value of the phase of the a-loop in the kth monopole crossed-loop antenna, phasek,3Represents an average value of the phase of the b-loop in the kth monopole crossed-loop antenna;
the amplitude calibration value is:
Ak＝[ampk,2/ampk,1,ampk,3/ampk,1]k∈[1,2]
wherein ,ampk,2/ampk,1I.e. amplitude calibration value, amp, of the a-loop in the kth monopole cross-loop antennak,3/ampk,1Namely the amplitude calibration value of the b-loop in the kth monopole crossed-loop antenna;
the phase calibration value is:
PHk＝[phasek,2-phasek,1,phasek,3-phasek,1]k∈[1,2]
wherein, phasek,2-phasek,1I.e. phase calibration value, phase of the a-loop in the kth monopole cross-loop antennak,3-phasek,1I.e. the kth monopole crossbar ringPhase calibration value of b-loop in antenna;
the calibration value is compensated to obtain calibrated radar echo data of two rings:
x′k,1(n,d)＝xk,1(n,d)
wherein ,x′k,1(n, d) denotes radar echo data, x 'of a monopole channel of the kth monopole cross-loop antenna after calibration'k,2(n, d) denotes radar echo data of a-ring in the kth monopole cross-ring antenna after calibration, x'k,3(n, d) represents the radar echo data of the b-ring in the k-th monopole cross-ring antenna after calibration;
for calibration between monopoles:
taking target data normal to the radar antenna, the target data can be expressed as:
[x1,1(p),x2,1(p)]p∈[1,Q]
wherein Q represents the number of target data points in the normal direction of the radar antenna, x1,1(p) target data for a monopole channel in the first monopole cross-loop antenna, x2,1(p) target data representing a monopole channel in a second monopole cross-loop antenna;
target data [ x ] in the normal direction of the radar antenna1,1(p),x2,1(p)]In the method, the amplitude of radar target echoes is respectively calculated by a mode taking method, and the average value of the target amplitude is obtained by averaging the obtained amplitudes, wherein the average value is as follows:
[amp1,1,amp2,1]
wherein ,amp1,1Representing the average value, amp, of the amplitude of the target signal on the monopole channel of the first monopole cross-loop antenna2,1An average of the amplitudes of the target signal in the monopole channel representing the second monopole cross-loop antenna;
calculating the phase by a method of solving the argument, and obtaining the average value of the target phase by averaging the obtained phases, wherein the average value is as follows:
[phase1,1,phase2,1]
wherein, phase1,1Representing the average value, phase, of the phase of the target signal in the monopole channel of the first monopole cross-loop antenna2,1An average value representing the phase of the target signal on the monopole channel of the second monopole cross-loop antenna;
the amplitude calibration value is:
A′＝[amp2,1/amp1,1]
wherein ,amp2,1/amp1,1I.e., amplitude calibration values for the monopole channels in the second monopole cross-loop antenna.
The phase calibration value is:
PH′＝[phase2,1-phase1,1]
wherein, phase2,1-phase1,1Namely the phase calibration value of a monopole channel in the second monopole crossed loop antenna;
the calibration value is compensated to the calibrated radar echo data of the second monopole channel:
x′1,1(n,d)＝x1,1(n,d)
x′2,1(n,d)＝x2,1(n,d)/A′*ejPH′
wherein ,x′1,1(n, d) is the monopole channel of the first monopole cross-loop antenna after calibrationOf radar echo data of x'2,1(n, d) are the radar echo data of the monopole channel of the second monopole cross-loop antenna after calibration;
step 1 the calibrated radar echo data is expressed as:
[x′k,1(n,d),x′k,2(n,d),x′k,3(n,d)]k∈[1,2]n∈[1,N]d∈[1,D]
wherein k denotes a monopole cross-loop antenna number, N denotes the number of points of radar echo in frequency, and D denotes the number of points of radar echo in distance, x'k,1(n, d) denotes radar echo data, x 'of a monopole channel of the kth monopole cross-loop antenna after calibration'k,2(n, d) represents a-ring radar echo data x 'in the k-th monopole crossed-ring antenna after calibration'k,3(n, d) represents the radar echo data of the b-ring in the k-th monopole cross-ring antenna after calibration;
preferably, the logarithm of step 2 forms radar echo data as:
calibrating the post-radar echo data [ x'k,1(n,d),x′k,2(n,d),x′k,3(n,d)]Taking logarithm to obtain radar echo data formed by logarithm:
Pk,l(n,d)＝10log[x′k,l(n,d)]l∈[1,3]k∈[1,2]n∈[1,N]d∈[1,D]
wherein k denotes a monopole cross-loop antenna number, N denotes the number of points of radar echo in frequency, D denotes the number of points of radar echo in distance, l denotes an antenna number of 3-channel monopole cross-loop antenna, x'k,1(n, d) denotes radar echo data, x 'of a monopole channel of the kth monopole cross-loop antenna after calibration'k,2(n, d) denotes radar echo data of a-ring in the kth monopole cross-ring antenna after calibration, x'k,3(n, d) represents the radar echo data of the b-ring in the k-th monopole cross-ring antenna after calibration;
the radar echo data after smoothing filtering in the step 2 is calculated in the following process:
logarithmic formed radar echo data Pk,lIn (n, d), a long-distance element d is selected as [ d ∈ [1,d2]Radar echo data Pk,l(n,d′)d′∈[d1,d2]Smoothing filtering in the doppler dimension:
wherein ,for smooth filtered spectra, Pk,l(N, d') is long-distance radar echo data, and N is the point number of Doppler frequency;
the detailed process of judging whether the jump signal is contained in the step 2 is as follows:
getLeftmost and rightmost N inSPoint weighting to obtain noise floor:
judgment ofIf there is a signal α higher than NOISE floor NOISE, if there is a signal, it is considered that there is a jump;
the detailed process for judging whether the field radar echo data is interfered in the step 2 comprises the following steps:
if calibrated radar echo data x'k,1(n,d),x′k,2(n,d),x′k,3(n,d)]If four channel data contain hopping signals, the field radar echo data are interfered;
preferably, the array flow pattern of the monopole cross-loop antenna six-channel in step 3 is as follows:
wherein theta is a beam direction, AI [1] in the vector AI represents a weighting factor of a monopole channel of the first monopole cross-loop antenna, AI [2] represents a weighting factor of an a-loop in the first monopole cross-loop antenna, AI [3] represents a weighting factor of a b-loop in the first monopole cross-loop antenna, AI [4] represents a weighting factor of a monopole channel of the second monopole cross-loop antenna, AI [5] represents a weighting factor of an a-loop in the second monopole cross-loop antenna, and AI [6] represents a weighting factor of a b-loop in the second monopole cross-loop antenna;
in step 3, the calibrated radar echo data are:
X＝[x′1,1(n,d),x′1,2(n,d),x′1,3(n,d),x′2,1(n,d),x′2,2(n,d),x′2,3(n,d)]T
wherein T represents transpose of matrix, x'1,1(n, d) denotes radar echo data, x 'of the monopole channel of the first monopole cross-loop antenna after calibration'1,2(n, d) represents radar echo data of a ring in the first monopole crossed-ring antenna after calibration, x'1,3(n, d) represents radar echo data of a b-loop in the first monopole crossed-loop antenna after calibration, x'2,1(n, d) denotes radar echo data, x 'of the monopole channel of the second monopole cross-loop antenna after calibration'2,2(n, d) denotes the radar echo data of the a-ring in the calibrated second monopole crossed-loop antenna, x'2,3(n, d) denotes the second monopole crossed-loop antenna after calibrationRadar echo data of ring b;
and step 3, synthesizing the six-channel data:
wherein theta is the direction of the beam, x'1,1(n, d) denotes radar echo data, x 'of the monopole channel of the first monopole cross-loop antenna after calibration'1,2(n, d) represents radar echo data of a ring in the first monopole crossed-ring antenna after calibration, x'1,3(n, d) represents radar echo data of a b-loop in the first monopole crossed-loop antenna after calibration, x'2,1(n, d) denotes radar echo data, x 'of the monopole channel of the second monopole cross-loop antenna after calibration'2,2(n, d) denotes the radar echo data of the a-ring in the calibrated second monopole crossed-loop antenna, x'2,3(n, d) represents the radar echo data of the b-loop in the second monopole crossed-loop antenna after calibration;
in step 3, the beam direction with the largest signal-to-interference ratio is selected by detecting the signal-to-interference ratio as follows:
detecting signal-to-interference ratio at XAIIn (1) selecting XAIIs far distance d e [ d ∈ [1,d2]Moiety XAI(n,d′)d′∈[d1,d2]Calculating the average intensity of interference P by summingI：
Wherein M1 is the total number of Doppler points;
selection of XaShort distance d e [ d [ ]3,d4]Moiety XAI(n,d″)d″∈[d3,d4]Calculating the average intensity P of the signal by summingS：
Wherein M2 is the total number of Doppler points;
the signal-to-interference ratio is defined as SIR ═ PS/PIAnd the direction in which the signal-to-interference ratio is maximum is defined as thetamaxThe data of the direction in which the signal-to-interference ratio is maximum after synthesis is expressed as:
wherein ,θmaxThe direction with the largest signal-to-interference ratio is the beam direction at the moment, and the beam null is just aligned to the interference incoming direction at the moment to realize interference suppression;
preferably, the data of the three field beam domains in step 4 are respectively expressed as:
XAI,0(n,d),XAI,1(n,d)，XAI,2(n,d)
XAI,0(n,d)＝XAI,max(n,d)
wherein ,XAI,max(n, d) is data in the direction in which the post-synthesis signal-to-interference ratio is maximum, x'1,1(n, d) denotes radar echo data, x 'of the monopole channel of the first monopole cross-loop antenna after calibration'1,2(n, d) represents radar echo data of a ring in the first monopole crossed-ring antenna after calibration, x'1,3(n, d) represents radar echo data of a b-loop in the first monopole crossed-loop antenna after calibration, x'2,1(n, d) denotes radar echo data, x 'of the monopole channel of the second monopole cross-loop antenna after calibration'2,2(n, d) denotes the radar echo data of the a-ring in the calibrated second monopole crossed-loop antenna, x'2,3(n, d) shows the radar echo data of the b-loop in the second monopole cross-loop antenna after calibration, thetamaxThe direction with the largest signal-to-interference ratio is the beam direction at the moment, and theta1＝θmax- β for the second field beam pointing, θ2＝θmax+ β is the third field beam pointing direction;
in step 4, the estimation of the super-resolution signal arrival angle of the beam domain according to the beam domain multiple signal classification algorithm is as follows:
the implementation process of the beam domain multiple signal classification algorithm is data of three field beam domains
X1＝[XAI,0(n,d),XAI,1(n,d)，XAI,2(n,d)]T
Inputting the signal into a MUSIC estimator to output a MUSIC spectrum PMUSIC(DOA), MUSIC spectrum PMUSICDirection DOA corresponding to maximum value of (DOA)maxI.e. the direction of the angle of arrival sought.
Compared with the prior art, the invention has the advantages that:
at the position of the monopole cross ring null, the array weighted value is zero, so the interference suppression effect is good;
the algorithm directly detects the signal-to-interference ratio of the inhibition result, avoids complex operations such as subspace solving and the like, and greatly reduces the calculated amount;
the arrival angle estimation of the signal is carried out through the MUSIC algorithm of the beam domain, compared with beam forming, the signal arrival angle estimation method has higher spatial resolution, and compared with the common MUSIC algorithm, the signal arrival angle estimation method has higher robustness;
because the interference generally comes from the continent and is generally opposite to the coming direction of the ocean echo, the null points to the interference, and the main beam of the antenna points to the ocean, the attenuation of the signal can be ensured to be small, and the follow-up further data processing is facilitated.
Drawings
FIG. 1: a flow chart of the algorithm;
FIG. 2: a schematic diagram of a receiving antenna of a high-frequency ground wave radar;
FIG. 3: the structure of the data received by the high-frequency ground wave radar;
FIG. 4: an interference identification process of the high-frequency ground wave radar;
FIG. 5: a beam forming schematic diagram of a high-frequency ground wave radar;
FIG. 6: beam offset diagram of high frequency ground wave radar.
Detailed Description
In order to facilitate the understanding and implementation of the present invention for those of ordinary skill in the art, the present invention will be described in more detail with reference to the accompanying drawings and examples, it being understood that the implementation examples described herein are only for the purpose of illustration and explanation and are not intended to limit the present invention.
The following describes an embodiment of the present invention with reference to fig. 1 to 6, and a specific embodiment of the present invention is a method for suppressing radio frequency interference of a portable high-frequency ground wave radar, including the following steps:
step 1: dividing a first-order peak area of radar echo through radar echo data, calculating the calibration values of the amplitude and the phase between three channels of a monopole crossed ring in the first-order peak area of the radar echo, and further calculating the calibration values of the amplitude and the phase between monopoles according to a target echo to obtain calibrated radar echo data;
step 1 the radar echo data are expressed as:
[xk,1(n,d),xk,2(n,d),xk,3(n,d)]k∈[1,2]n∈[1,N]d∈[1,D]
wherein k represents the monopole cross-loop antenna serial number, N represents the number of radar echo points in frequency, D represents the number of radar echo points in distance, xk,1(n, d) denotes radar echo data of a monopole channel of a kth monopole cross-loop antenna, xk,2(n, d) denotes radar echo data of a-ring in the k-th monopole cross-loop antenna, xk,3(n, d) denotes radar echo data of b-loop in the kth monopole crossed-loop antenna;
the first-order peak area of the radar echo in the step 1 is obtained by adopting a difference spectrum method:
will return radar [ x ]k,1(n,d),xk,2(n,d),xk,3(n,d)]Inputting the data into a difference spectrum algorithm, and calculating to obtain a first-order peak area of the radar echo as follows:
wherein k represents the serial number of the monopole cross-loop antenna, M represents the point number of the first-order peak echo,data representing a first-order peak region of a monopole channel of a kth monopole cross-loop antenna,data representing the first-order peak region of the a-loop in the kth monopole cross-loop antenna,data representing the first-order peak region of the b-loop in the kth monopole cross-loop antenna.
Radar echo at first order peakRespectively calculating the first-order peak amplitude of the radar echo by a modulus method, averaging the calculated amplitudes to obtain the average value of the first-order peak amplitudes, wherein the average value is as follows:
[ampk,1,ampk,2,ampk,3]k∈[1,2]
wherein ,ampk,1Represents the average, amp, of the amplitudes of the monopole channels of the kth monopole cross-loop antennak,2Represents the average value, amp, of the amplitude of the a-loop in the kth monopole crossed-loop antennak,3Represents an average value of the amplitude of the b-loop in the kth monopole cross-loop antenna;
calculating the phase by the method of solving the argument, and averaging all the phases to obtain the average value of the first-order peak phases, which is:
[phasek,1,phasek,2,phasek,3]k∈[1,2]
wherein, phasek,1Represents the average value, phase, of the phases of the monopole channels of the kth monopole cross-loop antennak,2Represents the average value of the phase of the a-loop in the kth monopole crossed-loop antenna, phasek,3Represents an average value of the phase of the b-loop in the kth monopole crossed-loop antenna;
the amplitude calibration value is:
Ak＝[ampk,2/ampk,1,ampk,3/ampk,1]k∈[1,2]
wherein ,ampk,2/ampk,1I.e. amplitude calibration value, amp, of the a-loop in the kth monopole cross-loop antennak,3/ampk,1Namely the amplitude calibration value of the b-loop in the kth monopole crossed-loop antenna;
the phase calibration value is:
PHk＝[phasek,2-phasek,1,phasek,3-phasek,1]k∈[1,2]
wherein, phasek,2-phasek,1I.e. phase calibration value, phase of the a-loop in the kth monopole cross-loop antennak,3-phasek,1Namely the phase calibration value of the b-loop in the kth monopole crossed-loop antenna;
the calibration value is compensated to obtain calibrated radar echo data of two rings:
x′k,1(n,d)＝xk,1(n,d)
wherein ,x′k,1(n, d) denotes radar echo data, x 'of a monopole channel of the kth monopole cross-loop antenna after calibration'k,2(n, d) denotes radar echo data of a-ring in the kth monopole cross-ring antenna after calibration, x'k,3(n, d) represents the radar echo data of the b-ring in the k-th monopole cross-ring antenna after calibration;
for calibration between monopoles:
taking target data normal to the radar antenna, the target data can be expressed as:
[x1,1(p),x2,1(p)]p∈[1,Q]
wherein Q represents the number of target data points in the normal direction of the radar antenna, x1,1(p) target data for a monopole channel in the first monopole cross-loop antenna, x2,1(p) target data representing a monopole channel in a second monopole cross-loop antenna;
target data [ x ] in the normal direction of the radar antenna1,1(p),x2,1(p)]Respectively calculating the amplitude of radar target echo by a mode selection method, obtaining the average value of the target amplitude by averaging the obtained amplitudes,comprises the following steps:
[amp1,1,amp2,1]
wherein ,amp1,1Representing the average value, amp, of the amplitude of the target signal on the monopole channel of the first monopole cross-loop antenna2,1An average of the amplitudes of the target signal in the monopole channel representing the second monopole cross-loop antenna;
calculating the phase by a method of solving the argument, and obtaining the average value of the target phase by averaging the obtained phases, wherein the average value is as follows:
[phase1,1,phase2,1]
wherein, phase1,1Representing the average value, phase, of the phase of the target signal in the monopole channel of the first monopole cross-loop antenna2,1An average value representing the phase of the target signal on the monopole channel of the second monopole cross-loop antenna;
the amplitude calibration value is:
A′＝[amp2,1/amp1,1]
wherein ,amp2,1/amp1,1I.e., amplitude calibration values for the monopole channels in the second monopole cross-loop antenna.
The phase calibration value is:
PH′＝[phase2,1-phase1,1]
wherein, phase2,1-phase1,1Namely the phase calibration value of a monopole channel in the second monopole crossed loop antenna;
the calibration value is compensated to the calibrated radar echo data of the second monopole channel:
x′1,1(n,d)＝x1,1(n,d)
x′2,1(n,d)＝x2,1(n,d)/A′*ejPH′
wherein ,x′1,1(n, d) is the radar echo data of the monopole channel of the first monopole cross-loop antenna after calibration, x'2,1(n, d) are the radar echo data of the monopole channel of the second monopole cross-loop antenna after calibration;
step 1 the calibrated radar echo data is expressed as:
[x′k,1(n,d),x′k,2(n,d),x′k,3(n,d)]k∈[1,2]n∈[1,N]d∈[1,D]
wherein k denotes a monopole cross-loop antenna number, N denotes the number of points of radar echo in frequency, and D denotes the number of points of radar echo in distance, x'k,1(n, d) denotes radar echo data, x 'of a monopole channel of the kth monopole cross-loop antenna after calibration'k,2(n, d) represents a-ring radar echo data x 'in the k-th monopole crossed-ring antenna after calibration'k,3(n, d) represents the radar echo data of the b-ring in the k-th monopole cross-ring antenna after calibration;
step 2: obtaining radar echo data formed by logarithm according to the calibrated radar echo data obtained in the step 1, selecting radar echo data formed by long-distance logarithm to carry out smooth filtering to obtain radar echo data after smooth filtering, comparing the radar echo data after smooth filtering with a threshold to judge whether jumping exists, and further judging whether the radar echo data of the field is interfered;
step 2, the radar echo data formed by logarithm is:
calibrating the post-radar echo data [ x'k,1(n,d),x′k,2(n,d),x′k,3(n,d)]Taking logarithm to obtain radar echo data formed by logarithm:
Pk,l(n,d)＝10log[x′k,l(n,d)]l∈[1,3]k∈[1,2]n∈[1,N]d∈[1,D]
wherein k represents monopole cross loop antenna serial number, and N represents radar in frequencyThe number of echoes, D the number of radar echoes over distance, l the antenna number of 3 channels of the monopole crossed-loop antenna, x'k,1(n, d) denotes radar echo data, x 'of a monopole channel of the kth monopole cross-loop antenna after calibration'k,2(n, d) denotes radar echo data of a-ring in the kth monopole cross-ring antenna after calibration, x'k,3(n, d) represents the radar echo data of the b-ring in the k-th monopole cross-ring antenna after calibration;
the radar echo data after smoothing filtering in the step 2 is calculated in the following process:
logarithmic formed radar echo data Pk,lIn (n, d), a long-distance element d is selected as [ d ∈ [1,d2]Radar echo data Pk,l(n,d′)d′∈[d1,d2]Smoothing filtering in the doppler dimension:
wherein ,for smooth filtered spectra, Pk,l(N, d') is long-distance radar echo data, and N is the point number of Doppler frequency;
the detailed process of judging whether the jump signal is contained in the step 2 is as follows:
getLeftmost and rightmost N inSPoint weighting to obtain noise floor:
judgment ofIf there is a signal with α dB higher than NOISE, if there is a signal, it is considered that there is a jump;
the detailed process for judging whether the field radar echo data is interfered in the step 2 comprises the following steps:
if calibrated radar echo data x'k,1(n,d),x′k,2(n,d),x′k,3(n,d)]If four channel data contain hopping signals, the field radar echo data are interfered;
and step 3: carrying out six-channel data synthesis through an array flow pattern of six channels of the monopole crossed loop antenna and calibrated radar echo data, continuously changing beam pointing of the synthesized six-channel data, and selecting the beam pointing with the largest signal-to-interference ratio as the final pointing of a beam by detecting the signal-to-interference ratio;
in step 3, the array flow pattern of the monopole cross-loop antenna six channels is as follows:
wherein theta is a beam direction, AI [1] in the vector AI represents a weighting factor of a monopole channel of the first monopole cross-loop antenna, AI [2] represents a weighting factor of an a-loop in the first monopole cross-loop antenna, AI [3] represents a weighting factor of a b-loop in the first monopole cross-loop antenna, AI [4] represents a weighting factor of a monopole channel of the second monopole cross-loop antenna, AI [5] represents a weighting factor of an a-loop in the second monopole cross-loop antenna, and AI [6] represents a weighting factor of a b-loop in the second monopole cross-loop antenna;
in step 3, the calibrated radar echo data are:
X＝[x′1,1(n,d),x′1,2(n,d),x′1,3(n,d),x′2,1(n,d),x′2,2(n,d),x′2,3(n,d)]T
wherein T represents transpose of matrix, x'1,1(n, d) denotes radar echo data, x 'of the monopole channel of the first monopole cross-loop antenna after calibration'1,2(n, d) represents radar echo data of a ring in the first monopole crossed-ring antenna after calibration, x'1,3(n, d) represents radar echo data of a b-loop in the first monopole crossed-loop antenna after calibration, x'2,1(n, d) denotes radar echo data, x 'of the monopole channel of the second monopole cross-loop antenna after calibration'2,2(n, d) denotes the radar echo data of the a-ring in the calibrated second monopole crossed-loop antenna, x'2,3(n, d) represents the radar echo data of the b-loop in the second monopole crossed-loop antenna after calibration;
and step 3, synthesizing the six-channel data:
wherein theta is the direction of the beam, x'1,1(n, d) denotes radar echo data, x 'of the monopole channel of the first monopole cross-loop antenna after calibration'1,2(n, d) represents radar echo data of a ring in the first monopole crossed-ring antenna after calibration, x'1,3(n, d) represents radar echo data of a b-loop in the first monopole crossed-loop antenna after calibration, x'2,1(n, d) denotes radar echo data, x 'of the monopole channel of the second monopole cross-loop antenna after calibration'2,2(n, d) denotes the radar echo data of the a-ring in the calibrated second monopole crossed-loop antenna, x'2,3(n, d) represents the radar echo data of the b-loop in the second monopole crossed-loop antenna after calibration;
in step 3, the beam direction with the largest signal-to-interference ratio is selected by detecting the signal-to-interference ratio as follows:
detecting signal-to-interference ratio at XAIIn (1) selecting XAIIs far distance d e [ d ∈ [1,d2]Moiety XAI(n,d′)d′∈[d1,d2]，d1＝60,d2The average interference strength P is calculated by summing 80I：
Wherein M1 is the total number of Doppler points;
selection of XaShort distance d e [ d [ ]3,d4]Moiety XAI(n,d″)d″∈[d3,d4]，d3＝10,d4Signal average strength P is calculated by summation at 30S：
Wherein M2 is the total number of Doppler points;
the signal-to-interference ratio is defined as SIR ═ PS/PIAnd the direction in which the signal-to-interference ratio is maximum is defined as thetamaxThe data of the direction in which the signal-to-interference ratio is maximum after synthesis is expressed as:
wherein ,θmaxThe direction with the largest signal-to-interference ratio is the beam direction at the moment, and the beam null is just aligned to the interference incoming direction at the moment to realize interference suppression;
and 4, step 4: adjusting the angle of the beam direction with the maximum signal-to-interference ratio in the step 3 to obtain data of a three-field beam domain, and further realizing super-resolution signal arrival angle estimation of the beam domain according to a beam domain multiple signal classification algorithm;
the data of the three field beam domains in step 4 are respectively expressed as:
XAI,0(n,d),XAI,1(n,d)，XAI,2(n,d)
XAI,0(n,d)＝XAI,max(n,d)
wherein ,XAI,max(n, d) is data in the direction in which the post-synthesis signal-to-interference ratio is maximum, x'1,1(n, d) denotes radar echo data, x 'of the monopole channel of the first monopole cross-loop antenna after calibration'1,2(n, d) represents radar echo data of a ring in the first monopole crossed-ring antenna after calibration, x'1,3(n, d) represents radar echo data of a b-loop in the first monopole crossed-loop antenna after calibration, x'2,1(n, d) denotes radar echo data, x 'of the monopole channel of the second monopole cross-loop antenna after calibration'2,2(n, d) denotes the radar echo data of the a-ring in the calibrated second monopole crossed-loop antenna, x'2,3(n, d) shows the radar echo data of the b-loop in the second monopole cross-loop antenna after calibration, thetamaxThe direction with the largest signal-to-interference ratio is the beam direction at the moment, and theta1＝θmax- β for the second field beam pointing, θ2＝θmax+ β for the third field beam pointing, β -15 °;
in step 4, the estimation of the super-resolution signal arrival angle of the beam domain according to the beam domain multiple signal classification algorithm is as follows:
the implementation process of the beam domain multiple signal classification algorithm is data of three field beam domains
X1＝[XAI,0(n,d),XAI,1(n,d)，XAI,2(n,d)]T
Inputting the signal into a MUSIC estimator to output a MUSIC spectrum PMUSIC(DOA), MUSIC spectrum PMUSICDirection DOA corresponding to maximum value of (DOA)maxI.e. the direction of the angle of arrival sought.
The specific embodiments described herein are merely illustrative of the spirit of the invention. Various modifications or additions may be made to the described embodiments or alternatives may be employed by those skilled in the art without departing from the spirit or ambit of the invention as defined in the appended claims.
Claims (5)
1. A portable high-frequency ground wave radar radio frequency interference suppression method is characterized by comprising the following steps:
step 1: dividing a first-order peak area of radar echo through radar echo data, calculating the calibration values of the amplitude and the phase between three channels of the monopole crossed loop antenna in the first-order peak area of the radar echo, and further calculating the calibration values of the amplitude and the phase between monopoles according to a target echo to obtain calibrated radar echo data;
step 2: obtaining radar echo data formed by logarithm according to the calibrated radar echo data obtained in the step 1, selecting radar echo data formed by long-distance logarithm to carry out smooth filtering to obtain radar echo data after smooth filtering, comparing the radar echo data after smooth filtering with a threshold to judge whether jumping exists, and further judging whether the radar echo data of the field is interfered;
and step 3: carrying out six-channel data synthesis through an array flow pattern of six channels of the monopole crossed loop antenna and calibrated radar echo data, continuously changing beam pointing of the synthesized six-channel data, and selecting the beam pointing with the largest signal-to-interference ratio as the final pointing of a beam by detecting the signal-to-interference ratio;
and 4, step 4: and (3) adjusting the angle of the beam direction with the maximum signal-to-interference ratio in the step (3) to obtain data of three field beam domains, and further realizing the super-resolution signal arrival angle estimation of the beam domains according to a beam domain multiple signal classification algorithm.
2. The portable high-frequency ground wave radar radio frequency interference suppression method according to claim 1, characterized by: step 1 the radar echo data are expressed as:
[xk,1(n,d),xk,2(n,d),xk,3(n,d)]k∈[1,2]n∈[1,N]d∈[1,D]
wherein k represents the monopole cross-loop antenna serial number, N represents the number of radar echo points in frequency, D represents the number of radar echo points in distance, xk,1(n, d) denotes radar echo data of a monopole channel of a kth monopole cross-loop antenna, xk,2(n, d) denotes radar echo data of a-ring in the k-th monopole cross-loop antenna, xk,3(n, d) denotes radar echo data of b-loop in the kth monopole crossed-loop antenna;
the first-order peak area of the radar echo in the step 1 is obtained by adopting a difference spectrum method:
will return radar [ x ]k,1(n,d),xk,2(n,d),xk,3(n,d)]Inputting the data into a difference spectrum algorithm, and calculating to obtain a first-order peak area of the radar echo as follows:
wherein k represents the serial number of the monopole cross-loop antenna, M represents the point number of the first-order peak echo,data representing a first-order peak region of a monopole channel of a kth monopole cross-loop antenna,data representing the first-order peak region of the a-loop in the kth monopole cross-loop antenna,data representing a first-order peak region of a b-loop in a kth monopole cross-loop antenna;
radar echo at first order peakRespectively calculating the first-order peak amplitude of the radar echo by a modulus method, averaging the calculated amplitudes to obtain the average value of the first-order peak amplitudes, wherein the average value is as follows:
[ampk,1,ampk,2,ampk,3]k∈[1,2]
wherein ,ampk,1Represents the average, amp, of the amplitudes of the monopole channels of the kth monopole cross-loop antennak,2Represents the average value, amp, of the amplitude of the a-loop in the kth monopole crossed-loop antennak,3Represents an average value of the amplitude of the b-loop in the kth monopole cross-loop antenna;
calculating the phase by the method of solving the argument, and averaging all the phases to obtain the average value of the first-order peak phases, which is:
[phasek,1,phasek,2,phasek,3]k∈[1,2]
wherein, phasek,1Represents the average value, phase, of the phases of the monopole channels of the kth monopole cross-loop antennak,2Represents the average value of the phase of the a-loop in the kth monopole crossed-loop antenna, phasek,3Represents an average value of the phase of the b-loop in the kth monopole crossed-loop antenna;
the amplitude calibration value is:
Ak＝[ampk,2/ampk,1,ampk,3/ampk,1]k∈[1,2]
wherein ,ampk,2/ampk,1I.e. amplitude calibration value, amp, of the a-loop in the kth monopole cross-loop antennak,3/ampk,1Namely the amplitude calibration value of the b-loop in the kth monopole crossed-loop antenna;
the phase calibration value is:
PHk＝[phasek,2-phasek,1,phasek,3-phasek,1]k∈[1,2]
wherein, phasek,2-phasek,1I.e. phase calibration value, phase of the a-loop in the kth monopole cross-loop antennak,3-phasek,1Namely the phase calibration value of the b-loop in the kth monopole crossed-loop antenna;
the calibration value is compensated to obtain calibrated radar echo data of two rings:
x′k,1(n,d)＝xk,1(n,d)
wherein ,x′k,1(n, d) denotes radar echo data, x 'of a monopole channel of the kth monopole cross-loop antenna after calibration'k,2(n, d) denotes radar echo data of a-ring in the kth monopole cross-ring antenna after calibration, x'k,3(n, d) represents the radar echo data of the b-ring in the k-th monopole cross-ring antenna after calibration;
for calibration between monopoles:
taking target data normal to the radar antenna, the target data can be expressed as:
[x1,1(p),x2,1(p)]p∈[1,Q]
wherein Q represents the number of target data points in the normal direction of the radar antenna, x1,1(p) target data for a monopole channel in the first monopole cross-loop antenna, x2,1(p) target data representing a monopole channel in a second monopole cross-loop antenna;
target data [ x ] in the normal direction of the radar antenna1,1(p),x2,1(p)]In the method, the amplitude of radar target echoes is respectively calculated by a mode taking method, and the average value of the target amplitude is obtained by averaging the obtained amplitudes, wherein the average value is as follows:
[amp1,1,amp2,1]
wherein ,amp1,1Representing the average value, amp, of the amplitude of the target signal on the monopole channel of the first monopole cross-loop antenna2,1An average of the amplitudes of the target signal in the monopole channel representing the second monopole cross-loop antenna;
calculating the phase by a method of solving the argument, and obtaining the average value of the target phase by averaging the obtained phases, wherein the average value is as follows:
[phase1,1,phase2,1]
wherein, phase1,1Representing the average value, phase, of the phase of the target signal in the monopole channel of the first monopole cross-loop antenna2,1An average value representing the phase of the target signal on the monopole channel of the second monopole cross-loop antenna;
the amplitude calibration value is:
A′＝[amp2,1/amp1,1]
wherein ,amp2,1/amp1,1Namely the amplitude calibration value of a monopole channel in the second monopole crossed loop antenna;
the phase calibration value is:
PH′＝[phase2,1-phase1,1]
wherein, phase2,1-phase1,1Namely the phase calibration value of a monopole channel in the second monopole crossed loop antenna;
the calibration value is compensated to the calibrated radar echo data of the second monopole channel:
x′1,1(n,d)＝x1,1(n,d)
x′2,1(n,d)＝x2,1(n,d)/A′*ejPH′
wherein ,x′1,1(n, d) is the radar echo data of the monopole channel of the first monopole cross-loop antenna after calibration, x'2,1(n, d) are the radar echo data of the monopole channel of the second monopole cross-loop antenna after calibration;
step 1 the calibrated radar echo data is expressed as:
[x′k,1(n,d),x′k,2(n,d),x′k,3(n,d)]k∈[1,2]n∈[1,N]d∈[1,D]
wherein k denotes a monopole cross-loop antenna number, N denotes the number of points of radar echo in frequency, and D denotes the number of points of radar echo in distance, x'k,1(n, d) denotes radar echo data, x 'of a monopole channel of the kth monopole cross-loop antenna after calibration'k,2(n, d) represents a-ring radar echo data x 'in the k-th monopole crossed-ring antenna after calibration'k,3And (n, d) represents the radar echo data of the b-ring in the calibrated kth monopole crossed-ring antenna.
3. The portable high-frequency ground wave radar radio frequency interference suppression method according to claim 1, characterized by: step 2, the radar echo data formed by logarithm is:
calibrating the post-radar echo data [ x'k,1(n,d),x′k,2(n,d),x′k,3(n,d)]Taking logarithm to obtain radar echo data formed by logarithm:
Pk,l(n,d)＝10log[x′k,l(n,d)]l∈[1,3]k∈[1,2]n∈[1,N]d∈[1,D]
wherein k denotes a monopole cross-loop antenna number, N denotes the number of points of radar echo in frequency, D denotes the number of points of radar echo in distance, l denotes an antenna number of 3-channel monopole cross-loop antenna, x'k,1(n, d) denotes radar echo data, x 'of a monopole channel of the kth monopole cross-loop antenna after calibration'k,2(n, d) denotes the kth after calibrationRadar echo data of a-ring in monopole cross-ring antenna, x'k,3(n, d) represents the radar echo data of the b-ring in the k-th monopole cross-ring antenna after calibration;
the radar echo data after smoothing filtering in the step 2 is calculated in the following process:
logarithmic formed radar echo data Pk,lIn (n, d), a long-distance element d is selected as [ d ∈ [1,d2]Radar echo data Pk,l(n,d′)d′∈[d1,d2]Smoothing filtering in the doppler dimension:
wherein ,for smooth filtered spectra, Pk,l(N, d') is long-distance radar echo data, and N is the point number of Doppler frequency;
the detailed process of judging whether the jump signal is contained in the step 2 is as follows:
getLeftmost and rightmost N inSPoint weighting to obtain noise floor:
judgment ofIf there is a signal α higher than NOISE floor NOISE, if there is a signal, it is considered that there is a jump;
the detailed process for judging whether the field radar echo data is interfered in the step 2 comprises the following steps:
if calibrated radar echo data x'k,1(n,d),x′k,2(n,d),x′k,3(n,d)]In which four channel data containAnd (4) jumping signals, and then the field radar echo data is interfered.
4. The portable high-frequency ground wave radar radio frequency interference suppression method according to claim 1, characterized by: in step 3, the array flow pattern of the monopole cross-loop antenna six channels is as follows:
wherein theta is a beam direction, AI [1] in the vector AI represents a weighting factor of a monopole channel of the first monopole cross-loop antenna, AI [2] represents a weighting factor of an a-loop in the first monopole cross-loop antenna, AI [3] represents a weighting factor of a b-loop in the first monopole cross-loop antenna, AI [4] represents a weighting factor of a monopole channel of the second monopole cross-loop antenna, AI [5] represents a weighting factor of an a-loop in the second monopole cross-loop antenna, and AI [6] represents a weighting factor of a b-loop in the second monopole cross-loop antenna;
in step 3, the calibrated radar echo data are:
X＝[x′1,1(n,d),x′1,2(n,d),x′1,3(n,d),x′2,1(n,d),x′2,2(n,d),x′2,3(n,d)]T
wherein T represents transpose of matrix, x'1,1(n, d) denotes radar echo data, x 'of the monopole channel of the first monopole cross-loop antenna after calibration'1,2(n, d) represents radar echo data of a ring in the first monopole crossed-ring antenna after calibration, x'1,3(n, d) represents radar echo data of a b-loop in the first monopole crossed-loop antenna after calibration, x'2,1(n, d) denotes radar echo data, x 'of the monopole channel of the second monopole cross-loop antenna after calibration'2,2(n, d) denotes the a-ring of the second monopole crossed-loop antenna after calibrationTo echo data, x'2,3(n, d) represents the radar echo data of the b-loop in the second monopole crossed-loop antenna after calibration;
and step 3, synthesizing the six-channel data:
wherein theta is the direction of the beam, x'1,1(n, d) denotes radar echo data, x 'of the monopole channel of the first monopole cross-loop antenna after calibration'1,2(n, d) represents radar echo data of a ring in the first monopole crossed-ring antenna after calibration, x'1,3(n, d) represents radar echo data of a b-loop in the first monopole crossed-loop antenna after calibration, x'2,1(n, d) denotes radar echo data, x 'of the monopole channel of the second monopole cross-loop antenna after calibration'2,2(n, d) denotes the radar echo data of the a-ring in the calibrated second monopole crossed-loop antenna, x'2,3(n, d) represents the radar echo data of the b-loop in the second monopole crossed-loop antenna after calibration;
in step 3, the beam direction with the largest signal-to-interference ratio is selected by detecting the signal-to-interference ratio as follows:
detecting signal-to-interference ratio at XAIIn (1) selecting XAIIs far distance d e [ d ∈ [1,d2]Moiety XAI(n,d′)d′∈[d1,d2]Calculating the average intensity of interference P by summingI：
Wherein M1 is the total number of Doppler points;
selection of XaShort distance d e [ d [ ]3,d4]Moiety XAI(n,d″)d″∈[d3,d4]Calculating the average intensity P of the signal by summingS：
Wherein M2 is the total number of Doppler points;
the signal-to-interference ratio is defined as SIR ═ PS/PIAnd the direction in which the signal-to-interference ratio is maximum is defined as thetamaxThe data of the direction in which the signal-to-interference ratio is maximum after synthesis is expressed as:
wherein ,θmaxThe direction with the largest signal-to-interference ratio is the beam direction at the moment, and the beam null is just aligned to the incoming direction of the interference at the moment, so that the interference suppression is realized.
5. The portable high-frequency ground wave radar radio frequency interference suppression method according to claim 1, characterized by: the data of the three field beam domains in step 4 are respectively expressed as:
XAI,0(n,d),XAI,1(n,d)，XAI,2(n,d)
XAI,0(n,d)＝XAI,max(n,d)
wherein ,XAI,max(n, d) is data in the direction in which the post-synthesis signal-to-interference ratio is maximum, x'1,1(n, d) denotes radar echo data, x 'of the monopole channel of the first monopole cross-loop antenna after calibration'1,2(n, d) represents radar echo data of a ring in the first monopole crossed-ring antenna after calibration, x'1,3(n, d) represents radar echo data of a b-loop in the first monopole crossed-loop antenna after calibration, x'2,1(n, d) denotes radar echo data, x 'of the monopole channel of the second monopole cross-loop antenna after calibration'2,2(n, d) denotes the second monopole after calibrationRadar echo data of a-ring in sub-crossed-ring antenna, x'2,3(n, d) shows the radar echo data of the b-loop in the second monopole cross-loop antenna after calibration, thetamaxThe direction with the largest signal-to-interference ratio is the beam direction at the moment, and theta1＝θmax- β for the second field beam pointing, θ2＝θmax+ β is the third field beam pointing direction;
in step 4, the estimation of the super-resolution signal arrival angle of the beam domain according to the beam domain multiple signal classification algorithm is as follows:
the implementation process of the beam domain multiple signal classification algorithm is data of three field beam domains
X1＝[XAI,0(n,d),XAI,1(n,d)，XAI,2(n,d)]T
Inputting the signal into a MUSIC estimator to output a MUSIC spectrum PMUSIC(DOA), MUSIC spectrum PMUSICDirection DOA corresponding to maximum value of (DOA)maxI.e. the direction of the angle of arrival sought.
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Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN111337886A (en) * | 2020-03-23 | 2020-06-26 | 中国人民解放军空军工程大学 | Radar interference suppression method and device based on channel ratio function and electronic equipment |
| CN112051542A (en) * | 2020-08-25 | 2020-12-08 | 华中科技大学 | SAIR RFI source geographical positioning method and system based on multi-snapshot difference |
| CN112051542B (en) * | 2020-08-25 | 2023-09-29 | 华中科技大学 | SAIR RFI source geographic positioning method and system based on multi-snapshot difference |
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