CN109239671A - 一种抑制直流偏置的双频连续波多普勒雷达电路结构 - Google Patents
一种抑制直流偏置的双频连续波多普勒雷达电路结构 Download PDFInfo
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Abstract
本发明公开了一种抑制直流偏置的双频连续波多普勒雷达电路结构,接收天线连接四号功分器,四号功分器输出端一路串联一号带通滤波器、一号低噪声放大器、一号混频器、五号带通滤波器和一号模数转换器,另一路串联二号带通滤波器、二号低噪声放大器、二号混频器、六号带通滤波器和二号模数转换器,一号模数转换器和二号模数转换器均连接现场可编程门阵列;发射天线串联功率放大器、二号功分器,二号功分器输入端连接、三号功分器;一号功分器连接一号本振,输出端一路连接二号功分器,另一路经三号带通滤波器连接一号混频器;三号功分器连接二号本振,输出端一路连接二号功分器,另一路经四号带通滤波器连接二号混频器。
Description
技术领域
本发明涉及双频多普勒雷达电路领域,更具体的说,是涉及一种抑制直流偏置的双频连续波多普勒雷达电路结构。
背景技术
连续波多普勒雷达是实现生命体征探测的一种主要雷达结构。在连续波多普勒雷达众多接收机结构中,零中频结构是最常用的一种接收机结构,该结构不存在镜像频率干扰的问题,不再需要镜像抑制滤波器,因此简化了雷达的结构,但是该结构的本振频率和射频信号的频率相等,因而在接收机中混频后会存在直流偏置问题,这会严重影响信号解调结果的精度,甚至会限制该结构在高精度领域的应用。
针对零中频接收机结构的直流偏置问题,有人提出了数字低中频接收机结构[1],即利用一个与发射信号频率相差较小的本振信号输入混频器并与接收信号混频,混频产生的低中频信号再由模数转换器采样,最后在数字域进行第二次混频而产生基带信号。在该结构中,需要产生两个不同频率的信号,一个用作发射信号,另外一个用作本振信号,这在一定程度上浪费了信号源。
基于现有数字低中频接收机结构,有必要提出一种新型的接收机结构,以提高信号源的利用率。
【参考文献】
[1]Wu Y,Li J.The design of digital radar receivers[J].IEEE Aerospace&Electronic Systems Magazine,1998,13(1):35-41.
发明内容
本发明的目的是为了克服现有技术中的不足,提供一种抑制直流偏置的双频连续波多普勒雷达电路结构,提高了信号源的利用率,令两种不同频率的信号源都用作发射信号,并互相用作本振信号以实现数字低中频接收机结构;提高了生命体征探测的精度,由于两个频率的信号都用作发射信号,因此两个频率的信号都可以探测生命体征信号。
本发明的目的是通过以下技术方案实现的。
本发明的抑制直流偏置的双频连续波多普勒雷达电路结构,包括接收天线和发射天线,所述接收天线连接有四号功分器,所述四号功分器输出端分为两路,其中一路依次串联有一号带通滤波器、一号低噪声放大器、一号混频器、五号带通滤波器和一号模数转换器,另一路依次串联有二号带通滤波器、二号低噪声放大器、二号混频器、六号带通滤波器和二号模数转换器,所述一号模数转换器和二号模数转换器均连接现场可编程门阵列;
所述发射天线连接有功率放大器,所述功率放大器输入端连接有二号功分器,所述二号功分器输入端分为两路,其中一路连接有一号功分器,另一路连接有三号功分器;所述一号功分器输入端连接有一号本振,输出端分为两路,其中一路连接二号功分器输入端,另一路经三号带通滤波器连接至一号混频器输入端;所述三号功分器输入端连接有二号本振,输出端分为两路,其中一路连接二号功分器输入端,另一路经四号带通滤波器连接至二号混频器输入端。
在发射端,一号本振和二号本振产生的频率分别为1.67GHz和2.06GHz,两个频率的信号分别经过一号功分器和三号功分器分成两路,一路均用作发射信号,另外一路均用作本振信号;两个发射信号利用二号功分器合成,经过功率放大器(PA)放大后通过发射天线发射出去;
在接收端,接收到的信号先经过四号功分器将信号分成两路,然后接收信号分别经过中心频率为2.06GHz的一号带通滤波器和1.67GHz的二号带通滤波器,之后两路接收信号分别经一号低噪声放大器和二号低噪声放大器放大,分别与中心频率为1.67GHz的本振信号和中心频率为2.06GHz的本振信号进行混频;混频得到的低中频信号先分别经过五号带通滤波器和六号带通滤波器滤波,再分别经一号模数转换器和二号模数转换器采样转换成数字信号,之后低中频信号在现场可编程门阵列数字域中进行第二次正交混频,最终得到基带信号,上传至计算机。
与现有技术相比,本发明的技术方案所带来的有益效果是:
(1)本发明提高了信号源的利用率,两种不同频率的信号源都用作发射信号,并互相用作本振信号输入混频器,以实现数字低中频接收机结构。
(2)本发明中由于两个频率的信号都用作发射信号,因此两个频率的信号都可以探测到生命体征信号,并对两个探测结果进行相关处理,可以进一步提高生命体征探测的精度。
附图说明
图1是本发明抑制直流偏置的双频连续波多普勒雷达电路结构原理图。
附图标记:LO1一号本振,LO2二号本振,Power Divider1一号功分器,PowerDivider2二号功分器,Power Divider3三号功分器,Power Divider4四号功分器,PA功率放大器,Tx_Antenna发射天线,Rx_Antenna接收天线,BPF1一号带通滤波器,BPF2二号带通滤波器,BPF3三号带通滤波器,BPF4四号带通滤波器,BPF5五号带通滤波器,BPF6六号带通滤波器,BPF7七号带通滤波器,BPF8八号带通滤波器,BPF9九号带通滤波器,BPF10十号带通滤波器,LNA1一号低噪声放大器,LNA2二号低噪声放大器,Mixer1一号混频器,Mixer2二号混频器,Mixer3三号混频器,Mixer4四号混频器,Mixer5五号混频器,Mixer6六号混频器,ADC1一号模数转换器,ADC2二号模数转换器,FPGA现场可编程门阵列,Computer计算机。
具体实施方式
为了更清楚的说明本发明的技术方案,下面结合附图对本发明作进一步说明。对于本领域普通技术人员来讲,在不付出创造性劳动的前提下,还可以根据这些附图获得其他的附图。
本发明的抑制直流偏置的双频连续波多普勒雷达电路结构,如图1所示,包括接收天线Rx_Antenna和发射天线Tx_Antenna。所述接收天线Rx_Antenna连接有四号功分器Power Divider4,所述四号功分器Power Divider4输出端分为两路,其中一路依次串联有一号带通滤波器BPF1、一号低噪声放大器LNA1、一号混频器Mixer1、五号带通滤波器BPF5和一号模数转换器ADC1,另一路依次串联有二号带通滤波器BPF2、二号低噪声放大器LNA2、二号混频器Mixer2、六号带通滤波器BPF6和二号模数转换器ADC2,所述一号模数转换器ADC1和二号模数转换器ADC2均连接现场可编程门阵列FPGA。其中,现场可编程门阵列FPGA的作用相当于四个带通滤波器和四个混频器,如图1中所示的七号带通滤波器BPF7、八号带通滤波器BPF8、九号带通滤波器BPF9、十号带通滤波器BPF10、三号混频器Mixer3、四号混频器Mixer4、五号混频器Mixer5、六号混频器Mixer6。
所述发射天线Tx_Antenna连接功率放大器PA输出端,所述功率放大器PA输入端连接二号功分器Power Divider2输出端,所述二号功分器Power Divider2输入端分为两路,其中一路连接有一号功分器Power Divider1,另一路连接有三号功分器Power Divider3。所述一号功分器Power Divider1输入端连接有一号本振LO1,输出端分为两路,其中一路输出端A连接二号功分器Power Divider2输入端E,另一路输出端B经三号带通滤波器BPF3连接至一号混频器Mixer1输入端。所述三号功分器Power Divider3输入端连接有二号本振LO2,输出端分为两路,其中一路输出端C连接二号功分器Power Divider2输入端F,另一路输出端D经四号带通滤波器BPF4连接至二号混频器Mixer2输入端。
在发射端,一号本振LO1和二号本振LO2产生的频率分别为1.67GHz和2.06GHz,两个频率的信号分别经过一号功分器Power Divider1和三号功分器Power Divider3分成两路,一路均用作发射信号,另外一路均用作本振信号。为了尽量减小混频后基带信号的残余相位噪声,使用同一块晶振驱动两个本振信号源。两个发射信号利用二号功分器PowerDivider2合成,经过功率放大器PA放大后通过发射天线Tx_Antenna发射出去。在接收端,接收到的信号先经过四号功分器Power Divider4将信号分成两路,然后接收信号分别经过中心频率为2.06GHz的一号带通滤波器BPF1和1.67GHz的二号带通滤波器BPF2,使每个接收通道中只含有一个频率的信号。之后两路接收信号分别经一号低噪声放大器LNA1和二号低噪声放大器LNA2放大,分别与中心频率为1.67GHz的本振信号和中心频率为2.06GHz的本振信号进行混频。混频时,1.67GHz的接收信号与2.06GHz的本振信号进行混频,2.06GHz的接收信号与1.67GHz的本振信号进行混频。混频得到的低中频信号先分别经过五号带通滤波器BPF5和六号带通滤波器BPF6滤波,再分别经一号模数转换器ADC1和二号模数转换器ADC2采样转换成数字信号,之后低中频信号在现场可编程门阵列FPGA数字域中进行第二次正交混频,最终得到基带信号,上传至计算机Computer。
生命体征探测实现的方式具体如下。忽略幅度变化,设发射信号T(t)如公式
(1)所示:
T(t)=cos(2πft+φ(t))(1)
在式(1)中,f为发射信号的频率,t为时间,φ(t)为初始相位。人的胸腔运动会对发射信号产生调制作用,并使发射信号产生反射。接收天线接收到的频率为f1的反射信号R1(t)和频率为f2的反射信号R2(t)分别如式(2)、(3)所示:
在式(2)、(3)中,d0为雷达与被测物之间的距离,x(t)为人体的胸腔运动,λ1和λ2分别对应频率f1和f2的波长,c为信号的传播速度,φ1(t-2d0/c)和φ2(t-2d0/c)为残余相位。反射信号与本振信号混频后,得到的两路中频信号RIF1(t)和RIF2(t)分别如式(4)、(5)所示:
在式(4)、(5)中,fIF=f1-f2为混频后的中频信号,Δφ1和Δφ2为残余相位。如式(4)、(5)所示的中频信号分别经过一号模数转换器和二号模数转换器后,变成数字信号,并在数字域进行第二次混频,得到的基带信号BI1(n)、BQ1(n)、BI2(n)、BQ2(n)分别如式(6)-(9)所示:
利用复数信号解调法提取生命体征信号,重建的复数信号S1(n)、S2(n)分贝如式(10)、(11)所示:
实施例:
本发明中具体使用元器件的型号如下描述,一号本振LO1和二号本振LO2均采用Analog Devices公司的LTC6948IUFD,利用该本振产生1.67GHz和2.06GHz两个频率;一号功分器Power Divider1、二号功分器Power Divider2、三号功分器Power Divider3、四号功分器Power Divider4均采用Anaren公司的PD0922J5050S2HF;1.67GHz的二号带通滤波器BPF2和三号带通滤波器BPF3均采用TriQuint公司的TQQ7303;2.06GHz的一号带通滤波器BPF1和四号带通滤波器BPF4均采用TriQuint公司的856738;390MHz的五号带通滤波器BPF5和六号带通滤波器BPF6均采用Qualcomm公司的B39391B5047Z810;一号低噪声放大器LNA1和二号低噪声放大器LNA2均采用Analog Devices公司的HMC618ALP3ETR;一号混频器Mixer1和二号混频器Mixer2均采用AnalogDevices公司的LT5575EUF;一号模数转换器ADC1和二号模数转换器ADC2采用Analog Devices公司的AD9625;现场可编程门阵列FPGA采用Intel公司的5CSXFC6D6F31C6N。
尽管上面结合附图对本发明的功能及工作过程进行了描述,但本发明并不局限于上述的具体功能和工作过程,上述的具体实施方式仅仅是示意性的,而不是限制性的,本领域的普通技术人员在本发明的启示下,在不脱离本发明宗旨和权利要求所保护的范围情况下,还可以做出很多形式,这些均属于本发明的保护之内。
Claims (2)
1.一种抑制直流偏置的双频连续波多普勒雷达电路结构,包括接收天线(Rx_Antenna)和发射天线(Tx_Antenna),其特征在于,所述接收天线(Rx_Antenna)连接有四号功分器(Power Divider4),所述四号功分器(Power Divider4)输出端分为两路,其中一路依次串联有一号带通滤波器(BPF1)、一号低噪声放大器(LNA1)、一号混频器(Mixer1)、五号带通滤波器(BPF5)和一号模数转换器(ADC1),另一路依次串联有二号带通滤波器(BPF2)、二号低噪声放大器(LNA2)、二号混频器(Mixer2)、六号带通滤波器(BPF6)和二号模数转换器(ADC2),所述一号模数转换器(ADC1)和二号模数转换器(ADC2)均连接现场可编程门阵列(FPGA);
所述发射天线(Tx_Antenna)连接有功率放大器(PA),所述功率放大器(PA)输入端连接有二号功分器(Power Divider2),所述二号功分器(Power Divider2)输入端分为两路,其中一路连接有一号功分器(Power Divider1),另一路连接有三号功分器(PowerDivider3);所述一号功分器(Power Divider1)输入端连接有一号本振(LO1),输出端分为两路,其中一路连接二号功分器(Power Divider2)输入端,另一路经三号带通滤波器(BPF3)连接至一号混频器(Mixer1)输入端;所述三号功分器(Power Divider3)输入端连接有二号本振(LO2),输出端分为两路,其中一路连接二号功分器(Power Divider2)输入端,另一路经四号带通滤波器(BPF4)连接至二号混频器(Mixer2)输入端。
2.根据权利要求1所述的抑制直流偏置的双频连续波多普勒雷达电路结构,其特征在于,在发射端,一号本振(LO1)和二号本振(LO2)产生的频率分别为1.67GHz和2.06GHz,两个频率的信号分别经过一号功分器(Power Divider1)和三号功分器(Power Divider3)分成两路,一路均用作发射信号,另外一路均用作本振信号;两个发射信号利用二号功分器(Power Divider2)合成,经过功率放大器(PA)放大后通过发射天线(Tx_Antenna)发射出去;
在接收端,接收到的信号先经过四号功分器(Power Divider4)将信号分成两路,然后接收信号分别经过中心频率为2.06GHz的一号带通滤波器(BPF1)和1.67GHz的二号带通滤波器(BPF2),之后两路接收信号分别经一号低噪声放大器(LNA1)和二号低噪声放大器(LNA2)放大,分别与中心频率为1.67GHz的本振信号和中心频率为2.06GHz的本振信号进行混频;混频得到的低中频信号先分别经过五号带通滤波器(BPF5)和六号带通滤波器(BPF6)滤波,再分别经一号模数转换器(ADC1)和二号模数转换器(ADC2)采样转换成数字信号,之后低中频信号在现场可编程门阵列(FPGA)数字域中进行第二次正交混频,最终得到基带信号,上传至计算机(Computer)。
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