CN109188366A - Broadband emission Adaptive beamformer method based on subband maximum signal noise ratio principle - Google Patents
Broadband emission Adaptive beamformer method based on subband maximum signal noise ratio principle Download PDFInfo
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Abstract
The broadband emission Adaptive beamformer method based on subband maximum signal noise ratio principle that the invention discloses a kind of includes the following steps: to calculate the output signal of wideband array Step 1: design broadband emission aerial array；Step 2: design sub-filter group；Step 3: completing the sub-band division of broadband signal using the analysis filter group in sub-filter group；Step 4: calculating each sub-band adaptive Wave beam forming weight vector based on subband maximum signal noise ratio principle；Step 5: treated broadband signal is reconstructed using the synthesis filter group in sub-filter group.The method of the present invention can form that depth is very deep and direction null not varying with frequency in desired locations, and calculation amount is smaller, is conducive to Project Realization.
Description
Technical field
The invention belongs to array signal processing fields, and in particular to a kind of broadband hair based on subband maximum signal noise ratio principle
Penetrate Adaptive beamformer method.
Background technique
The null for the interference signal that is used to decay often is placed in receiving end by the adaptive array disposed in modern radar system,
Such as hostile interference, it is not intended to which electromagnetic interference or environment clutter etc., the antenna of this scheme is usually on aperture with uniform amplitude
Weighting is sent, to maximize main beam gain.It is this to be gradually improved in radar receiving end signal processing technique, by excellent
It is more and more difficult to change radar return signal Processing Algorithm promotion detection performance, therefore, nearest more and more research institutions are
The technology for the transmitting terminal creation null in radar is developed, benefit is that antenna can apply significant pair to interference signal
To loss.So far, the most of transmitting zero setting algorithms developed are suitable for narrowband application, and assume unlimited phase and
Amplitude precision.
Under normal circumstances, weighted value applied by each array element only calculates in the centre frequency of array signal, corresponds to
Half-wave long spacing between array element.In addition, each subsequent phase shifter of array element is only corrected signal center frequency.Therefore,
The actual phase shift of the broadband signal of each array element transmitting can be deviated with actual frequency, so as to cause in entire signal bandwidth,
The null of transmitting signal can deviate pointing direction.
To solve the above-mentioned problems, Peter G.Vouras proposes a kind of wideband array Robust Transmission zero setting (Robust
Transmit Nulling, RTN) beamforming algorithm, the algorithm is maximum in order to make to emit Signal-to-Noise (SINR), derives
SINR function about frequency integrator, and SINR function is solved by being conjugated iterative algorithm, to obtain optimal pumping
Head delay line coefficient.Due to the algorithm conjugation iterative initial value setting there are some problems and iteration step length calculate it is complicated, in order to
It obtains optimal solution, generally requires repeatedly to be conjugated iteration, increase considerably calculation amount, increase the load of system, be unfavorable for work
Journey is implemented.
Summary of the invention
The broadband emission Adaptive beamformer method based on subband maximum signal noise ratio principle that the present invention provides a kind of, hair
Ejected wave beam can form that depth is very deep and direction null not varying with frequency in desired locations, and calculation amount is smaller, is conducive to engineering
It realizes.
In order to solve the above-mentioned technical problem, using following technical scheme:
Broadband emission Adaptive beamformer method based on subband maximum signal noise ratio principle, includes the following steps:
Step 1: design broadband emission aerial array, calculates the output signal of wideband array；
Step 2: design sub-filter group；
Step 3: completing the sub-band division of broadband signal using the analysis filter group in sub-filter group；
Step 4: calculating each sub-band adaptive Wave beam forming weight vector based on subband maximum signal noise ratio principle；
Step 5: treated broadband signal is reconstructed using the synthesis filter group in sub-filter group.
Further, the broadband emission aerial array is the uniform linear array that element number of array is M, after each array element
Face is the tapped delay line (Tapped Delay Line, TDL) for being equivalent to Discrete Finite impact response filter, TDL system
Number is J, and the low-limit frequency of the primary output signal x (n) of wideband array is fL, highest frequency fH, n=0, ± 1, ± 2 ....
The response of TDL array meets following formula:
Wherein, j is imaginary unit, θ0For the array signal direction of the launch, ω is numerical frequency, wm[k] is m-th of array element
The weighted value of k-th of tap, m=0,1 ..., M-1, k=0,1 ..., J-1, TsFor the sampling time interval of two neighboring tap,
φ is the phase difference that two neighboring array element transmits signal, and φ meets formula:
Wherein, d is array element spacing, and f is instantaneous frequency, and c is the light velocity.
Space is mixed in order to prevent, and d=c/ (2f is arrangedH), in order to avoid being instantaneously mixed, T is sets=1/ (2fH)。
The output signal of m-th of array element are as follows:
Wherein, xmIt (n) is the output signal of m-th of array element, x (n-k) indicates input discrete signal x (n) to left k
Unit.
Further, the sub-filter group selects discrete Fourier transform filtering device group (Discrete
Fourier Transform Filter Bank, DFTFB), sub-filter group generally includes two groups of filter groups, wherein one
Group is analysis filter group, and for the decomposition of broadband signal, each way band after decomposing can be carried out individually at required signal
Reason；Another set is synthesis filter group, for the reconstruct of broadband signal, obtains system after reconstruct treated output letter
Number.
Further, there is Q sub-band processing channel behind each array element, there is an analysis filter in each sub-band processing channel
Wave device and a synthesis filter.Analysis filter in each subband channel is filtered by the low-pass prototype that a length is P
Device H0(z) translation obtains, and is f in sample frequencysWhen, length is the filter H of Pq(z) broadband signal that bandwidth is B can be filtered
It is f at bandwidthsThe subband signal of/P, therefore the length P=f of filters/(B/M).Q-th of Subband Analysis Filter shock response
Meet following formula:
Hq(z)=H0(zWq+i) (4)
H0(z)=1+z-1+…+z-(P-1) (5)
Wherein, Hq(z) z-transform of q-th of multichannel analysis filter impulse response, q=1 ..., Q and complex variable z are indicated
=ejω, W=e-j2π/P, q+i q-th of Subband Analysis Filter of expression is relative to low-pass filter H0(z) frequency shift (FS), and i=
fL/(B/M)-0.5。
Q-th of sub-band synthesis filter shock response meets following formula:
Fq(z)=W-(q+i)F0(zWq+i) (6)
F0(z)=1+z-1+…+z-(P-1) (7)
Wherein, Fq(z) z-transform of q-th of channel synthesis filter shock response is indicated.
By above formula, it can be concluded that, each synthesis filter and corresponding analysis filter have identical amplitude response, broadband
It is by sub-band division and reconstruct if signal is the frequency information that will not change original signal by sub-band division and reconstruct
Obtained output signal meets formula:
Y (n)=Qx (n-Q+1) (8)
Wherein, y (n) is the output signal by sub-band division and reconstruct, and x (n-Q+1) indicates discrete signal x (n) to the right
Translate Q-1 unit.
Further, when the broadband signal direction of the launch is θ0When, the array steering vector of signal meets formula:
v(θ0, f) and=[1, exp (j2 π fdsin θ0/c),…,exp(j2πfd(M-1)sinθ0/c)]T (9)
Wherein, []TFor transposition operator, v (θ0, f) and the expression direction of the launch is θ0, frequency be f signal array guide
Vector.
After analysis filter carries out sub-band division, the tap sampling frequency of TDL is reduced to original 1/Q, subband TDL delay
Chain vector meets formula:
Steering vector meets formula when relevant to signal frequency empty:
In formula,Indicate the Kronecker product of vector, Vst(θ0, f) the expression direction of the launch be θ0, frequency be f sky when lead
Draw vector.
Further, if broadband signal bandwidth is uniformly divided into K frequency point by analysis filter, then there is { f1,f2,...,
fK}∈[fL,fH], signal variance matrix and interference noise covariance matrix meet following formula:
Wherein, []HFor transposition conjugate operation symbol, Rst-qIt is the signal variance matrix of q-th of subband signal, Nst-qIt is q
The interference noise covariance matrix of a subband signal, K are frequency point sum, Vst-q(θ0,fl) expression frequency be flWhen sky when guide
Vector, Hq(fl) expression frequency be flWhen q-th of Subband Analysis Filter frequency response, Fq(fl) expression frequency be flWhen q
The frequency response of a sub-band synthesis filter, β are the power of interference signal, σ2It is the function of zero-mean additive white noise Gaussian process
Rate, I are unit matrix, θ0It is main lobe direction, θ1It is the direction for desirably forming null, fl∈{f1,f2,...,fKAnd l=1,
2,...,K。
Further, the signal-to-noise ratio SINR of q-th of subband signalqMeet formula:
Wherein, WqIt is the dimension TDL weight vector of NJ × 1 of q-th of subband signal, works as SINRqWhen maximum, it is optimal to obtain weight vector
Solution:
Wherein, Wopt-qIt is subband optimal T DL weight vector, λmaxIt isMaximum eigenvalue, Wopt-qIt is λmaxIt is corresponding
Feature vector.
Further, according to the reconstruct of synthesis filter group, by emitting Adaptive beamformer, m-th of array element output
Signal frequency-domain expression are as follows:
Wherein, Ym(ejω) indicate m-th of array element output signal frequency domain, wqm[k] indicates m-th of array element, q-th of subband
K-th of tap weightings, X (ejω) indicate original wideband signal frequency domain, Hq(ejω) indicate that the analysis of q-th of subband filters
The frequency response of device, Fq(ejω) indicate q-th of subband synthesis filter frequency response.
Further, the Broadband emission signal launching beam antenna radiation pattern after the reconstruct of synthesis filter group are as follows:
Wherein, P (θ, f) indicates broadband signal launching beam antenna radiation pattern, vst(θ, f) indicates the broadband signal direction of the launch
Steering vector when sky when for θ, frequency being f, Hq(f) frequency response of q-th of Subband Analysis Filter when frequency is f, F are indicatedq
(f) frequency response of q-th of sub-band synthesis filter when frequency is f is indicated.
By above-mentioned technological means, following technical effect can be obtained:
The broadband emission Adaptive beamformer method based on subband maximum signal noise ratio principle that the invention discloses a kind of is led to
The full bandwidth covariance matrix and interference noise covariance matrix of Maximum-likelihood estimation (MEL) broadband signal are crossed, based on maximum letter
Dry make an uproar finds out optimal T DL weight vector than (MSINR) criterion, not only greatly reduces the operand of method, also has good property
Energy.It being handled by sub-band division, the deeper null that can be formed in desired direction is stronger to the inhibiting effect of interference, and
And the tap sampling frequency of TDL is reduced, it is more conducive to Project Realization
Detailed description of the invention
Fig. 1 is the flow chart of the method for the present invention.
Fig. 2 is wideband array TDL processing structure schematic diagram of the present invention.
Fig. 3 is the ARRAY PROCESSING structural schematic diagram the present invention is based on sub-band division.
Fig. 4 is broadband RTN algorithm launching beam antenna radiation pattern.
Fig. 5 is subband RTN algorithm broadband emission beam antenna directional diagram.
Fig. 6 is the unallocated subband of the present invention based on broadband MSINR algorithm broadband emission Adaptive beamformer figure；Its
In, (a) is broadband MSINR algorithm launching beam antenna direction, is (b) the broadband algorithm null direction MSINR with frequency variation diagram.
Fig. 7 is present invention division subband based on subband MSINR algorithm broadband emission Adaptive beamformer figure；Wherein,
(a) it is subband MSINR algorithm launching beam antenna direction, is (b) the algorithm null direction subband MSINR with frequency variation diagram.
Specific embodiment
Technical solution of the present invention is described in detail with reference to the accompanying drawing:
A kind of broadband emission Adaptive beamformer method based on subband maximum Signal to Interference plus Noise Ratio criterion, as shown in Figure 1, main
It wants including the following steps:
Step 1: design broadband emission aerial array, calculates the output signal of wideband array.The letter of m-th of array element output
Number xm(n) meet formula:
Wherein, x (n-k) refers to the discrete signal x (n) of output to k unit of left, wm[k] refers to the kth of m-th of array element
The weighted value of a tap, m=0,1 ..., M-1, k=0,1 ..., J-1, M are array element sums, and J is tapped delay line coefficient.
Step 2: design sub-filter group, sub-filter group can be divided into analysis filter group and synthesis filter
Group, analysis filter group are used for the sub-band division of broadband signal, and synthesis filter group is used for signal reconstruction, the choosing of sub-filter group
Discrete Fourier transform filtering device group.
Step 3: completing the sub-band division of broadband signal using the analysis filter group in sub-filter group.Assuming that every
There is Q sub-band processing channel behind a array element, broadband signal bandwidth is uniformly divided into K frequency point, signal by analysis filter
Variance matrix and interference noise covariance matrix meet following formula:
Wherein, []HFor transposition conjugate operation symbol, Rst-qIt is the signal variance matrix of q-th of subband signal, Nst-qIt is q
The interference noise covariance matrix of a subband signal, K are frequency point sum, Vst-q(θ0,fl) expression frequency be flWhen sky when guide
Vector, Hq(fl) expression frequency be flWhen q-th of Subband Analysis Filter frequency response, Fq(fl) expression frequency be flWhen q
The frequency response of a sub-band synthesis filter, β are the power of interference signal, σ2It is the function of zero-mean additive white noise Gaussian process
Rate, I are unit matrix, θ0It is main lobe direction, θ1It is the direction for desirably forming null, fl∈{f1,f2,...,fKAnd l=1,
2,...,K。
Step 4: calculating each sub-band adaptive Wave beam forming weight vector based on subband maximum signal noise ratio principle.Q-th of son
The signal-to-noise ratio SINR of band signalqMeet formula:
Wherein, WqIt is the dimension TDL weight vector of NJ × 1 of q-th of subband signal.Work as SINRqWhen maximum, available weight vector
Optimal solution:
Wherein, subband optimal T DL weight vector Wopt-qIt isMaximum eigenvalue λmaxCorresponding feature vector.
Step 5: treated broadband signal is reconstructed using the synthesis filter group in sub-filter group.
The optimal T DL weight vector for finding out each subband, according to the reconstruct of synthesis filter group, by emitting Adaptive beamformer, m
The frequency-domain expression of the signal of a array element output are as follows:
Wherein, Ym(ejω) indicate m-th of array element output signal frequency domain, wqm[k] indicates m-th of array element, q-th of subband
K-th of tap weightings, X (ejω) indicate original wideband signal frequency domain, Hq(ejω) indicate that the analysis of q-th of subband filters
The frequency response of device, Fq(ejω) indicate q-th of subband synthesis filter frequency response.
The main lobe direction of final output is θ0Broadband signal launching beam antenna radiation pattern are as follows:
Wherein, P (θ, f) indicates broadband signal launching beam antenna radiation pattern, vst(θ, f) indicates the broadband signal direction of the launch
Steering vector when sky when for θ, frequency being f, Hq(f) frequency response of q-th of Subband Analysis Filter when frequency is f, F are indicatedq
(f) frequency response of q-th of sub-band synthesis filter when frequency is f is indicated.
In this embodiment, the validity of this method is further verified by Computer Simulation, and is utilized
The RTN beamforming algorithm of Peter G.Vouras is compared with algorithm of the invention.The parameter setting of this emulation experiment
It is as shown in table 1:
1 system emulation parameter of table
| Parameter name | Parameter values |
| Array number (M) | 32 |
| Subband port number (Q) | 5 |
| Signal center frequency (fc) | 1250MHz |
| Signal bandwidth (B) | 500MHz |
| Array element spacing (d) | 0.1m |
| Main beam direction (θ0) | 0° |
| Interference radiating way (θ1) | 20° |
| Original tap sampling frequency (Ts) | 3000MHz |
| It divides frequency points (K) | 96 |
In addition, time domain broadband when in order to ensure unallocated subband Wave beam forming and the time domain width phase after division subband
Together, TDL order J is 15 when unallocated subband, and it is wideband array TDL processing of the present invention that TDL order J, which is 5, Fig. 2, when dividing subband
Structural schematic diagram.
This ARRAY PROCESSING structure of emulation based on sub-band division is as shown in figure 3, broadband signal x (n) is filtered by analysis
Device, each subband after division individually carry out TDL processing, and treated, and signal is reconstructed by synthesis filter, are finally located
Output signal y after reasonm(n)。
According to theory analysis and emulation experiment, it is deeper that RTN algorithm can form depth in broadband emission wave beam assigned direction
Null, null direction does not change with frequency.The launching beam antenna radiation pattern of broadband RTN algorithm and subband RTN algorithm
Launching beam antenna radiation pattern difference is as shown in Figure 4 and Figure 5, it can be seen that compares wider band RTN algorithm, subband RTN algorithm can
To obtain deeper null.
The beam antenna directional diagram based on broadband MSINR broadband emission adaptive beam-forming algorithm of subband is not divided
As shown in (a) in Fig. 6, null direction with shown in (b) of the frequency variation such as in Fig. 6, divide subband based on subband MSINR
Shown in (a) in the beam antenna directional diagram such as Fig. 7 of broadband emission adaptive beam-forming algorithm, null direction becomes with frequency
Change as shown in (b) in Fig. 7.As can be seen that being interfered when angle is 20 ° from (b) in (b) and Fig. 7 in Fig. 6
It is a vertical lines on direction, this illustrates that broadband MSINR algorithm and subband MSINR algorithm can inhibit aperture to get over
Effect, the null direction formed on broadband emission wave beam do not change with frequency.
The null depth correlation that algorithms of different emulation experiment obtains is as shown in table 2:
2 algorithms of different of table forms null depth correlation (dB)
| Algorithm | Most | Center | Highest |
| Broadband RTN algorithm | 36.4 | 41.8 | 42.6 |
| Subband RTN algorithm | 33.2 | 45.9 | 38.4 |
| Broadband MSINR algorithm | 57.6 | 73.0 | 66.2 |
| Subband MSINR algorithm | 76.2 | 86.6 | 69.7 |
From table 2 it can be seen that the null depth formed based on MSINR criterion algorithm is obviously than the depth of RTN algorithm, and subband
The broadband emission adaptive beam-forming algorithm performance based on MSINR criterion divided is most strong.Broadband MSINR algorithm is formed by
Wave beam null depth improves 20dB or so in low-limit frequency, centre frequency, highest frequency, and in centre frequency, depth is reachable
73dB, performance are substantially better than RTN algorithm.Meanwhile subband MSINR algorithm, relative to broadband MSINR algorithm, null depth is further
It is promoted, centre frequency null depth reaches 86.2dB, further strengthens to the rejection of interference, and relative to broadband
The tap sampling frequency of MSINR algorithm, TDL is reduced to original 1/5, more conducively Project Realization.
Embodiments of the present invention are explained in detail above in conjunction with attached drawing, but the invention is not limited to above-mentioned
Embodiment within the knowledge of a person skilled in the art can also be before not departing from present inventive concept
It puts and makes a variety of changes.
Claims (9)
1. the broadband emission Adaptive beamformer method based on subband maximum signal noise ratio principle, which is characterized in that including as follows
Step:
Step 1: design broadband emission aerial array, calculates the output signal of wideband array；
Step 2: design sub-filter group；
Step 3: completing the sub-band division of broadband signal using the analysis filter group in sub-filter group；
Step 4: calculating each sub-band adaptive Wave beam forming weight vector based on subband maximum signal noise ratio principle；
Step 5: treated broadband signal is reconstructed using the synthesis filter group in sub-filter group.
2. the broadband emission Adaptive beamformer method according to claim 1 based on subband maximum signal noise ratio principle,
It is characterized in that, the broadband emission aerial array in step 1 is the uniform linear array that element number of array is M, behind each array element
The tapped delay line for being equivalent to Discrete Finite impact response filter, tapped delay line coefficient is J, wideband array it is defeated
The low-limit frequency of signal x (n) is f outL, highest frequency fH, n=0, ± 1, ± 2 ...；The signal x of m-th of array element outputm(n)
Meet formula:
Wherein, x (n-k) refers to the discrete signal x (n) of output to k unit of left, wm[k] refers to k-th of tap of m-th of array element
Weighted value, m=0,1 ..., M-1, k=0,1 ..., J-1.
3. the broadband emission Adaptive beamformer method according to claim 1 based on subband maximum signal noise ratio principle,
It is characterized in that, the sub-filter group selects discrete Fourier transform filtering device group.
4. the broadband emission Adaptive beamformer method according to claim 2 based on subband maximum signal noise ratio principle,
It is characterized in that, there is Q sub-band processing channel behind each array element, have in each sub-band processing channel an analysis filter and
One synthesis filter.
5. the broadband emission Adaptive beamformer method according to claim 4 based on subband maximum signal noise ratio principle,
It is characterized in that, the analysis filter in each subband channel is the lowpass prototype filter H for being P by a length0(z) translation obtains
, it is f in sample frequencysWhen, P=fs/ (B/M), wherein B is the bandwidth of signal in the subband channel, and M is array element sum；Point
Analysis filter meets following formula:
Hq(z)=H0(zWq+i)
H0(z)=1+z-1+…+z-(P-1)
Wherein, Hq(z) z-transform of q-th of multichannel analysis filter impulse response, q=1 ..., Q and complex variable z=e are indicatedjω,
W=e-j2π/P, q+i q-th of Subband Analysis Filter of expression is relative to low-pass filter H0(z) frequency shift (FS), i=fL/(B/
M) -0.5, fLIt is the low-limit frequency of broadband signal.
6. the broadband emission Adaptive beamformer method according to claim 5 based on subband maximum signal noise ratio principle,
It is characterized in that, synthesis filter meets following formula:
Fq(z)=W-(q+i)F0(zWq+i)
F0(z)=1+z-1+…+z-(P-1)
Wherein, Fq(z) z-transform of q-th of channel synthesis filter is indicated.
7. the broadband emission Adaptive beamformer method according to claim 1 based on subband maximum signal noise ratio principle,
It is characterized in that, the optimal weight vector W of the subband for meeting subband maximum signal noise ratio principleopt-qMeet formula:
Wherein, λmaxIt isMaximum eigenvalue, Rst-qIt is the signal variance matrix of q-th of subband signal, Nst-qIt is q-th
The interference noise covariance matrix of subband signal.
8. the broadband emission Adaptive beamformer method according to claim 1 based on subband maximum signal noise ratio principle,
It is characterized in that, the frequency-domain expression for the signal that m-th of array element exports after the reconstruct of synthesis filter group are as follows:
Wherein, Ym(ejω) indicate m-th of array element output signal frequency domain, Q is sub-band processing total number of channels, and J is tapped delay
Linear system number, q=1 ..., Q, k=0,1 ..., J-1, wqm[k] indicates k-th of tap weightings of m-th of array element, q-th of subband,
X(ejω) indicate original wideband signal frequency domain, Hq(ejω) indicate q-th of subband analysis filter frequency response, Fq(ejω)
Indicate the frequency response of the synthesis filter of q-th of subband.
9. the broadband emission Adaptive beamformer method according to claim 8 based on subband maximum signal noise ratio principle,
It is characterized in that, the Broadband emission signal launching beam antenna radiation pattern after the reconstruct of synthesis filter group are as follows:
Wherein, P (θ, f) indicates broadband signal launching beam antenna radiation pattern, vst(θ, f) indicate broadband signal direction of the launch be θ,
Frequency be f when sky when steering vector, Wopt-qIt is optimal weight vector, Hq(f) q-th of sub-band analysis filtration when frequency is f is indicated
The frequency response of device, Fq(f) frequency response of q-th of sub-band synthesis filter when frequency is f is indicated.
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| CN112420068A (en) * | 2020-10-23 | 2021-02-26 | 四川长虹电器股份有限公司 | Quick self-adaptive beam forming method based on Mel frequency scale frequency division |
| CN116505994A (en) * | 2023-06-26 | 2023-07-28 | 成都金支点科技有限公司 | Multi-beam forming method and device |
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| CN110166098A (en) * | 2019-04-25 | 2019-08-23 | 河海大学 | A kind of broadband only phase emits Adaptive beamformer method |
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| CN116505994A (en) * | 2023-06-26 | 2023-07-28 | 成都金支点科技有限公司 | Multi-beam forming method and device |
| CN116505994B (en) * | 2023-06-26 | 2023-09-01 | 成都金支点科技有限公司 | Multi-beam forming method and device |
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