CN109104201A - Based on the frequency dependence IQ mismatch calibration of FFT operation and compensation method - Google Patents
Based on the frequency dependence IQ mismatch calibration of FFT operation and compensation method Download PDFInfo
- Publication number
- CN109104201A CN109104201A CN201810882335.9A CN201810882335A CN109104201A CN 109104201 A CN109104201 A CN 109104201A CN 201810882335 A CN201810882335 A CN 201810882335A CN 109104201 A CN109104201 A CN 109104201A
- Authority
- CN
- China
- Prior art keywords
- frequency
- frequency point
- pos
- positive
- calibration
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
- 238000000034 method Methods 0.000 title claims abstract description 29
- 238000004891 communication Methods 0.000 claims abstract description 24
- 150000001875 compounds Chemical class 0.000 claims abstract description 23
- 230000005540 biological transmission Effects 0.000 claims description 4
- 238000001914 filtration Methods 0.000 claims description 2
- 238000004088 simulation Methods 0.000 claims description 2
- 230000008569 process Effects 0.000 abstract description 3
- 238000005070 sampling Methods 0.000 description 2
- 230000021615 conjugation Effects 0.000 description 1
- 238000010276 construction Methods 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
- 230000006872 improvement Effects 0.000 description 1
- 230000004048 modification Effects 0.000 description 1
- 238000012986 modification Methods 0.000 description 1
- 238000003032 molecular docking Methods 0.000 description 1
- 230000032258 transport Effects 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/0003—Software-defined radio [SDR] systems, i.e. systems wherein components typically implemented in hardware, e.g. filters or modulators/demodulators, are implented using software, e.g. by involving an AD or DA conversion stage such that at least part of the signal processing is performed in the digital domain
- H04B1/0028—Software-defined radio [SDR] systems, i.e. systems wherein components typically implemented in hardware, e.g. filters or modulators/demodulators, are implented using software, e.g. by involving an AD or DA conversion stage such that at least part of the signal processing is performed in the digital domain wherein the AD/DA conversion occurs at baseband stage
- H04B1/0042—Digital filtering
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B17/00—Monitoring; Testing
- H04B17/10—Monitoring; Testing of transmitters
- H04B17/11—Monitoring; Testing of transmitters for calibration
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B17/00—Monitoring; Testing
- H04B17/20—Monitoring; Testing of receivers
- H04B17/21—Monitoring; Testing of receivers for calibration; for correcting measurements
Landscapes
- Engineering & Computer Science (AREA)
- Computer Networks & Wireless Communication (AREA)
- Signal Processing (AREA)
- Physics & Mathematics (AREA)
- Electromagnetism (AREA)
- Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
Abstract
The frequency dependence IQ mismatch based on FFT operation that the present invention relates to a kind of is calibrated and compensated method.This method increases a digital matched filter by the road I or the road Q of the digital receiver base band in Wireless Broadband Communication Systems, to compensate frequency dependence IQ mismatch in receiver.Digital matched filter coefficient is obtained by calibration algorithm, process is, the positive compound calibration signal of frequency point is sent in transmitter, the frequency-region signal of each frequency point is obtained by FFT operation in digital receiver base band after the calibrated access of signal, the deviation that each frequency point needs to compensate successively is calculated according to the frequency-region signal size of the frequency-region signal of positive frequency point and its negative frequency point of mirror image, frequency domain deviation is passed through into IFFT operation, obtains the tap coefficient of digital matched filter.The method being calibrated and compensated there are frequency dependence IQ mismatch suitable for system of broadband wireless communication has very wide application range, is particularly suitable for WiMAX ofdm system.
Description
Technical field
The present invention relates to a kind of based on the frequency dependence IQ mismatch calibration of FFT operation and compensation method.
Background technique
Modern wireless communication technology mostly uses high bandwidth and high-order modulating greatly to realize the wireless transmission of high-speed.Example
Such as, the optional support 160M bandwidth of newest WLAN standard 802.11ac agreement and 256QAM modulation system, high broadband and
With the design of the system of high order modulation to the non-ideal characteristic of radio-frequency front-end be calibrated and compensated propose more harsh standard with
It is required that.
Amplitude-frequency characteristic by devices such as Analog Baseband part IQ two-way filter, amplifiers is inconsistent to be influenced, and IQ loses
In different frequency points be with caused gain mismatch and phase error it is inconsistent, i.e., IQ mismatch is and frequency dependence.IQ loses
Image signal interference with generation, can reduce the signal-to-noise ratio of signal, influence the EVM of transmitter and receiver.With communication system
The increase of bandwidth, it is increasingly common with the IQ mismatch of frequency dependence, therefore frequency dependence IQ mismatch is calibrated and compensated
It is the key that improve system of broadband wireless communication performance.
The prior art is calibrated and compensated to frequency independence IQ mismatch, therefore, logical for broadband wireless
Letter system needs to design a kind of method that can effectively eliminate frequency dependence IQ mismatch.
Summary of the invention
It is calibrated and compensated method the object of the present invention is to provide a kind of effective receiver frequency dependence IQ mismatch, from
And improve the overall performance of Wireless Broadband Communication Systems.
In order to achieve the above objectives, the technical solution adopted by the present invention is that:
It is a kind of based on the frequency dependence IQ mismatch calibration of FFT operation and compensation method, for including transmitter and connect
The frequency dependence IQ mismatch of the Wireless Broadband Communication Systems of receipts machine is calibrated and compensated, in the digital baseband of the receiver
The road I or the road Q increase a digital matched filter, and the tap coefficient of the digital matched filter passes through based on FFT operation
Calibration obtains, and is compensated in the Wireless Broadband Communication Systems by the digital matched filter in receiver analog channel
Frequency dependence IQ mismatch.
Preferably, the method for the tap coefficient of the digital matched filter is obtained by the calibration based on FFT operation are as follows:
The positive compound calibration signal of frequency point is sent in the transmitter, the positive compound calibration signal of frequency point passes through the wireless broadband communication
Digital baseband part is believed by the frequency domain that FFT operation obtains each positive frequency point in the receiver after the analog calibration access of system
The frequency-region signal that the negative frequency point of mirror image number is corresponded to each positive frequency point, according to the frequency-region signal of each positive frequency point and its negative frequency point of mirror image
Frequency-region signal calculates the deviation that each frequency point needs to carry out frequency domain compensation, then needs each frequency point to carry out frequency domain compensation
Deviation obtain the tap coefficient of the digital matched filter by IFFT operation.
Preferably, the method packet of the tap coefficient of the digital matched filter is obtained by the calibration based on FFT operation
Include following steps:
Step (1): the Wireless Broadband Communication Systems are switched into frequency dependence IQ calibration mode, and described wireless
IQ analog calibration access is established in wide-band communication system；
Step (2): the positive compound calibration signal of frequency point is generated in the digital baseband of the transmitter, the positive frequency point is multiple
The receives link that calibration signal passes through the transmitting link of the transmitter, the IQ analog calibration access, the receiver is closed, it is defeated
Out to the digital baseband of the receiver；
Step (3): the digital baseband of the receiver calls FFT module to carry out FFT operation to signal is received, and obtains described
The frequency-region signal POS_FX [k] of the corresponding each frequency point of the positive compound calibration signal of frequency point and as the positive compound calibration signal of frequency point
Corresponding FFT result and save, the frequency points that the FFT operation uses for N, k be frequency point serial number, k=-N/2 ..., N/2-
1, frequency point serial number k=1,2 ..., N/2-1 correspond to positive frequency point, corresponding 0 frequency point of k=0, k=-1, and -2 ..., the corresponding negative frequency point of-N/2,
The identical negative frequency point of frequency point serial number absolute value and positive frequency point mirror image frequency point each other；
Step (4): according to frequency point sequence, for k=1, the positive frequency point of 2 ..., N/2-1, successively calculate ADD_POS [k]=
POS_FX [k]+POS_FX* [- k] and SUB_POS [k]=POS_FX [k]-POS_FX* [- k], wherein POS_FX* [- k] is each
The conjugated signal of the frequency-region signal of the negative frequency point of positive frequency point mirror image；
Step (5): the amplitude absolute value ADD_POS_ of ADD_POS [k], SUB_POS [k] are successively calculated according to frequency point sequence
ABS [k], SUB_POS_ABS [k] and phase angle ADD_POS_ARG [k], SUB_POS_ARG [k]；
Step (6): successively calculating k=1,2 according to frequency point sequence ..., the corresponding number matching of the positive frequency point of N/2-1
Gain compensation basic value F ξ _ gain_pos (k) of filter=ADD_POS_ABS [k]/SUB_POS_ABS [k] and phase compensation
Basic value F ξ _ arg_pos (k)=ADD_POS_ARG [k]-SUB_POS_ARG [k]；
Step (7): the gain compensation basic value based on the corresponding digital matched filter of each positive frequency point calculates
The gain compensation value of each frequency point
Phase compensation basic value based on the corresponding digital matched filter of each positive frequency point calculates each frequency point
Phase compensation value
Step (8): according to frequency point sequence obtain each frequency point need to carry out deviation F ξ (k)=F ξ of frequency domain compensation _
Gain (k) * [cos (F ξ _ arg (k))+j*sin (F ξ _ arg (k))], k=-N/2 ..., N/2-1；
Step (9): the deviation for needing to carry out frequency domain compensation to each frequency point carries out the IFFT operation of N point, obtains the number
N number of tap coefficient of word matched filter.
Preferably, in the step (1), the signal that frequency mixer in the transmission link of the transmitter exports is directly inputted
To the receives link of the receiver frequency mixer and establish the IQ analog calibration access.
Preferably, in the step (2), it is positive and negative that the positive compound calibration signal of frequency point, which is to each positive frequency point real part,
1 random number, imaginary part 0 are 0 signal to each negative frequency point and the 0 frequency point real and imaginary parts.
Preferably, in the step (11), T effectively Ts of the tap coefficient as the digital matched filter before choosing
Rank tap coefficient.
Due to the above technical solutions, the present invention has the following advantages over the prior art: the present invention can be to nothing
Line wide-band communication system is calibrated and compensated frequency dependence IQ mismatch, can effectively improve the accurate of I/Q signal calibration
Degree, promotes the overall performance of broadband wireless communications, has very wide application range, is particularly suitable for WiMAX orthogonal frequency division multiplexing
With in system.
Detailed description of the invention
Attached drawing 1 is the system construction drawing of receiving end frequency dependence IQ mismatch calibration and compensation.
Specific embodiment
The invention will be further described for embodiment shown in reference to the accompanying drawing.
Embodiment one: Wireless Broadband Communication Systems include independent transmitter and receiver two parts, wherein in transmitter
It is formed with transmitting link (analog channel of transmitter), receives link (analog channel of receiver) is formed in receiver, connects
The frequency dependence IQ mismatch analog calibration access of receipts machine, which needs for the analog link of transmitter and receiver to be connected, to be led to
Letter.
With reference to shown in attached drawing 1, one kind is for above-mentioned 802.11ac Wireless Broadband Communication Systems and related to unit frequency is received
Property the method that is calibrated and compensated of IQ mismatch, by increasing a number matching filter on the road digital baseband I of receiver or the road Q
Wave device compensates the frequency dependence IQ mismatch due to caused by analog filter and radio-frequency devices etc. and reality in simulation receiving path
It is existing.In the present embodiment, the digital matched filter is added on the road digital baseband Q.Wherein, the tap coefficient of digital matched filter
It is obtained by the calibration based on FFT operation.Specific calibration process is to send the positive compound calibration signal of frequency point in transmitter, just
The compound calibration signal of frequency point passes through FFT operation in digital receiver base band after the analog calibration access of Wireless Broadband Communication Systems
The size of the frequency-region signal of the frequency-region signal of each positive frequency point and its negative frequency point of mirror image is obtained, according to the frequency domain of each positive frequency point of frequency domain
The frequency-region signal of signal and its negative frequency point of mirror image calculates the deviation that each frequency point needs to carry out frequency domain compensation, and each frequency point is needed
The deviation for carrying out frequency domain compensation passes through IFFT operation, obtains the tap coefficient of Q railway digital matched filter.
In embodiment, it is assumed that 802.11ac system needs to calibrate in the frequency range of baseband analog filter -40M to 40M
Frequency dependence IQ mismatch condition, the digital baseband signal sample rate of transmitter and receiver is 80M.It is above-mentioned to be calibrated and compensated
Method the following steps are included:
Wireless Broadband Communication Systems switching analog radio frequency access is entered frequency dependence IQ calibration mode by step (1), and
IQ analog calibration access is established in the Wireless Broadband Communication Systems, specially exports frequency mixer in the transmission link of transmitter
Signal be directly inputted to receiver receives link frequency mixer, form the IQ analog calibration access an of closed loop.
Step (2), the positive compound calibration signal of frequency point of digital baseband generation of transmitter, the positive compound calibration signal of frequency point are logical
Transmitting link, IQ analog calibration access, receives link are crossed, the digital baseband of receiver is then outputed signal to after ADC is sampled.
The frequency point interval of calibration signal is equal to the subcarrier spacing 312.5KHz of system real data, using 256 point FFT operations, total frequency
Point number is N=256, and frequency domain respectively samples the serial number range of frequency point from k=-N/2 ..., N/2-1, i.e. k=-128, -127 ..., -
1,0,1 ..., 126,127, frequency point serial number k=1,2 ..., N/2-1, i.e. k=1,2 ..., 127 correspond to positive frequency points, k=0 corresponding 0
Frequency point, k=-1, -2 ...,-N/2 i.e. k=-1, -2 ..., -127 corresponding negative frequency points, the identical negative frequency point of frequency point serial number absolute value
With positive frequency point mirror image frequency point each other.The positive compound calibration signal of frequency point is to each effective frequency point, i.e. k=1,2 ..., 127 positive frequency point
Numerical value is positive and negative 1 random number of real part, and imaginary part 0, to remaining frequency point, i.e., negative frequency point and 0 frequency point real part imaginary part are all 0 signal,
Frequency domain data obtains the calibration signal of time domain by IFFT operation, is output to calibration access through DAC.
Step (3), receiver sample the compound calibration signal of positive frequency point by ADC, and digital baseband calls FFT module docking
The collection of letters number carries out a FFT operation, respectively obtains the frequency-region signal (256 frequency points) of the corresponding each frequency point of the compound calibration signal of positive frequency point
POS_FX [k], k=-128 ..., 127, the frequency-region signal POS_FX [k] of each frequency point is used as the compound calibration signal pair of positive frequency point
The frequency-region signal of the negative frequency point of the FFT result answered, the frequency-region signal comprising each positive frequency point and each positive frequency point mirror image saves
FFT result.
Step (4), according to frequency point sequence, for having the k=1 of signal, 2 ..., N/2-1, i.e. k=1,2 ..., 127 just
Frequency point successively calculates
ADD_POS [k]=POS_FX [k]+POS_FX* [- k]
With
SUB_POS [k]=POS_FX [k]-POS_FX* [- k],
Wherein, POS_FX* [- k] is the conjugated signal of the frequency-region signal of the negative frequency point of each positive frequency point mirror image.
Step (5) successively calculates 2 parameter ADD_POS [k], SUB_POS [k] described in step (6) according to frequency point sequence
Amplitude absolute value ADD_POS_ABS [k], SUB_POS_ABS [k] and phase angle ADD_POS_ARG [k], SUB_POS_ARG
[k]。
Step (6) successively calculates useful signal positive frequency point k=1,2 ..., N/2-1 according to frequency point sequence, i.e. k=1,
2 ..., the gain compensation basic value of 127 corresponding Q railway digital matched filters
F ξ _ gain_pos (k)=ADD_POS_ABS [k]/SUB_POS_ABS [k]
With phase compensation basic value
F ξ _ arg_pos (k)=ADD_POS_ARG [k]-SUB_POS_ARG [k].
Step (7) meets the relationship of conjugation, therefore the gain compensation base based on each positive frequency point due to the offset of positive and negative frequency point
Plinth value F ξ _ gain_pos (k) and the gain compensation value for defining each frequency point without mirror image frequency point are 0, can calculate each frequency of frequency domain
The gain compensation value of point
Phase compensation basic value F ξ _ arg_pos (k) and definition based on the corresponding digital matched filter of each positive frequency point
The phase compensation value of each frequency point of no mirror image frequency point is 0, can calculate the phase compensation value of each frequency point
Step (8), obtained according to frequency point sequence the deviation F ξ (k) for needing the to carry out frequency domain compensation=F ξ of 256 frequency points _
Gain (k) * [cos (F ξ _ arg (k))+j*sin (F ξ _ arg (k))], k=-N/2 ..., N/2-1, i.e. k=-128 ..., -1,
1,…,127。
Step (9), each frequency point is needed to carry out frequency domain compensation deviation carry out the i.e. 256 point IFFT operation of N point to get
To 256 tap coefficients of the Q railway digital matched filter of corresponding 80M data sampling rate.T before retaining, such as 12 are effectively taken out
Head coefficient matches compensating filter to get the T rank for having arrived final corresponding 80M data sampling rate, i.e. 12 rank time domains.
Receiver frequency dependence I/Q signal provided by the present embodiment is calibrated and compensated method, effectively eliminates receiver
The problem of frequency domain correlation IQ mismatch that the devices such as analog baseband filter generate, it can effectively promote 802.11ac system receiver
The performance of demodulating and decoding.
The invention patent provides a kind of receiver frequency dependence IQ mismatch calibration based on FFT operation and compensation side
Method.This method is by increasing a digital matched filter on the road digital baseband I of receiver or the road Q, to compensate in RF access
The IQ mismatch of the frequency dependence due to caused by analog filter and radio-frequency devices.And the calculating of digital matched filter coefficient passes through
Calibration algorithm obtains, and calibration process is to send the positive compound calibration signal of frequency point in transmitter, receiving after the calibrated access of signal
Machine obtains the size of each positive frequency point signal of frequency domain and its negative frequency point signal of mirror image by FFT operation, big according to above two signal
The small deviation for successively calculating each frequency point and needing to carry out frequency domain compensation transports each frequency point frequency domain compensation deviation by IFFT
It calculates, obtains the tap coefficient on the road I or Q railway digital matched filter.The method can effectively eliminate the filtering of receiver Analog Baseband
The devices such as device generate frequency domain correlation IQ mismatch the problem of, can effectively improve I/Q signal calibration accuracy, promoted broadband without
The overall performance of line communication.
According to the disclosed embodiment, those skilled in the art can be realized or using the present invention.It is described above real
Applying example is only presently preferred embodiments of the present invention, is not intended to limit the invention, all within the spirits and principles of the present invention,
Any modification, equivalent replacement, improvement and so on, it is within the scope of the present invention.
Claims (6)
1. it is a kind of based on the frequency dependence IQ mismatch calibration of FFT operation and compensation method, for including transmitter and reception
The frequency dependence IQ mismatch of the Wireless Broadband Communication Systems of machine is calibrated and compensated, it is characterised in that: in the receiver
The road digital baseband I or the road Q increase a digital matched filter, the tap coefficient of the digital matched filter is by being based on
The calibration of FFT operation obtains, and receiver mould in the Wireless Broadband Communication Systems is compensated by the digital matched filter
Frequency dependence IQ mismatch in quasi- access.
2. according to claim 1 based on the frequency dependence IQ mismatch calibration of FFT operation and compensation method, feature exists
In: the method for the tap coefficient of the digital matched filter is obtained by the calibration based on FFT operation are as follows: in the transmitter
Send the compound calibration signal of positive frequency point, simulation school of the positive compound calibration signal of frequency point Jing Guo the Wireless Broadband Communication Systems
Digital baseband part by FFT operation obtains the frequency-region signal and each positive frequency point of each positive frequency point in the receiver after quasi- access
The frequency-region signal of the negative frequency point of corresponding mirror image, calculates according to the frequency-region signal of the frequency-region signal of each positive frequency point and its negative frequency point of mirror image
Each frequency point needs to carry out the deviation of frequency domain compensation, then the deviation that each frequency point needs to carry out frequency domain compensation is passed through
IFFT operation obtains the tap coefficient of the digital matched filter.
3. according to claim 2 based on the frequency dependence IQ mismatch calibration of FFT operation and compensation method, feature exists
In: by the calibration based on FFT operation obtain the tap coefficient of the digital matched filter method the following steps are included:
Step (1): the Wireless Broadband Communication Systems are switched into frequency dependence IQ calibration mode, and in the WiMAX
IQ analog calibration access is established in communication system；
Step (2): the positive compound calibration signal of frequency point, the positive compound school of frequency point are generated in the digital baseband of the transmitter
Calibration signal by the transmitter transmitting link, the IQ analog calibration access, the receiver receives link, export to
The digital baseband of the receiver；
Step (3): the digital baseband of the receiver calls FFT module to carry out FFT operation to signal is received, and obtains the positive frequency
The frequency-region signal POS_FX [k] of the corresponding each frequency point of the compound calibration signal of point is simultaneously corresponding as the positive compound calibration signal of frequency point
FFT result and save, the frequency points that the FFT operation uses for N, k be frequency point serial number, k=-N/2 ..., N/2-1, frequency
Point serial number k=1,2 ..., N/2-1 correspond to positive frequency point, corresponding 0 frequency point of k=0, k=-1, and -2 ..., the negative frequency point of-N/2 correspondence, frequency point
The identical negative frequency point of serial number absolute value and positive frequency point mirror image frequency point each other；
Step (4): according to frequency point sequence, for k=1, the positive frequency point of 2 ..., N/2-1 successively calculates ADD_POS [k]=POS_
FX [k]+POS_FX* [- k] and SUB_POS [k]=POS_FX [k]-POS_FX* [- k], wherein POS_FX* [- k] is each positive frequency
The conjugated signal of the frequency-region signal of the negative frequency point of point mirror image；
Step (5): the amplitude absolute value ADD_POS_ABS of ADD_POS [k], SUB_POS [k] are successively calculated according to frequency point sequence
[k], SUB_POS_ABS [k] and phase angle ADD_POS_ARG [k], SUB_POS_ARG [k]；
Step (6): successively calculating k=1,2 according to frequency point sequence ..., the corresponding digital matched filtering of the positive frequency point of N/2-1
Gain compensation basic value F ξ _ gain_pos (k) of device=ADD_POS_ABS [k]/SUB_POS_ABS [k] and phase compensation basis
Value F ξ _ arg_pos (k)=ADD_POS_ARG [k]-SUB_POS_ARG [k]；
Step (7): the gain compensation basic value based on the corresponding digital matched filter of each positive frequency point calculates each frequency
The gain compensation value of point
Phase compensation basic value based on the corresponding digital matched filter of each positive frequency point calculates the phase of each frequency point
Offset
Step (8): deviation F ξ (k)=F ξ _ gain that each frequency point needs to carry out frequency domain compensation is obtained according to frequency point sequence
(k) * [cos (F ξ _ arg (k))+j*sin (F ξ _ arg (k))], k=-N/2 ..., N/2-1；
Step (9): the deviation for needing to carry out frequency domain compensation to each frequency point carries out the IFFT operation of N point, obtains the number
N number of tap coefficient with filter.
4. according to claim 3 based on the frequency dependence IQ mismatch calibration of FFT operation and compensation method, feature exists
In: in the step (1), the signal that frequency mixer in the transmission link of the transmitter exports is directly inputted to the receiver
Receives link frequency mixer and establish the IQ analog calibration access.
5. according to claim 3 based on the frequency dependence IQ mismatch calibration of FFT operation and compensation method, feature exists
In: in the step (2), it is positive and negative 1 random number, imaginary part that the positive compound calibration signal of frequency point, which is to each positive frequency point real part,
It is 0, is 0 signal to each negative frequency point and the 0 frequency point real and imaginary parts.
6. according to claim 3 based on the frequency dependence IQ mismatch calibration of FFT operation and compensation method, feature exists
In: in the step (11), T effective T rank tap coefficients of the tap coefficient as the digital matched filter before choosing.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201810882335.9A CN109104201B (en) | 2018-08-06 | 2018-08-06 | Frequency correlation IQ mismatch calibration and compensation method based on FFT operation |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201810882335.9A CN109104201B (en) | 2018-08-06 | 2018-08-06 | Frequency correlation IQ mismatch calibration and compensation method based on FFT operation |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN109104201A true CN109104201A (en) | 2018-12-28 |
| CN109104201B CN109104201B (en) | 2020-08-18 |
Family
ID=64848699
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201810882335.9A Expired - Fee Related CN109104201B (en) | 2018-08-06 | 2018-08-06 | Frequency correlation IQ mismatch calibration and compensation method based on FFT operation |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN109104201B (en) |
Cited By (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN109861706A (en) * | 2019-02-27 | 2019-06-07 | 中国电子科技集团公司第五十四研究所 | A kind of broadband zero intermediate frequency reciver quadrature mismatch compensation device and method |
| CN110677201A (en) * | 2019-10-23 | 2020-01-10 | 中国科学院微电子研究所 | Frequency domain compensation and calibration method |
| CN112051555A (en) * | 2020-08-18 | 2020-12-08 | 上海理工大学 | Digital IQ calibration method based on complex signal spectrum operation |
| CN112888025A (en) * | 2021-01-12 | 2021-06-01 | 深圳市极致汇仪科技有限公司 | Method and system for processing received WIFI data based on extended bandwidth |
| CN114900200A (en) * | 2022-05-18 | 2022-08-12 | 青岛柯锐思德电子科技有限公司 | UWB receiver front-end data processing method based on digital mixing |
| CN115276944A (en) * | 2022-07-19 | 2022-11-01 | 深圳市极致汇仪科技有限公司 | Integrated tester, and method and system for compensating signal IQ (in-phase quadrature) circuit clock deviation by integrated tester |
| CN116707666A (en) * | 2023-05-30 | 2023-09-05 | 南京朗立微集成电路有限公司 | Method and equipment for correcting IQ imbalance of WiFi transmitter |
Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1728694A (en) * | 2004-07-09 | 2006-02-01 | Sst通信公司 | RF receiver mismatches calibration system and method |
| US20080310534A1 (en) * | 2007-06-18 | 2008-12-18 | Yoshimasa Egashira | Wireless communication method and wireless communication apparatus |
| CN101627599A (en) * | 2007-03-09 | 2010-01-13 | 高通股份有限公司 | Quadrature imbalance estimation using unbiased training sequences |
| CN101969321A (en) * | 2010-11-09 | 2011-02-09 | 北京理工大学 | FFT (Fast Fourier Transform) based large frequency offset secondary catching method of direct sequence spread spectrum system |
| CN102447663A (en) * | 2010-10-07 | 2012-05-09 | 美信集成产品公司 | Digital correction of analog polyphase filters |
| CN104639490A (en) * | 2015-01-27 | 2015-05-20 | 电子科技大学 | Joint estimation and compensation method for frequency-dependent IQ (In-phase Quadrature) mismatch and channel |
| CN107819710A (en) * | 2016-09-12 | 2018-03-20 | 深圳市中兴微电子技术有限公司 | I/Q mismatch compensation method and apparatus, compensation equipment and communication equipment |
-
2018
- 2018-08-06 CN CN201810882335.9A patent/CN109104201B/en not_active Expired - Fee Related
Patent Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1728694A (en) * | 2004-07-09 | 2006-02-01 | Sst通信公司 | RF receiver mismatches calibration system and method |
| CN101627599A (en) * | 2007-03-09 | 2010-01-13 | 高通股份有限公司 | Quadrature imbalance estimation using unbiased training sequences |
| US20080310534A1 (en) * | 2007-06-18 | 2008-12-18 | Yoshimasa Egashira | Wireless communication method and wireless communication apparatus |
| CN102447663A (en) * | 2010-10-07 | 2012-05-09 | 美信集成产品公司 | Digital correction of analog polyphase filters |
| CN101969321A (en) * | 2010-11-09 | 2011-02-09 | 北京理工大学 | FFT (Fast Fourier Transform) based large frequency offset secondary catching method of direct sequence spread spectrum system |
| CN104639490A (en) * | 2015-01-27 | 2015-05-20 | 电子科技大学 | Joint estimation and compensation method for frequency-dependent IQ (In-phase Quadrature) mismatch and channel |
| CN107819710A (en) * | 2016-09-12 | 2018-03-20 | 深圳市中兴微电子技术有限公司 | I/Q mismatch compensation method and apparatus, compensation equipment and communication equipment |
Cited By (10)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN109861706A (en) * | 2019-02-27 | 2019-06-07 | 中国电子科技集团公司第五十四研究所 | A kind of broadband zero intermediate frequency reciver quadrature mismatch compensation device and method |
| CN110677201A (en) * | 2019-10-23 | 2020-01-10 | 中国科学院微电子研究所 | Frequency domain compensation and calibration method |
| CN110677201B (en) * | 2019-10-23 | 2022-03-01 | 中国科学院微电子研究所 | Frequency domain compensation and calibration method |
| CN112051555A (en) * | 2020-08-18 | 2020-12-08 | 上海理工大学 | Digital IQ calibration method based on complex signal spectrum operation |
| CN112051555B (en) * | 2020-08-18 | 2023-07-25 | 上海理工大学 | Digital IQ calibration method based on complex signal spectrum operation |
| CN112888025A (en) * | 2021-01-12 | 2021-06-01 | 深圳市极致汇仪科技有限公司 | Method and system for processing received WIFI data based on extended bandwidth |
| CN114900200A (en) * | 2022-05-18 | 2022-08-12 | 青岛柯锐思德电子科技有限公司 | UWB receiver front-end data processing method based on digital mixing |
| CN115276944A (en) * | 2022-07-19 | 2022-11-01 | 深圳市极致汇仪科技有限公司 | Integrated tester, and method and system for compensating signal IQ (in-phase quadrature) circuit clock deviation by integrated tester |
| CN116707666A (en) * | 2023-05-30 | 2023-09-05 | 南京朗立微集成电路有限公司 | Method and equipment for correcting IQ imbalance of WiFi transmitter |
| CN116707666B (en) * | 2023-05-30 | 2024-04-05 | 南京朗立微集成电路有限公司 | Method and equipment for correcting IQ imbalance of WiFi transmitter |
Also Published As
| Publication number | Publication date |
|---|---|
| CN109104201B (en) | 2020-08-18 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN109104201A (en) | Based on the frequency dependence IQ mismatch calibration of FFT operation and compensation method | |
| US8559571B2 (en) | Method and apparatus for beamforming of multi-input-multi-output (MIMO) orthogonal frequency division multiplexing (OFDM) transceivers | |
| JP4261578B2 (en) | Wireless communication apparatus and reception method | |
| US8233524B2 (en) | Radio transmitter IQ imbalance measurement and correction methods and apparatus | |
| US8995572B1 (en) | Digital Predistortion for nonlinear RF power amplifiers | |
| CN104717172B (en) | IQ imbalance compensations method and apparatus in a kind of emitter | |
| US7986755B2 (en) | Method and apparatus for calibration for beamforming of multi-input-multi-output (MIMO) orthogonol frequency division multiplexing (OFDM) transceivers | |
| CN105847198B (en) | The IQ imbalances of OFDM-WLAN radio frequency test systems estimate and compensation method | |
| CN114374593B (en) | IQ imbalance compensation method for WiFi broadband transceiving path and application | |
| CN102176708A (en) | Calibration of transmit and receive chains in a mimo communication system | |
| EP2839620B1 (en) | Technique for calibrating a receiver apparatus | |
| WO2014044581A1 (en) | Loopback technique for iq imbalance estimation for calibration in ofdm systems | |
| CN110380996B (en) | Frequency-dependent IQ imbalance compensation method in SC-FDE system | |
| CN108616469B (en) | Method and device for estimating and compensating IQ imbalance of receiving end of SC-FDE system | |
| CN106161304B (en) | A kind of transmitting terminal IQ imbalance compensation method of joint channel estimation | |
| CN110278167A (en) | A kind of pair of IQ imbalance carries out the continuous wireless communications method estimated with compensation | |
| US20090213724A1 (en) | Method and system for i/q branch equalization in ofdm systems | |
| US20060245522A1 (en) | Method and apparatus for adjusting symbol timing and/or symbol positioning of a receive burst of data within a radio receiver | |
| Lin et al. | Joint adaptive transmitter/receiver IQ imbalance correction for OFDM systems | |
| KR20090065410A (en) | Transmitter and receiver for high throughput wireless communication system with multiple antenna, test for the transmitter and receiver | |
| CN111786922B (en) | OFDM system IQ imbalance and channel joint estimation method based on NLS | |
| US10979262B2 (en) | IQ mismatch correction for zero-IF/low-IF TX/RX | |
| Liu et al. | Low-complexity calibration of joint TX/RX I/Q imbalance in wideband direct-conversion transceiver | |
| US20110150131A1 (en) | Apparatus and method for processing digital transmission/reception signals to correct in-band gain flatness | |
| WO2017156786A1 (en) | Signal processing method and related device |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant | ||
| CF01 | Termination of patent right due to non-payment of annual fee | ||
| CF01 | Termination of patent right due to non-payment of annual fee |
Granted publication date: 20200818 |