CN108988928B - Method for detecting double-channel single-pulse angle error in frequency domain - Google Patents

Method for detecting double-channel single-pulse angle error in frequency domain Download PDF

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CN108988928B
CN108988928B CN201810499063.4A CN201810499063A CN108988928B CN 108988928 B CN108988928 B CN 108988928B CN 201810499063 A CN201810499063 A CN 201810499063A CN 108988928 B CN108988928 B CN 108988928B
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/14—Relay systems
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    • G01S19/01—Satellite radio beacon positioning systems transmitting time-stamped messages, e.g. GPS [Global Positioning System], GLONASS [Global Orbiting Navigation Satellite System] or GALILEO
    • G01S19/13—Receivers
    • G01S19/23—Testing, monitoring, correcting or calibrating of receiver elements
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    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S19/00—Satellite radio beacon positioning systems; Determining position, velocity or attitude using signals transmitted by such systems
    • G01S19/01—Satellite radio beacon positioning systems transmitting time-stamped messages, e.g. GPS [Global Positioning System], GLONASS [Global Orbiting Navigation Satellite System] or GALILEO
    • G01S19/13—Receivers
    • G01S19/24—Acquisition or tracking or demodulation of signals transmitted by the system
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Abstract

The invention discloses a method for detecting a double-channel single-pulse angle error in a frequency domain, and belongs to the technical field of self-tracking of radio frequency antennas. The method comprises the processing steps of FFT processing of a sum signal and a difference signal receiving channel, correlation and accumulation of the sum signal and the difference signal, filtering between FFT frames, normalization and the like, and realizes the detection of the single pulse angle error with high performance. The invention carries out digital demodulation of the angle error based on the frequency domain, has the advantages of various workable signals, high response speed, high integration degree, low workable signal-to-noise ratio, convenient time delay correction, high phase correction precision and the like, and is an important improvement on the prior art.

Description

Method for detecting double-channel single-pulse angle error in frequency domain
Technical Field
The invention relates to the technical field of radio frequency antenna self-tracking, in particular to a monopulse tracking technology of a parabolic multi-mode feed source antenna used for satellite communication, and particularly relates to a method for detecting a double-channel monopulse angle error in a frequency domain.
Background
Currently, most single pulse tracking receivers employ single-channel angular error detection methods, such as various modulated envelope detection methods or correlation detection methods. However, a single channel causes that the tracking receiver needs to work under a higher signal-to-noise ratio, some single-pulse tracking receivers adopt a dual-channel time-domain-based angular error detection method, and the time-domain angular error demodulation can only realize lower delay correction precision and phase correction precision, and has weak adaptability to signal bandwidth and signal types.
Disclosure of Invention
In view of the above, the present invention provides a method for detecting a single pulse angle error in a frequency domain, which can operate at a lower signal-to-noise ratio, can conveniently perform high-precision delay correction and phase correction, and can be adapted to continuous signals with various bandwidths, such as: single-frequency signals, modulation signals with various bandwidths, and even noise signals with broadband (such as signal sources of sun, radio star, and the like); by adding corresponding functional modules, the system can also adapt to discontinuous signals such as TDMA, frequency hopping, pulse modulation and the like.
Based on the above purpose, the technical scheme provided by the invention is as follows:
a method for detecting a double-channel single-pulse angle error in a frequency domain is applied to the following scenes:
the sum signal and the difference signal generated by the antenna feed source are respectively subjected to the same low-noise amplification, analog down-conversion and gain amplification, then the sum signal and the difference signal are respectively subjected to the same and synchronous A/D conversion, digital zero intermediate frequency orthogonal processing and sampling rate extraction conversion, and then respectively subjected to the same 2NWindowing FFT processing of points; the effective bandwidth of the signal corresponds to the interval of the FFT output frequency point [ -m, m [ -m [ ]]M is a positive integer;
the method comprises the following steps:
(1) taking complex conjugate for all points in the output effective interval of sum signal FFT, and taking complex conjugate for n-th point of sum signal FFT
Figure BDA0001669839830000021
The nth point delta corresponding to the effective output interval of the difference signal FFTnPerforming complex multiplication to obtain related frequency spectrum
Figure BDA0001669839830000022
(2) Correlating the spectrum at all points within the effective bandwidth of the signal
Figure BDA0001669839830000023
The delay-difference correction of (2) is performed,wherein the time delay difference is tau, the frequency interval of adjacent spectral lines output by FFT is omega, e is a natural constant, and j is an imaginary unit;
(3) all the correlated spectra in the effective bandwidth after time delay correction
Figure BDA0001669839830000024
Are accumulated, the accumulated result is
Figure BDA0001669839830000025
(4) The energy spectrums of all frequency points in the effective bandwidth are calculated and accumulated for the output of the sum signal FFT, and the accumulation result is
Figure BDA0001669839830000026
(5) Energy spectrum accumulation calculated for different FFT frames in continuous time
Figure BDA0001669839830000027
With correlation spectrum accumulation
Figure BDA0001669839830000028
Filtering frames and reducing the sampling rate respectively to obtain sum signal energy sigma and a correlation value delta with the sampling rate suitable for output;
(6) calculating a normalization value of an inter-frame filtering result
Figure BDA0001669839830000029
(7) Calculating the power of the sum signal from sigma, based on
Figure BDA00016698398300000210
The angular error of the antenna is calculated.
As can be seen from the above description, the beneficial effects of the present invention are:
1. the invention can realize the single pulse digital demodulation of the frequency domain and can conveniently finish the delay correction and the phase correction of the channel. Compared with the traditional realization scheme of single-pulse time domain demodulation, the method has great improvement on the adaptability of signal bandwidth and the precision of correction parameters;
2. the invention uses a dual-channel demodulation mode to normalize the sum and difference signals of the accumulated result. Compared with the traditional realization scheme of single-channel and time-domain demodulation, the method can work under the condition of lower signal-to-noise ratio (improved by more than 6 dB);
3. the invention can be suitable for the single pulse demodulation of various continuous signals, such as single-frequency signals, modulation signals of various bandwidths, even signals in a section of frequency in broadband signals, noise signals and the like; by adding corresponding functional modules, the system can also be suitable for discontinuous signals such as TDMA, frequency hopping, pulse modulation and the like;
4. the invention can adopt high-speed digital chips such as a high-speed FPGA (field programmable gate array), a DSP (digital signal processing) chip or a GPU (graphic processing unit) as hardware cores, and the device manufactured by the principle has the advantages of high integration degree, small volume, simple structure, high reliability, easy upgrading and the like.
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In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings used in the description of the embodiments or the prior art will be briefly described below, it is obvious that the drawings in the following description are only some embodiments of the present invention, and for those skilled in the art, other drawings can be obtained according to the drawings without creative efforts.
FIG. 1 is a schematic block diagram of a dual channel single pulse tracking receiver for angular error detection in the frequency domain in an embodiment of the present invention;
FIG. 2 shows an embodiment of the present invention in which a non-single frequency sum signal and a difference signal are respectively passed through 2NAn amplitude spectrogram after point FFT processing; in FIG. 2, the 3dB bandwidth of the non-single frequency signal corresponds to the post-FFT processed [ -m, m]Range, point n is [ -m, m]At any point in the range, m and n are positive integers; when the bandwidth of the signal is greater than [ -m, m [ -m [ ]]In range of [ -m, m [ - ]]Then the maximum bandwidth which can be realized by FFT processing number and does not cause aliasing is taken;
FIG. 3 shows a single-frequency sum signal and difference signal respectively passing through 2NAn amplitude spectrogram after point FFT processing; in FIG. 3, the single frequency signal plus Hanning (Hanning) window and FFT processed main lobe corresponds to three points n-1, n +1, etc., where the nth point is the maximum amplitude point, [ -m, m]Is the maximum bandwidth of the FFT process that does not cause aliasing.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is described in further detail below with reference to the accompanying drawings in conjunction with specific embodiments.
A method for detecting the angle error of a double-channel monopulse in a frequency domain assumes that the signal processing processes of a sum signal processing channel and a difference signal processing channel sequentially comprise the following steps:
1. after the received radio frequency signal passes through two paths of identical low-noise amplification and analog down converters, the frequency of the received signal is converted to a proper central frequency and adjusted to a proper amplitude, and the sum signal and the difference signal processed by the analog down converter are assumed to be respectively:
Figure BDA0001669839830000031
wherein ω is1Is the center frequency of the sum signal, theta (-) is the phase function of the received signal with zero mean, a (-) is the amplitude envelope function of the received signal, mu is the current normalized difference slope, phi is the angle of the antenna from the satellite axis,
Figure BDA0001669839830000032
to synthesize the error angle, γ is the phase of the difference signal relative to the sum signal, and τ is the delay difference of the sum-difference receiving channel.
2. The signals are converted into digital signals through synchronous high-speed A/D with the same sampling rate.
3. The digital signal is converted to a zero intermediate frequency complex signal using a synchronous digital down converter.
4. Two paths of complex signals are converted into a proper sampling rate through synchronous sampling rate extraction and conversion, and the sum signal and the difference signal after the processing are respectively assumed to be:
Figure BDA0001669839830000041
wherein, ω is0Is the center frequency of the sum signal residual small enough, γ' is the fixed phase of the difference signal relative to the sum signal, e is a natural constant (equal to about 2.71828), and j is the imaginary unit.
5. The complex signal is processed by synchronous windowing function and then is processed by 2NFFT (fast fourier transform) processing of the points.
6. And performing subsequent single pulse demodulation processing on the two FFT processing results. According to the time shift property of frequency domain transformation, and the arbitrary nth point spectrum expression in the signal bandwidth [ -m, m ] after the signal and the difference signal are respectively subjected to FFT processing is as follows:
Figure BDA0001669839830000042
wherein, anTo sum the amplitude, θ, of the signal FFT-processed nth point spectrumnIn order to sum the phase of the n-th point spectrum after the signal FFT processing, ω is the frequency difference between adjacent spectral lines after the signal FFT processing, m is the frequency point of the FFT corresponding to the effective bandwidth of the signal (usually 3dB bandwidth), and m and n are both positive integers.
The method performs single-pulse angular error demodulation on the processed signals of the two receiving channels, as shown in fig. 1, and includes the following steps:
(1) complex conjugate is taken for all points in the output effective interval of the sum signal FFT, and the complex conjugate of the nth point of the sum signal is taken
Figure BDA0001669839830000043
The nth point delta corresponding to the effective output interval of the difference signal FFTnPerforming complex multiplication to obtain related frequency spectrum
Figure BDA0001669839830000044
In particular, the present invention relates to a method for producing,the following cases are divided:
(101) for wideband signals, performing all corresponding points within the effective bandwidth
Figure BDA0001669839830000045
The sum signal FFT processed spectrogram, shown in FIG. 2, has a signal bandwidth of [ -m, m ] according to equation (3)]The conjugate of the arbitrary nth point spectrum is
Figure BDA0001669839830000046
The sum and difference correlation spectra are therefore:
Figure BDA0001669839830000047
(102) for the signal with single frequency, different points are selected according to different added window functions, for example, a Hanning window takes 3 points, and a rectangular window takes 5 or 7 points.
As shown in fig. 3, a frequency spectrum diagram of a single-frequency signal after FFT processing and a frequency spectrum of the nth point of the signal corresponding to the maximum amplitude are calculated by taking the frequency spectrums of three points n-1, n, and n +1 when a hanning window is added before FFT processing, where the point n may be any point located within the maximum bandwidth [ -m, m ] that can be processed by FFT.
(2) Correlating spectra at all points within the signal bandwidth
Figure BDA0001669839830000051
Wherein the time delay difference is tau, and the frequency interval of adjacent spectral lines of the FFT output is omega.
Figure BDA0001669839830000052
Specifically, the following cases are classified:
(201) for the time delay correction of the broadband signal, the time delay correction can be selected to be carried out in an effective interval of the FFT output of the sum signal, wherein the nth point is multiplied by ejnωτ(ii) a Alternatively, the difference signal is output within an effective interval of FFT output, where the nth point is multiplied by e-jnωτ(ii) a And when the time delay is large, the method can be carried out in a time domain matched with a frequency domain.
The condition for which a delay correction has to be made is that the signal satisfies
Figure BDA0001669839830000053
Namely satisfy
Figure BDA0001669839830000054
I.e. may be considered a broadband signal.
(202) For single frequency signals or satisfy
Figure BDA0001669839830000055
The narrow-band signal of (2) may not be corrected for delay.
The condition for not performing the time delay correction is that
Figure BDA0001669839830000056
I.e. the effect of the delay tau is small enough to be considered a narrowband signal.
To be at
Figure BDA0001669839830000057
Preferably, the delay correction is performed.
The time delay of the single-frequency signal can be eliminated by phase correction, so that time delay correction is not needed.
(3) Effective bandwidth after time delay correction [ -m, m]All of the relevant spectra therein
Figure BDA0001669839830000058
Performing complex number accumulation to obtain an accumulation result
Figure BDA0001669839830000059
Figure BDA00016698398300000510
(4) The energy spectrums of all frequency points in the effective bandwidth are calculated and accumulated for the output of the sum signal FFT, and the accumulation result is
Figure BDA00016698398300000511
Calculating the energy spectrum of the frequency point n in the effective bandwidth, namely adding the square of the real part and the square of the imaginary part to obtain
Figure BDA00016698398300000512
Thus, the energy of the summed signal spectrum can be summed as:
Figure BDA00016698398300000513
(5) energy spectrum accumulation calculated for different FFT frames in continuous time
Figure BDA0001669839830000061
With correlation spectrum accumulation
Figure BDA0001669839830000062
And respectively filtering frames and reducing the sampling rate to respectively obtain sum signal energy sigma and a correlation value delta with the sampling rate suitable for output.
FFT of each frame obtains a DC form sum signal energy value
Figure BDA0001669839830000063
And correlation value
Figure BDA0001669839830000064
The FFT frame rate for wideband signals may be up to 1M times/sec, and a high sampling rate may involve too wide a noise bandwidth, thus requiring noise filtering and a reduction in the output sampling rate. The simplest average down-sampling, Cascaded CIC (integrated-comb Cascaded) down-sampling, or FIR (Finite Impulse Response) down-sampling, half-band filtering down-sampling, FORROW filtering down-sampling and other filtering down-sampling modes can be used, and after filtering down-sampling of FFT interframe output values, sum signal energy can be filtered
Figure BDA0001669839830000065
And correlation value
Figure BDA0001669839830000066
The noise contained in (a).
(6) Calculating a normalization value of an inter-frame filtering result
Figure BDA0001669839830000067
Figure BDA0001669839830000068
The normalization value may be calculated before or after the FFT inter-frame filtering. For a broadband signal with low signal-to-noise ratio, noise contained in signal energy can be better filtered by calculating a normalization value after the FFT interframe filtering, so that the fluctuation of an output error signal is reduced.
(7) Calculating the power of the sum signal from sigma, based on
Figure BDA0001669839830000069
The angular error of the antenna is calculated.
Equation (8) is the standard complex angular error, and the channel phase shift γ' can be corrected with high precision in digital processing, and then the angular error of the antenna can be obtained.
Those of ordinary skill in the art will understand that: the discussion of any embodiment above is meant to be exemplary only, and is not intended to intimate that the scope of the disclosure, including the claims, is limited to these examples. Any omissions, modifications, substitutions, improvements and the like in the foregoing embodiments are intended to be included within the scope of the present invention within the spirit and principle of the present invention.

Claims (1)

1. A method for detecting a double-channel single-pulse angle error in a frequency domain is characterized by being applied to the following scenes:
the sum signal and the difference signal generated by the antenna feed source are respectively subjected to the same low-noise amplification, analog down-conversion and amplificationAmplifying, subjecting the sum signal and the difference signal to the same and synchronous A/D conversion, digital zero intermediate frequency orthogonal processing, sampling rate extraction conversion, and performing the same 2NWindowing FFT processing of points; the effective bandwidth of the signal corresponds to the interval [ (m, m ] of the FFT output frequency point, and m is a positive integer;
the method comprises the following steps:
(1) taking complex conjugate for all frequency points in the output effective interval of sum signal FFT, and taking complex conjugate for the nth frequency point of the sum signal
Figure FDA0002547450370000011
The nth frequency point delta corresponding to the effective output interval of the difference signal FFTnPerforming complex multiplication to obtain related frequency spectrum
Figure FDA0002547450370000012
(2) The related frequency spectrums of all frequency points in the effective bandwidth of the signal are processed
Figure FDA0002547450370000013
Correcting the time delay difference, wherein the time delay difference is tau, the frequency interval of adjacent spectral lines output by FFT is omega, e is a natural constant, and j is an imaginary unit;
(3) all the correlated spectra in the effective bandwidth after time delay correction
Figure FDA0002547450370000014
Are accumulated, the accumulated result is
Figure FDA0002547450370000015
(4) The energy spectrums of all frequency points in the effective output interval are calculated and accumulated for the output of the sum signal FFT, and the accumulation result is
Figure FDA0002547450370000016
(5) Energy spectrum accumulation result calculated for different FFT frames in continuous time
Figure FDA0002547450370000017
And the correlation spectrum accumulation result
Figure FDA0002547450370000018
Filtering frames and reducing the sampling rate respectively to obtain sum signal energy sigma and a correlation value delta with the sampling rate suitable for output;
(6) calculating a normalization value of an inter-frame filtering result
Figure FDA0002547450370000019
(7) Calculating the power of the sum signal from sigma, based on
Figure FDA00025474503700000110
The angular error of the antenna is calculated.
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