CN108490256B - Multi-spectral-line-based PSK signal two-channel phase difference obtaining method and device - Google Patents
Multi-spectral-line-based PSK signal two-channel phase difference obtaining method and device Download PDFInfo
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Abstract
The invention relates to a method for acquiring a phase difference of two channels of a PSK signal based on a multispectral line, belongs to the technical field of digital signal processing, and solves the problem that the calculation accuracy of the phase difference of the two channels is low under the condition of low signal-to-noise ratio in the prior art. The method specifically comprises the following steps: carrying out synchronous AD sampling on PSK signals of two channels, wherein the total number of sampling points of each channel is N; selecting any one of the two channels as a reference channel, and solving the steady power spectral density of a sampling signal of the reference channel; determining all phase difference spectral lines in the estimated bandwidth of the channel sampling signal according to the steady power spectral density of the reference channel sampling signal; and solving the phase difference of the two channels of the PSK signal according to the phase difference spectral line. And a corresponding device is obtained according to the method for obtaining the phase difference of the two channels of the PSK signal based on the multispectral line, so that the purpose of obtaining the phase difference of the two channels of the PSK signal with higher precision under the condition of low signal-to-noise ratio is realized, and the method is also suitable for the condition of high signal-to-noise ratio.
Description
Technical Field
The invention relates to the technical field of digital signal processing, in particular to a method and a device for acquiring a phase difference of two channels of a Phase Shift Keying (PSK) signal based on a multispectral line.
Background
The phase difference between two receiving channels of the same radiation source signal has important application in the fields of interferometer direction finding, signal synthesis, phased array antenna and the like.
Under the condition of higher signal-to-noise ratio, the traditional two-channel signal phase difference calculation result based on the maximum spectral line method can generally meet the application requirement. However, under low signal-to-noise ratio conditions, the performance degradation of the conventional method is significant. The multi-channel signal phase difference acquisition technology under the condition of low signal-to-noise ratio is a hot problem of domestic and foreign research.
For low signal-to-noise ratio signals, the traditional method improves the calculation accuracy of the phase difference of the two channels at the cost of enlarging the sample length. However, in practical studies, it has been found that long-time sampling is not always allowed before the phase difference calculation result is given, and the radiation source is not likely to radiate signals for a long time. In this case, the phase difference calculation result is caused to be less accurate.
Disclosure of Invention
In view of the foregoing analysis, the present invention aims to provide a method and an apparatus for obtaining a two-channel phase difference of a PSK signal based on multiple spectral lines, so as to solve the problem of low accuracy of a two-channel phase difference calculation result under a low signal-to-noise ratio condition.
The purpose of the invention is mainly realized by the following technical scheme:
on one hand, a method for acquiring a phase difference of two channels of a PSK signal based on a multispectral line is provided, which specifically comprises the following steps:
carrying out synchronous AD sampling on PSK signals of two channels, wherein the total number of sampling points of each channel is N;
selecting any one of the two channels as a reference channel, and solving the steady power spectral density of a sampling signal of the reference channel;
determining all phase difference spectral lines in the estimated bandwidth of the channel sampling signal according to the steady power spectral density of the reference channel sampling signal;
and acquiring the phase difference of the two channels of the PSK signal according to the phase difference spectral line.
The invention has the following beneficial effects: the method for acquiring the phase difference between the two channels of the PSK signal based on the multiple spectral lines provided by this embodiment makes full use of the phase difference information included in multiple spectral lines of the signal, and improves the phase difference calculation accuracy of two receiving channels of the PSK signal of the same radiation source in the environment with a low signal-to-noise ratio.
On the basis of the scheme, the invention is further improved as follows:
further, after the sampling results of the two channels are respectively cached, the robust power spectral density of the reference channel sampling signal is obtained.
The beneficial effect of adopting the further scheme is that: by caching the sampling result, the number of sampling points of each channel can be determined, and the sampling result is subjected to subsequent processing after being received.
Further, the reference channel is sampled with a signal xNIs divided into k sections without overlapping and then,
k＝N/M (1)
wherein, M is the number of sampling points of each section, and N is the total number of sampling points.
The beneficial effect of adopting the further scheme is that: by segmenting the reference channel sampling signal, a spectral line with higher resolution can be obtained.
Further, the reference channel is sampled with a signal xNIs divided into k sections with overlap, half of the adjacent two sections of sampling signals are overlapped,
wherein, M is the number of sampling points of each section, and N is the total number of sampling points.
The beneficial effect of adopting the further scheme is that: by providing another optional sampling signal segmentation mode, the sampling signal can be segmented according to actual needs by people in the field, and a spectral line with higher resolution is obtained.
Further, the obtaining the robust power spectral density of the reference channel sampling signal includes:
adding a rectangular window to the ith segment of the sampling signal to obtain a result
Wherein n is the serial number of the sampling point, i is the number of the segments of the sampling signal, d1[n+(i-1)M]The sampling window is a rectangular window, and the length of the window is the number M of sampling points in each section;
respectively calculating the power spectrum of the sampled signal after each section is added with a rectangular window
Omega is the frequency of the sampling signal;
obtaining an average periodogram of the sampled signal
Determining robust power spectral density
Wherein P (omega) is the theoretical maximum power spectrum of the sampling signal, w1(M) is a triangular window of length 2M-1, M is w1(m) sequence of sample points, D1(ω) is the frequency spectrum of a rectangular window of length M, W1(ω) is w obtained by autocorrelation of a rectangular window of length M1(m) spectrum.
The beneficial effect of adopting the further scheme is that: the method for calculating the steady power spectral density of the sampled signal is provided, the density of different frequency components contained in the power spectral density of the signal is fully utilized, and the signal bandwidth information is effectively reflected.
Further, M is 32.
The beneficial effect of adopting the further scheme is that: aiming at the two situations that no overlapping exists in the sampling signals and overlapping exists in the sampling signals, the number M of each sampling point can be set to be 32, the PSD result stability of the signals is good, and the segmentation is not too thin to cause large calculation amount.
Further, according to the robust power spectral density of the reference channel sampling signal, determining all phase difference spectral lines in the channel sampling signal estimation bandwidth, specifically:
extracting spectral line L corresponding to maximum power spectral density in reference channel sampling signal steady power spectral density function0；
Extraction line L0Left spectral line LaWhich is said spectral line L0The first root on the left side satisfies La-1、LaThe power spectral densities corresponding to +1 are all larger than the spectral line LaThe corresponding spectral line of the power spectral density;
extraction line L0Spectral line L on the rightbWhich is said spectral line L0The first root on the right side satisfies Lb-1、LbThe power spectral densities corresponding to +1 are all larger than the spectral line LbThe corresponding spectral line of the power spectral density;
La、Lband all spectral lines in between are all phase difference spectral lines in the channel sampling signal estimation bandwidth.
The beneficial effect of adopting the further scheme is that: the method comprises the steps of firstly obtaining a spectral line corresponding to the maximum power spectral density, taking the spectral line as a center, selecting a plurality of spectral lines meeting a certain condition, obtaining a more accurate phase difference calculation result by utilizing a large amount of phase difference information contained in the spectral lines, and avoiding the problem that the accuracy rate of the phase difference calculation result is reduced under the condition of low signal-to-noise ratio only by a single spectral line.
Further, acquiring a phase difference of two channels of the PSK signal according to the phase difference spectral line, comprising:
respectively determining spectral lines La、LbThe corresponding spectral line in the FFT result of the sampled signal is
M is the number of sampling points of each section;
calculating to obtain a phase difference complex vector Z of sampling signals of two channels of the PSK signal:
wherein the content of the first and second substances,
sampling the conjugate of the p point result of the FFT for the reference channel; x2(p) is the result of sampling the p-th point of the signal FFT for another channel; r is1(p) is
A die of r2(p) is X2(p) a modulus; phi is a1(p) is
Phase of (phi)2(p) is X2(p) a phase;
and extracting phase information of the phase difference complex vector Z to obtain the phase difference of the two channels of the PSK signal.
The beneficial effect of adopting the further scheme is that: the method has the advantages that the signal phase information contained in a plurality of spectral lines of the signal is fully utilized, namely, the phases contained in all spectral lines in the signal estimation bandwidth are weighted and averaged, the calculation accuracy of the phase difference of the two channels under the condition of low signal-to-noise ratio can be effectively improved, and the method is also suitable under the condition of high signal-to-noise ratio.
On the other hand, a two-channel phase difference obtaining device for a PSK signal based on multiple spectral lines is provided, which specifically includes:
the signal sampling module is used for carrying out synchronous AD sampling on the PSK signals of the two channels, and the total number of sampling points of each channel is N;
the robust power spectral density calculating module is used for selecting any one of the two channels as a reference channel and calculating the robust power spectral density of the sampling signal of the reference channel;
the phase difference spectral line determining module is used for determining all phase difference spectral lines in the estimation bandwidth of the channel sampling signal according to the steady power spectral density of the reference channel sampling signal;
and the two-channel phase difference acquisition module is used for acquiring the two-channel phase difference of the PSK signal according to the phase difference spectral line.
The device corresponds to the method for acquiring the phase difference of the two channels of the PSK signal based on the multispectral line.
In the invention, the technical schemes can be combined with each other to realize more preferable combination schemes. Additional features and advantages of the invention will be set forth in the description which follows, and in part will be obvious from the description, or may be learned by practice of the invention. The objectives and other advantages of the invention will be realized and attained by the structure particularly pointed out in the written description and claims hereof as well as the appended drawings.
Drawings
The drawings are only for purposes of illustrating particular embodiments and are not to be construed as limiting the invention, wherein like reference numerals are used to designate like parts throughout.
FIG. 1 is a flow chart of a method for obtaining a phase difference of two channels of a PSK signal based on multiple spectral lines;
FIG. 2 is a PSD function simulation result for a typical PSK signal;
fig. 3 is a flowchart of a two-channel phase difference obtaining apparatus for a PSK signal based on multiple spectral lines;
FIG. 4 shows the simulation results of PSD function for certain BSPK signals;
FIG. 5a) is a phase difference result obtained by the method of the present application;
fig. 5b) shows the phase difference results obtained with the N-point maximum line method.
Detailed Description
The accompanying drawings, which are incorporated in and constitute a part of this application, illustrate preferred embodiments of the invention and together with the description, serve to explain the principles of the invention and not to limit the scope of the invention.
A specific embodiment of the present invention discloses a method for acquiring a phase difference between two channels of a PSK signal based on multiple spectral lines, and a flowchart is shown in fig. 1.
When in implementation, the method specifically comprises the following steps:
step S1: carrying out synchronous AD sampling on PSK signals of two channels, wherein the total number of sampling points of each channel is N;
step S2: selecting any one of the two channels as a reference channel, and calculating the steady Power Spectral Density (PSD) of a sampling signal of the reference channel;
step S3: determining all phase difference spectral lines in the estimated bandwidth of the channel sampling signal according to the steady power spectral density of the reference channel sampling signal;
step S4: and acquiring the phase difference of the two channels of the PSK signal according to the phase difference spectral line.
Compared with the prior art, the method for acquiring the phase difference between the two channels of the PSK signal based on the multiple spectral lines provided by the embodiment makes full use of the phase difference information contained in the multiple spectral lines of the signal, and improves the phase difference calculation accuracy of the two receiving channels of the PSK signal with the same radiation source in the environment with low signal-to-noise ratio.
Optionally, after the step S1, the sampling results of the two channels may be buffered respectively, and then the step S2 may be performed. By caching the sampling result, the number of sampling points of each channel can be determined, the integrity of the sampling result is ensured, the subsequent processing is facilitated, and the accuracy of the processing result is improved.
The bandwidth information of the signal can be effectively reflected by considering that the power spectral density of the signal represents the density of different frequency components contained in the signal. In order to obtain a reliable calculation result of the signal bandwidth, based on the above embodiments, an embodiment of the present invention may further analyze the power spectral density of the signal by using a windowed averaging algorithm.
In particular, estimating the robust power spectral density of the sampled signal may comprise the steps of,
sampling a reference channel with a signal xNIs divided into k sections without overlapping and then,
k＝N/M (1)
wherein, M is the number of sampling points of each section, and N is the total number of sampling points.
In another embodiment, the reference channel is sampled for signal xNIs divided into k sections with overlap, half of the adjacent two sections of sampling signals are overlapped,
wherein, M is the number of sampling points of each section, and N is the total number of sampling points.
By segmenting the reference channel sampling signal, a spectral line with higher resolution can be obtained.
Adding a rectangular window to the ith segment of the sampling signal to obtain a result
Wherein n is the serial number of the sampling point, i is the number of the segments of the sampling signal, d1[n+(i-1)M]The sampling window is a rectangular window, and the length of the window is the number M of sampling points in each section;
respectively calculating the power spectrum of the sampled signal after each section is added with a rectangular window
Omega is the frequency of the sampling signal;
obtaining an average periodogram of the sampled signal
Determining robust power spectral density
Wherein P (omega) is the theoretical maximum power spectrum of the sampling signal, w1(M) is of length 2M-1Triangular window, m is w1(m) sequence of sample points, D1(ω) is the frequency spectrum of a rectangular window of length M, W1(ω) is w obtained by autocorrelation of a rectangular window of length M1(m) spectrum.
Preferably, for the two cases that the sampling signals are not overlapped and are overlapped, the number M of sampling points in each segment is set to be 32, at this time, the PSD result of the signal is good in stability, and the segmentation is not too thin to cause a large amount of calculation.
Fig. 2 is a graph of the robust power spectral density obtained using the above method.
Determining all phase difference spectral lines in the estimated bandwidth of the channel sampling signal according to the robust power spectral density of the reference channel sampling signal, specifically:
the step 3 further comprises:
step S31: extracting spectral line L corresponding to maximum power spectral density in reference channel sampling signal steady power spectral density function0；
Step S32: extraction line L0Left spectral line LaWhich is said spectral line L0The first root on the left side satisfies La-1、LaThe power spectral densities corresponding to +1 are all larger than the spectral line LaThe corresponding spectral line of the power spectral density;
step S33: extraction line L0Spectral line L on the rightbWhich is said spectral line L0The first root on the right side satisfies Lb-1、LbThe power spectral densities corresponding to +1 are all larger than the spectral line LbThe corresponding spectral line of the power spectral density;
La、Lband all spectral lines in between are all phase difference spectral lines in the channel sampling signal estimation bandwidth.
The method comprises the steps of firstly obtaining a spectral line corresponding to the maximum power spectral density, taking the spectral line as a center, selecting a plurality of spectral lines meeting a certain condition, obtaining a more accurate phase difference calculation result by utilizing a large amount of phase difference information contained in the spectral lines, and avoiding the problem that the accuracy rate of the phase difference calculation result is reduced under the condition of low signal-to-noise ratio only by a single spectral line.
The step 4 further comprises the following steps:
step S41: respectively determining spectral lines La、LbThe corresponding spectral line in the FFT result of the sampled signal is
Step S42: calculating to obtain a phase difference complex vector Z of sampling signals of two channels of the PSK signal:
wherein the content of the first and second substances,sampling the conjugate of the p point result of the FFT for the reference channel; x2(p) is the result of sampling the p-th point of the signal FFT for another channel; r is1(p) isA die of r2(p) is X2(p) a modulus; phi is a1(p) is
Phase of (phi)2(p) is X2(p) a phase;
step S43: and extracting phase information of the phase difference complex vector Z to obtain the phase difference of the two channels of the PSK signal.
The method makes full use of the signal phase information contained in a plurality of spectral lines of the signal, namely, the phases contained in all spectral lines in the signal estimation bandwidth are weighted and averaged, the calculation accuracy of the phase difference of the two channels under the condition of low signal-to-noise ratio can be effectively improved, and the method is also applicable under the condition of high signal-to-noise ratio.
And designing a corresponding device according to the method for acquiring the phase difference of the two channels of the PSK signal based on the multispectral line, wherein a flow chart of the corresponding device is shown in FIG. 3.
The following describes the respective processes and effects of the above-described embodiment methods with specific examples.
The present embodiment selects BPSK signals, the carrier frequency is 80MHz, the signal bandwidth is 17kHz, the bandpass sampling frequency fs is 4.5649 × 105Hz, the number of sampling points is 1024 points, the matching bandwidth signal-to-noise ratio SNR is 0dB, and the phase difference between the two channels is 55 °. The robust power spectral density estimation is performed using the above embodiment step S2, wherein the length of each segment signal is specifically selected to be 32 points, overlapping 50%. FIG. 4 shows a robust power spectral density function obtained from a simulation, according to step S3a＝7×32＝224，lb＝11×32＝352。
For the BPSK signal, 1000 simulations are performed, and fig. 5a) shows the channel phase difference obtained based on the multi-spectral method proposed in the present application in the 1000 simulations, and the mean square error rms of the phase difference result is counted to be 5.07 °. Fig. 5b) shows the channel phase difference estimated by the conventional maximum spectral line method, and the mean square error rms of the phase difference result is counted to be 13.5 °. The analysis can be carried out, and based on the method for obtaining the phase difference of the two channels of the PSK signal based on the multispectral line, the accuracy of the phase difference calculation result is obviously superior to that of the estimation result based on the traditional multispectral line method.
The above description is only for the preferred embodiment of the present invention, but the scope of the present invention is not limited thereto, and any changes or substitutions that can be easily conceived by those skilled in the art within the technical scope of the present invention are included in the scope of the present invention.
Claims (10)
1. A PSK signal two-channel phase difference obtaining method based on multiple spectral lines is characterized by comprising the following steps:
carrying out synchronous AD sampling on PSK signals of two channels, wherein the total number of sampling points of each channel is N;
selecting any one of the two channels as a reference channel, and solving the steady power spectral density of a sampling signal of the reference channel;
determining all phase difference spectral lines in the estimated bandwidth of the channel sampling signal according to the steady power spectral density of the reference channel sampling signal;
and acquiring the phase difference of the two channels of the PSK signal according to the phase difference spectral line.
2. The method according to claim 1, wherein robust power spectral density of a reference channel sampled signal is obtained after buffering sampling results of two channels respectively.
3. The method of claim 1, wherein a reference channel is sampled for signal xNIs divided into k sections without overlapping and then,
k＝N/M (1)
wherein, M is the number of sampling points of each section, and N is the total number of sampling points.
4. The method of claim 1, wherein a reference channel is sampled for signal xNIs divided into k sections with overlap, half of the adjacent two sections of sampling signals are overlapped,
wherein, M is the number of sampling points of each section, and N is the total number of sampling points.
5. The method according to claim 3 or 4, wherein the obtaining the robust power spectral density of the reference channel sample signal comprises:
adding a rectangular window to the ith segment of the sampling signal to obtain a result
Wherein n is the serial number of the sampling point, i is the sampling signalNumber of stages of number, d1[n+(i-1)M]The sampling window is a rectangular window, and the length of the window is the number M of sampling points in each section;
respectively calculating the power spectrum of the sampled signal after each section is added with a rectangular window
Omega is the frequency of the sampling signal;
obtaining an average periodogram of the sampled signal
Determining robust power spectral density
Wherein P (omega) is the theoretical maximum power spectrum of the sampling signal, w1(M) is a triangular window of length 2M-1, M is w1(m) sequence of sample points, D1(ω) is the frequency spectrum of a rectangular window of length M, W1(ω) is w obtained by autocorrelation of a rectangular window of length M1(m) spectrum.
6. The method of claim 3 or 4, wherein M is 32.
7. The method according to claim 1, wherein the determining, according to the robust power spectral density of the reference channel sample signal, all phase difference spectral lines within an estimated bandwidth of the channel sample signal includes:
extracting spectral line L corresponding to maximum power spectral density in reference channel sampling signal steady power spectral density function0；
Extraction line L0Left spectral line LaWhich is said spectral line L0The first root on the left side satisfies La-1、LaThe power spectral densities corresponding to +1 are all larger than the spectral line LaThe corresponding spectral line of the power spectral density;
extraction line L0Spectral line L on the rightbWhich is said spectral line L0The first root on the right side satisfies Lb-1、LbThe power spectral densities corresponding to +1 are all larger than the spectral line LbThe corresponding spectral line of the power spectral density;
La、Lband all spectral lines in between are all phase difference spectral lines in the channel sampling signal estimation bandwidth.
8. The method according to claim 7, wherein obtaining the two-channel phase difference of the PSK signal according to the phase difference spectral line includes:
respectively determining spectral lines La、LbThe corresponding spectral line in the FFT result of the sampled signal is
M is the number of sampling points of each section;
calculating to obtain a phase difference complex vector Z of sampling signals of two channels of the PSK signal:
wherein the content of the first and second substances,
sampling the conjugate of the p point result of the FFT for the reference channel; x2(p) is the result of sampling the p-th point of the signal FFT for another channel; r is1(p) is
A die of r2(p) is X2(p) a modulus; phi is a1(p) is
Phase of (phi)2(p) is X2(p) a phase;
and extracting phase information of the phase difference complex vector Z to obtain the phase difference of the two channels of the PSK signal.
9. A two-channel phase difference obtaining device for PSK signals based on multiple spectral lines is characterized by comprising:
the signal sampling module is used for carrying out synchronous AD sampling on the PSK signals of the two channels, and the total number of sampling points of each channel is N;
the robust power spectral density calculating module is used for selecting any one of the two channels as a reference channel and calculating the robust power spectral density of the sampling signal of the reference channel;
the phase difference spectral line determining module is used for determining all phase difference spectral lines in the estimation bandwidth of the channel sampling signal according to the steady power spectral density of the reference channel sampling signal;
and the two-channel phase difference acquisition module is used for acquiring the two-channel phase difference of the PSK signal according to the phase difference spectral line.
10. The apparatus according to claim 9, wherein the phase difference spectral line obtaining module comprises:
a maximum power spectral density extraction module for extracting the most stable power spectral density function of the reference channel sampling signalSpectral line L corresponding to high power spectral density0；
A first spectral line extraction module for extracting the spectral line L0Left spectral line LaWhich is said spectral line L0The first root on the left side satisfies La-1、LaThe power spectral densities corresponding to +1 are all larger than the spectral line LaThe corresponding spectral line of the power spectral density;
a second spectral line extraction module for extracting the spectral line L0Spectral line L on the rightbWhich is said spectral line L0The first root on the right side satisfies Lb-1、LbThe power spectral densities corresponding to +1 are all larger than the spectral line LbThe corresponding spectral line of the power spectral density;
a phase difference spectral line determining module for determining La、LbAll spectral lines in between are all phase difference spectral lines in the channel sampling signal estimation bandwidth;
the two-channel phase difference acquisition module comprises:
corresponding spectral line determining module for determining spectral line La、LbCorresponding spectral lines in FFT results of sampled signalsM is the number of sampling points of each section;
and the phase difference complex vector calculation module is used for calculating and obtaining a phase difference complex vector Z of the sampling signals of the two channels of the PSK signal:
wherein the content of the first and second substances,
sampling the conjugate of the p point result of the FFT for the reference channel; x2(p) is the result of sampling the p-th point of the signal FFT for another channel; r is1(p) isA die of r2(p) is X2(p) a modulus; phi is a1(p) is
Phase of (phi)2(p) is X2(p) a phase;
and the PSK signal two-channel phase difference determining module is used for extracting the phase information of the phase difference complex vector Z to obtain the phase difference of the PSK signal two channels.
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Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2006098099A (en) * | 2004-09-28 | 2006-04-13 | Secom Co Ltd | Moving body detection device |
| CN1946071A (en) * | 2006-10-25 | 2007-04-11 | 中国电子科技集团公司第五十四研究所 | Method for single path detecting input signal phase difference and relative amplitude |
| CN104991225A (en) * | 2015-06-23 | 2015-10-21 | 中国电子科技集团公司第三十六研究所 | Method and device for direction finding ambiguity resolution of phase interferometer |
| CN105022059A (en) * | 2015-07-01 | 2015-11-04 | 南京森斯尔智能科技有限公司 | Coherent-processing multi-target tracking method of security monitoring radar system |
| CN106646348A (en) * | 2017-01-24 | 2017-05-10 | 成都泰格微电子研究所有限责任公司 | Interferometer phase difference measurement circuit and interferometer phase difference measurement method applicable to short-time multi-frequency signals |
-
2018
- 2018-03-15 CN CN201810214626.0A patent/CN108490256B/en active Active
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2006098099A (en) * | 2004-09-28 | 2006-04-13 | Secom Co Ltd | Moving body detection device |
| CN1946071A (en) * | 2006-10-25 | 2007-04-11 | 中国电子科技集团公司第五十四研究所 | Method for single path detecting input signal phase difference and relative amplitude |
| CN104991225A (en) * | 2015-06-23 | 2015-10-21 | 中国电子科技集团公司第三十六研究所 | Method and device for direction finding ambiguity resolution of phase interferometer |
| CN105022059A (en) * | 2015-07-01 | 2015-11-04 | 南京森斯尔智能科技有限公司 | Coherent-processing multi-target tracking method of security monitoring radar system |
| CN106646348A (en) * | 2017-01-24 | 2017-05-10 | 成都泰格微电子研究所有限责任公司 | Interferometer phase difference measurement circuit and interferometer phase difference measurement method applicable to short-time multi-frequency signals |
Non-Patent Citations (2)
| Title |
|---|
| "相位差方法校正多通道AD采集高精度时间误差";黄磊 等;《电子世界》;20160408;第35-38页 * |
| "通道间相位差求解算法分析";师鹏宇 等;《雷达与对抗》;20110315;第31卷(第1期);第45-47页 * |
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