CN108123554B - Wireless power transmission system based on low-stress inverter - Google Patents
Wireless power transmission system based on low-stress inverter Download PDFInfo
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- CN108123554B CN108123554B CN201810035378.3A CN201810035378A CN108123554B CN 108123554 B CN108123554 B CN 108123554B CN 201810035378 A CN201810035378 A CN 201810035378A CN 108123554 B CN108123554 B CN 108123554B
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- 230000005540 biological transmission Effects 0.000 title claims abstract description 17
- 239000003990 capacitor Substances 0.000 claims abstract description 45
- 238000010586 diagram Methods 0.000 description 3
- 238000004088 simulation Methods 0.000 description 3
- NAWXUBYGYWOOIX-SFHVURJKSA-N (2s)-2-[[4-[2-(2,4-diaminoquinazolin-6-yl)ethyl]benzoyl]amino]-4-methylidenepentanedioic acid Chemical compound C1=CC2=NC(N)=NC(N)=C2C=C1CCC1=CC=C(C(=O)N[C@@H](CC(=C)C(O)=O)C(O)=O)C=C1 NAWXUBYGYWOOIX-SFHVURJKSA-N 0.000 description 2
- 238000002955 isolation Methods 0.000 description 2
- 238000000034 method Methods 0.000 description 2
- 230000009286 beneficial effect Effects 0.000 description 1
- 230000007547 defect Effects 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
- H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
- H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/4815—Resonant converters
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Computer Networks & Wireless Communication (AREA)
- Inverter Devices (AREA)
Abstract
The invention discloses a wireless power transmission system based on a low-stress inverter, which comprises the low-stress inverter, a transmitting part, a receiving part and a load, wherein the low-stress inverter is used as a high-frequency power source of the wireless power transmission system, the transmitting part comprises a transmitting coil and a first capacitor connected with the transmitting coil, the receiving part comprises a receiving coil and a second capacitor connected with the receiving coil, and the receiving part transmits received electric energy to the load. The invention is characterized in that: firstly, a switching tube of the inverter has lower voltage stress; secondly, the inverter has higher electric energy transmission efficiency; third, the operating frequency of the system can reach more than MHz. In practical applications, the corresponding power levels and frequencies may be designed according to requirements.
Description
Technical Field
The invention relates to the technical field of wireless power transmission, in particular to a wireless power transmission system based on a low-stress inverter.
Background
The high-frequency inverter power supply in the wireless power transmission system is always a hot problem of research, and common high-frequency inverter power supplies comprise an E-type inverter, a D-type inverter and a full-bridge inverter circuit. In the application occasion with larger power, a class D inverter and a full-bridge inverter circuit are commonly used, in high frequency, a bootstrap or isolation circuit is required to be added for driving an upper tube so as to achieve the purpose of ground isolation with a lower tube, the design difficulty of the whole inverter is certainly increased, two switching tubes in the upper bridge arm and the lower bridge arm are simultaneously conducted due to false triggering of electromagnetic interference, and a large current flows through the switching tubes, so that the switching tubes are burnt, and the working frequency of the class D inverter and the full-bridge inverter circuit is greatly limited. The class E inverter only uses one switching tube, so that the class E inverter can work at a higher frequency, but the switching tube in the class E inverter has larger switching stress, so that the power class of the whole circuit is greatly limited.
Disclosure of Invention
The invention aims to overcome the defects and shortcomings of the prior art, and provides a wireless power transmission system based on a low-stress inverter, which is reasonable and reliable in structure and simple to control, wherein the working frequency of the system can reach more than MHz, and in practical application, the corresponding power level and frequency can be designed according to requirements.
In order to achieve the above purpose, the technical scheme provided by the invention is as follows: a wireless power transmission system based on a low-stress inverter comprises the low-stress inverter, a transmitting part, a receiving part and a load; the low-stress inverter comprises a direct-current voltage source, a choke coil, a switching tube, a resonant inductor, a resonant capacitor and a switching tube parallel capacitor, the transmitting part comprises a transmitting coil and a first capacitor connected with the transmitting coil, the receiving part comprises a receiving coil and a second capacitor connected with the receiving coil, and the receiving part transmits received electric energy to a load; the direct-current voltage source comprises a direct-current voltage source, a switch tube, a resonant inductor, a drain electrode, a choke coil, a transmitting coil, a receiving coil and a transmitting coil, wherein the negative electrode of the direct-current voltage source is connected with a source electrode of the switch tube, one end of the switch tube parallel capacitor and one end of the resonant inductor respectively, the other end of the resonant inductor is connected with one end of the resonant capacitor, the other end of the resonant capacitor is connected with the other end of the switch tube parallel capacitor, the drain electrode of the switch tube, one end of the choke coil and one end of the transmitting coil respectively, the other end of the choke coil is connected with the positive electrode of the direct-current voltage source, one end of the first capacitor is connected with the other end of the transmitting coil, one end of the receiving coil is connected with one end of the second capacitor, the other end of the second capacitor is connected with one end of the load, and the other end of the receiving coil is connected with the other end of the receiving coil.
When the low-stress inverter works in an optimal state, the conditions of zero-voltage turn-on and zero-voltage derivative turn-on are met.
The operating frequency of the low stress inverter, the resonant frequency of the transmitting portion, and the resonant frequency of the receiving portion are the same.
The frequency range is 0.5MHz to 50MHz.
The resonant frequency of the resonant inductor and the resonant capacitor is 2 times of the switching frequency.
Compared with the prior art, the invention has the following advantages and beneficial effects:
1. the two ends of the switching tube in the low-stress inverter are connected in parallel with an LC branch, LC resonates at twice the frequency of the switching tube, and a channel is provided for the second harmonic of the circuit, so that the voltage stress of the switching tube can be reduced.
2. When proper circuit parameters are designed, the low-stress inverter can work at zero-voltage on and zero-voltage derivative on, so that the low-stress inverter has higher efficiency.
Therefore, the low-stress inverter is very suitable for being used as a high-frequency inverter power supply in a wireless power transmission system, and the working frequency of the system can reach more than MHz. In practical applications, the corresponding power levels and frequencies may be designed according to requirements.
Drawings
Fig. 1 is a circuit diagram of the system of the present invention.
Fig. 2 is a circuit diagram of a low stress inverter.
Fig. 3 is a simulation of the system of the present invention.
Fig. 4 is a simulated waveform diagram of the system of the present invention.
Detailed Description
The invention will be further illustrated with reference to specific examples.
As shown in fig. 1, the wireless power transmission system based on the low-stress inverter provided in the present embodiment includes a low-stress inverter (as a high-frequency power source of the wireless power transmission system), a transmitting portion, a receiving portion, and a load R L2 The method comprises the steps of carrying out a first treatment on the surface of the The low-stress inverter comprises a direct-current voltage source u DC Choke coil L F Switch tube Q and resonant inductance L M Resonance capacitor C M Parallel capacitor C of switch tube F The transmitting part comprises a transmitting coil L 1 And the transmitting coil L 1 Connected first capacitor C 1 The receiving part comprises a receiving coil L 2 And the receiving coil L 2 A second capacitor C connected with 2 The receiving part transmits the received electric energy to the load R L2 The method comprises the steps of carrying out a first treatment on the surface of the Wherein the direct current voltage source u DC The negative electrode of the switch tube is respectively connected with the source electrode of the switch tube Q and the switch tube parallel capacitor C F One end of (2) resonant inductance L M Is connected to one end ofThe resonant inductance L M And the other end of (C) and the resonance capacitor C M Is connected to one end of the resonant capacitor C M The other end of (2) is respectively connected with a switch tube in parallel with a capacitor C F The other end of the switch tube Q, the drain electrode of the switch tube Q, the choke coil L F Is a transmitting coil L 1 Is connected to one end of the choke coil L F And a DC voltage source u DC Positive electrode of (C), first capacitor C 1 Is connected to one end of the first capacitor C 1 And a transmitting coil L 1 Is connected to the other end of the receiving coil L 2 And a second capacitor C 2 Is connected to one end of the second capacitor C 2 And the other end of (2) and the load R L2 Is connected to one end of the load R L2 And a receiving coil L 2 Is connected to the other end of the pipe.
When the low-stress inverter works in an optimal state, the conditions of zero-voltage turn-on and zero-voltage derivative turn-on are met. The working frequency of the low-stress inverter, the resonant frequency of the transmitting part and the resonant frequency of the receiving part are the same, and the frequency range is 0.5 MHz-50 MHz. Resonant inductance L M Resonance capacitor C M Is 2 times the switching frequency.
The circuit of the low stress inverter is shown in fig. 2, and the specific parameter design analysis is as follows:
let the peak current flowing through the load be i RL1 Initial phase isThe expression of the load current can be written as follows:
in one period of switching on and switching off of the switching tube, the switching tube is turned on for 0 to ωt to 2pi D, and the switching tube is turned off for 2 pi D to ωt to 2pi.
When the switching tube is conducted, namely, ωt is more than or equal to 0 and is less than 2pi D, the current flowing through the switching tube can be obtained by a KCL equation as follows:
i Q (ωt)＝i DC -i M (ωt)-i RL1 (ωt) (2)
when the switching tube is turned on, the current flowing through the network is:
bringing formula (3) into (2) yields:
when the switch tube is turned off, namely 2 pi D is less than or equal to ωt and less than 2 pi, the current flows through the resonant network L M C M The current of (2) is:
i M (ωt)＝i DC -i RL1 (ωt)-i CF (ωt) (5)
capacitance C in (5) F Is set according to the current of (1):
when the switching tube is turned off, the resonant network L M C M The terminal voltage of (2) is equal to the voltage across the switching tube:
differentiating the left and right sides of the formula (7) simultaneously:
the combination of formula (5), formula (6) and formula (8) can be obtained:
the general solution of the solution formula (9) is shown as a formula (10):
middle of making typeThe formula (10) is simplified as follows:
the capacitance C can be obtained by the formulas (9) and (11) F The current of (2) is:
the drain voltage of the switching tube is obtained by the formulas (6) and (12) as follows:
according to the voltage volt-second area balance on the input inductor, the direct current component of the inductance voltage drop of the choke coil is zero, the average value of the drain voltage of the switching tube is equal to the direct current power supply voltage, and the average value of the formula (13) can be obtained:
from equation (14), and normalizing the drain voltage of the switching tube, we can obtain:
to ensure efficient operation of the entire inverter, the inverter needs to meet ZVS and ZVDS conditions, as obtainable by equations (12) and (13):
u Q (2π)＝0 (16)
i CF (2π)＝0 (17)
from the formulas (3) and (11), the inductor L can be flown through in one period M The current expression of (2) is as follows:
the boundary conditions being determined by the conditions of continuity of current and voltage when the switch is on and off, i.e
i M (2πD - )＝i M (2πD + ) (19)
i M (0)＝i M (2π) (20)
Since only the fundamental wave and the third harmonic of the drain voltage of the switching tube are considered, let the formula (13)The solution yields k=1.25.
The voltage stress of the switching tube can be determined by the formula (12):
the duty cycle is selected to be d=0.4 based on factors such as stability of the circuit, voltage stress and current stress of the switching tube. The corresponding parameters A can be obtained by combining the formulas (16), (17) and (19) to (22) 1 ＝-1.15,A 2 ＝-0.47,B 1 ＝-0.11,B 2 ＝-1.28,I RL1 /i DC ＝2.87。
Bringing the above parameters into formula (16) makes it possible to:
assuming that the power on the dc side is all transferred to the load, the power is conserved:
combining formula (24) and formula (25) can be obtained:
from formulae (26) and I RL1 /i DC =2.87, the capacitance C can be obtained F Is calculated as follows:
because ofCombined (27), capacitor C M Is calculated as follows:
inductance L M And capacitor C M Forms a resonant network, the resonant frequency is twice the switching frequency, and the inductor L is formed by combining (28) M Is calculated as follows:
switching tube drain voltage is L S And C S The resonance network only has the fundamental wave component passing, namely the output impedance part can be obtained by the fundamental wave component of the drain voltage of the switch tube, and the real part of the output impedance and the output current are in-phase and the imaginary part of the output impedance and the output current are orthogonal:
fourier analysis of the voltage of the switching tube:
inductance L X Can be calculated from the following formula:
bringing formula (30) into formula (31):
capacitor C S Can be determined by the following formula:
Q L for the load quality factor, it is generally selected to be 5 to 20.
Inductance L S And capacitor C S Resonance frequency is switching frequency, inductance L S Is calculated as follows:
choke coil inductance L F The choke coil inductance L is required to be large enough to suppress ripple current on the DC side F Is generally satisfied:
designed according to the above analysis. A set of wireless power transmission system samples based on a low-stress inverter is given here, dc voltage u DC =20v, switching frequency f=1 MHz, duty cycle d=0.4, inductance L of the receiving coil 2 =40μh, internal resistance R of receiving coil 2 =0.1Ω, load R L2 =100Ω, capacitance C 1 ＝C 2 = 633.25PF, converting load to R at transmitting end L1 Choke coil L of low-stress inverter=6.31Ω F =150μh, inductance L M =1.44 μh, capacitance C M = 4.398nF, capacitor C F = 3.5185nF, inductance ls+l X =10.04 μh, capacitance C S = 2.981nF, inductance L S And L X Incorporated into the transmitter coil, the self-inductance L of the transmitter coil can be designed 1 Internal resistance R of transmitting coil = 50.04 μh 1 ＝0.12Ω，C 1 The simulation of wireless power transmission PSIM can be established according to the above parameters, as shown in fig. 3, and the corresponding simulation result is shown in fig. 4, and it can be seen from fig. 4 that the two switching tubes meet the requirement of soft switching.
The above embodiments are only preferred embodiments of the present invention, and are not intended to limit the scope of the present invention, so variations in shape and principles of the present invention should be covered.
Claims (2)
1. A wireless power transmission system based on a low-stress inverter, characterized in that: comprises a low-stress inverter, a transmitting part, a receiving part and a load; the low-stress inverter comprises a direct-current voltage source, a choke coil, a switching tube, a resonant inductor, a resonant capacitor and a switching tube parallel capacitor, the transmitting part comprises a transmitting coil and a first capacitor connected with the transmitting coil, the receiving part comprises a receiving coil and a second capacitor connected with the receiving coil, and the receiving part transmits received electric energy to a load; the negative electrode of the direct-current voltage source is respectively connected with the source electrode of the switch tube, one end of the switch tube parallel capacitor and one end of the resonant inductor, the other end of the resonant inductor is connected with one end of the resonant capacitor, the other end of the resonant capacitor is respectively connected with the other end of the switch tube parallel capacitor, the drain electrode of the switch tube, one end of the choke coil and one end of the transmitting coil, the other end of the choke coil is connected with the positive electrode of the direct-current voltage source and one end of the first capacitor, the other end of the first capacitor is connected with the other end of the transmitting coil, one end of the receiving coil is connected with one end of the second capacitor, the other end of the second capacitor is connected with one end of the load, and the load is connected with the other end of the receiving coil; the working frequency of the low-stress inverter, the resonant frequency of the transmitting part and the resonant frequency of the receiving part are the same; the frequency range is 0.5 MHz-50 MHz; the resonant frequency of the resonant inductor and the resonant capacitor is 2 times of the switching frequency.
2. A low stress inverter based wireless power transmission system as defined in claim 1 wherein: when the low-stress inverter works in an optimal state, the conditions of zero-voltage turn-on and zero-voltage derivative turn-on are met.
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Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH1042572A (en) * | 1996-07-25 | 1998-02-13 | Matsushita Electric Works Ltd | Power supply unit |
| CN103586564A (en) * | 2013-10-28 | 2014-02-19 | 广东电网公司电力科学研究院 | MIG welding power supply system based on STM32 |
| GB201501733D0 (en) * | 2015-02-02 | 2015-03-18 | Drayson Wireless Ltd | Inverter for inductive power transfer |
| CN207835170U (en) * | 2018-01-15 | 2018-09-07 | 华南理工大学 | A kind of wireless power transmission systems based on low stress inverter |
-
2018
- 2018-01-15 CN CN201810035378.3A patent/CN108123554B/en active Active
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH1042572A (en) * | 1996-07-25 | 1998-02-13 | Matsushita Electric Works Ltd | Power supply unit |
| CN103586564A (en) * | 2013-10-28 | 2014-02-19 | 广东电网公司电力科学研究院 | MIG welding power supply system based on STM32 |
| GB201501733D0 (en) * | 2015-02-02 | 2015-03-18 | Drayson Wireless Ltd | Inverter for inductive power transfer |
| CN207835170U (en) * | 2018-01-15 | 2018-09-07 | 华南理工大学 | A kind of wireless power transmission systems based on low stress inverter |
Non-Patent Citations (1)
| Title |
|---|
| 磁谐振无线输电***E类逆变电路分析;周佳丽 等;北京交通大学学报;20151015;第39卷(第05期);第112页-第117页 * |
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