CN107743045B - Array antenna beam forming receiving device and weight coefficient optimization method thereof - Google Patents

Abstract

The present invention relates to communication technology. The invention solves the defects that the prior intelligent antenna receiver can cause the expected signal to be submerged by noise or interference under the condition of weak signal or strong interference, thereby leading the characteristic of the expected signal not to be extracted and causing the performance of the receiver to be greatly reduced, and overcomes the defects of low algorithm convergence speed and high system complexity, and provides an array antenna beam forming receiving device and a weight coefficient optimization method thereof, and the technical scheme can be summarized as follows: and for the input of each antenna, an analog complex multiplier is adopted to take the demodulated in-phase signal and orthogonal signal as a complex number to be multiplied by another complex number which is calculated by the signal processor through feedback and takes two parameters, real part signals and imaginary part signals of the multiplication result are output, and the obtained real part signals and the obtained imaginary part signals are respectively added and then output. The invention has the advantages of ensuring good beam characteristics, greatly improving the signal-to-noise ratio and the anti-interference capability and being suitable for a signal receiving system.

Description

Array antenna beam forming receiving device and weight coefficient optimization method thereof

Technical Field

The present invention relates to a communication technology, and more particularly, to a wireless signal reception technology.

Background

The intelligent antenna receiver can obviously improve the receiving signal-to-noise ratio, inhibit interference and greatly improve the performance of the receiver, and is an important direction for the development of a new generation of wireless communication technology. The existing smart antenna system generally adopts a digital beam forming technology, which demodulates a signal received by each antenna by radio frequency to obtain a baseband signal, then performs analog-to-digital conversion to obtain a digital signal, performs algorithm processing on each digital signal, then combines multiple signals to obtain an output, and usually adopts MMSE (Minimum Mean square Error), RLS (Recursive Least square) and LMS (Least Mean square) iterative algorithms. The problems existing in the prior art are as follows: under the condition of weak signals or strong interference, the expected signals are submerged by noise or interference, so that the characteristics of the expected signals cannot be extracted, and the performance of a receiver is greatly reduced; the adopted algorithm has low convergence speed and is difficult to track the rapidly changing signal direction; and the algorithm has high complexity and poor practicability.

Disclosure of Invention

The invention aims to overcome the defects that the performance of a receiver is greatly reduced because the characteristics of an expected signal cannot be extracted because the expected signal is submerged by noise or interference under the condition of weak signals or strong interference of the conventional intelligent antenna receiver and overcome the defects of low algorithm convergence speed and high system complexity, and provides an array antenna beam forming receiving device and a weight coefficient optimization method thereof.

The invention solves the technical problem, adopts the technical scheme that the array antenna beam forming receiving device comprises a plurality of antennas, a plurality of radio frequency filters and two system output ends, wherein the antennas correspond to the radio frequency filters one by one, each antenna is connected with the input end of the corresponding radio frequency filter, the array antenna beam forming receiving device is characterized by also comprising a signal processor, two summers, a plurality of parallel signal amplification and demodulation modules and a plurality of analog complex multipliers, the signal amplification and demodulation modules correspond to the analog complex multipliers one by one and correspond to the radio frequency filters one by one, the output end of each radio frequency filter is connected with the input end of the corresponding signal amplification and demodulation module, the in-phase output end and the orthogonal output end of each signal amplification and demodulation module are respectively connected with the two ends of one complex input end of the corresponding analog complex multiplier one by one, the two ends of the other complex input end of each analog complex multiplier are respectively connected with the two corresponding output ends of the signal processor in a one-to-one correspondence manner, the two ends of the complex output end of each analog complex multiplier are respectively connected with the input ends of the two adders in a one-to-one correspondence manner, the real part of an adder output signal and the imaginary part of another adder output signal, the output ends of the two adders are respectively two system output ends, two parallel output signals are generated, namely the system real part output signal and the system imaginary part output signal, a system output signal is formed and is a complex number, the signal processor is provided with two input ends which are correspondingly connected with the output ends of the two adders, and the signal processor is also provided with two input ends which are;

the signal amplification demodulation module is used for amplifying an input signal and then demodulating the amplified input signal;

the analog complex multiplier is used for multiplying an input in-phase signal and an input quadrature signal serving as a complex number by another complex number serving as two input parameters and outputting a real part signal and an imaginary part signal of a multiplication result, and the another complex number is a weight coefficient;

the signal processor is used for respectively calculating two parameters (the real part and the imaginary part of the other complex number recorded above) corresponding to the weight coefficient of each analog complex multiplier according to the input reference signal and the system output signal, and sending the parameters to the corresponding analog complex multipliers; only two parameters corresponding to the weight coefficient corresponding to one analog complex multiplier are calculated at the same time, and the two parameters corresponding to the weight coefficient of each analog complex multiplier are circularly calculated in sequence.

Specifically, the signal amplification and demodulation module comprises a radio frequency amplifier and a radio frequency demodulator, wherein the input end of the radio frequency amplifier is used as the input end of the signal amplification and demodulation module, and the output end of the radio frequency amplifier is connected with the input end of the radio frequency demodulator;

the radio frequency demodulator is used for demodulating an input signal, and an in-phase output end and a quadrature output end of the radio frequency demodulator are respectively used as an in-phase output end and a quadrature output end of the signal amplification demodulation module.

Further, the analog complex multiplier multiplies the input in-phase signal and the input quadrature signal as a complex number by another complex number which is input by two parameters, and outputs a real part signal and an imaginary part signal of a multiplication result, wherein a calculation formula is as follows:

Y_n＝Re(s_nw_n)

U_n＝Im(s_nw_n)

wherein, Y_nDenotes the real part signal, U, output from the nth analog complex multiplier_nDenotes the imaginary signal, s, output from the nth analog complex multiplier_nA complex number is the inphase signal and the orthogonal signal input by the nth analog complex multiplier

Refers to the in-phase signal input by the nth analog complex multiplier,

is the quadrature signal, w, input to the nth analog complex multiplier_nThe weight coefficient input by the nth analog complex multiplier is obtained

Refers to a parameter input to the nth analog complex multiplier,

the method is characterized in that the method refers to another parameter input by an nth analog complex multiplier, Re (eta)) refers to a real part taking operation, Im (eta)) refers to a virtual-real part operation, n is a positive integer which is greater than or equal to 1 and less than or equal to M, M is the number of analog complex multipliers and also is the number of antennas and is a positive integer which is greater than or equal to 1.

A weight coefficient optimization method of an array antenna beam forming receiving device is applied to the array antenna beam forming receiving device and is characterized in that the output signal of a system real part is set as

The imaginary output signal of the system is

The system output signal is V ═ Y + jU; let n antenna, at the k time, the corresponding weight coefficient is expressed as

Is provided with h⁽ⁿ⁾(k) For the steering function corresponding to the kth time of the nth antenna, d⁽ⁿ⁾(k) A step function corresponding to the kth moment of the nth antenna; let R be reference signal, it is a complex number, its real part and imaginary part are respectively inputted into signal processor by two input ends for inputting reference signal, the mean square error of system output signal and reference signal is E [ | V-R |)²]If the corresponding mean square error at the k-th time is E (k), where E is the averaging operation, the optimization method includes the following stepsThe method comprises the following steps:

step A1, randomly setting weight coefficient

And satisfy

Wherein C is a real constant; setting the guiding function value and the step length function value as h⁽¹⁾(1)＝1，d⁽¹⁾(1)＝D₀，D₀Obtaining a system output signal V and a reference signal R as a constant;

step a2, if k is equal to 1, the procedure proceeds to step A3, otherwise the following calculation is performed:

d⁽ⁿ⁾(k)＝h⁽ⁿ⁾(k-1)d⁽ⁿ⁾(k-1)

where ξ is a positive real number and 0< ξ < 1;

step A3, calculating a weight coefficient, wherein the calculation formula is as follows:

d⁽ⁿ⁾(k+1)＝h⁽ⁿ⁾(k)d⁽ⁿ⁾(k)

adjusting the weight coefficients according to:

|w₁(k)|²+|w₂(k)|²+...+|w_n(k+1)|²+...+|w_M(k)|²＝C

step A4, if | w_n(k+1)-w_n(k)|²Is less than or equal to positive real number close to zero, then enter step A5, otherwise let k → k +1 and return to step A2;

step A5, if n is less than M, n → n +1, and go back to step A3; if n is M, n → 1, let k → 1, h⁽ⁿ⁾(k) 1 and d⁽ⁿ⁾(k)＝D₀And returns to step a 3.

A weight coefficient optimization method of an array antenna beam forming receiving device is applied to the array antenna beam forming receiving device and is characterized in that the output signal of a system real part is set as

The imaginary output signal of the system is

The system output signal is V ═ Y + jU; let n antenna, at the k time, the corresponding weight coefficient is expressed as

Is provided with h⁽ⁿ⁾(k) For the steering function corresponding to the kth time of the nth antenna, d⁽ⁿ⁾(k) A step function corresponding to the kth moment of the nth antenna; let R be a reference signal, which is a complex number whose real part and imaginary part are input to the signal processor by two input terminals for inputting the reference signal,

for the correlation coefficient of the reference signal with the system output signal, the corresponding correlation coefficient at the k-th instant is r (k), p [ | V | ]²]For the output power of the system output signal, the corresponding output power at the k-th instant is p (k), where E is the averaging operation, the optimization method comprises the following steps:

step B1, randomly setting weight coefficient

And satisfy

Wherein C is a real constant, and the guiding function value and the step length function value are respectively set as h⁽¹⁾(1) 1 and d⁽¹⁾(1)＝D₀，D₀Obtaining a system output signal V and a reference signal R as a constant;

if k is equal to 1, the step B2 is executed, and if not, the step B3 is executed as follows:

d⁽ⁿ⁾(k)＝h⁽ⁿ⁾(k-1)d⁽ⁿ⁾(k-1)

where ξ is a positive real number and 0< ξ < 1;

step B3, calculating the weight coefficient, the calculation formula is:

d⁽ⁿ⁾(k+1)＝h⁽ⁿ⁾(k)d⁽ⁿ⁾(k)

adjusting the weight coefficients according to:

|w₁(k)|²+|w₂(k)|²+...+|w_n(k+1)|²+...+|w_M(k)|²＝C

step B4, if | w_n(k+1)-w_n(k)|²If the real number is less than or equal to the positive real number close to zero, the step B5 is entered, otherwise, the step K → k +1 is entered, and the step B2 is returned;

step B5, if | r (k +1) -r (k) & gtdoes not smoke²Eta is less than or equal to eta and r (k +1) is more than or equal to sigma, eta is a positive solid close to zeroIf the number σ is a pre-specified positive real number, let k → 1, h⁽ⁿ⁾(k) 1 and d⁽ⁿ⁾(k)＝D₀Go to step B6; otherwise, continuing to judge, if n < M, then n → n +1, returning to step B3, if n ═ M, then let n → 1, k → 1, h⁽ⁿ⁾(k) 1 and d⁽ⁿ⁾(k)＝D₀Returning to step B3;

if k is equal to 1, the step B6 is executed, and if not, the step B7 is executed as follows:

d⁽ⁿ⁾(k)＝h⁽ⁿ⁾(k-1)d⁽ⁿ⁾(k-1)

step B7, calculating the weight coefficient, the calculation formula is:

d⁽ⁿ⁾(k+1)＝h⁽ⁿ⁾(k)d⁽ⁿ⁾(k)

adjusting the weight coefficients according to:

|w₁(k)|²+|w₂(k)|²+...+|w_n(k+1)|²+...+|w_M(k)|²＝C

step B8, if | w_n(k+1)-w_n(k)|²If not, entering the step B9, otherwise, enabling k → k +1, and returning to the step B6;

step B9, if | r (k +1) -r (k) & gtdoes not smoke²Eta and | p (k +1) -p (k) & ltu & gt²≦ is a positive real number close to zero, let k → 1, h⁽ⁿ⁾(k) 1 and d⁽ⁿ⁾(k)＝D₀Returning to the step B6, otherwise, continuing to judge, if n is less than M, then n → n +1, returning to the step B3; if n is equal to M, let n → 1, k → 1, h⁽ⁿ⁾(k) 1 and d⁽ⁿ⁾(k)＝D₀And returns to step B3.

The array antenna beam forming receiving device comprises a plurality of antennas, a plurality of radio frequency filters and two system output ends, wherein the antennas correspond to the radio frequency filters one by one, each antenna is connected with the input end of the corresponding radio frequency filter, the array antenna beam forming receiving device is characterized by also comprising a signal processor, two summers, a plurality of parallel signal amplification and demodulation modules and a plurality of analog complex multipliers, the signal amplification and demodulation modules correspond to the analog complex multipliers one by one and correspond to the radio frequency filters one by one, the output end of each radio frequency filter is connected with the input end of the corresponding signal amplification and demodulation module, the in-phase output end and the orthogonal output end of each signal amplification and demodulation module are respectively connected with the two ends of one complex input end of the corresponding analog complex multiplier one by one and correspond to the input ends of the signal processor one by one, the two ends of the other complex input end of each analog complex multiplier are respectively connected with the two corresponding output ends of the signal processor in a one-to-one correspondence manner, the two ends of the complex output end of each analog complex multiplier are respectively connected with the input ends of the two adders in a one-to-one correspondence manner, the real part of an adder output signal and the imaginary part of another adder output signal, the output ends of the two adders are respectively two system output ends, two parallel output signals are generated, namely the system real part output signal and the system imaginary part output signal, a system output signal is formed and is a complex number, the signal processor is provided with two input ends which are correspondingly connected with the output ends of the two adders, and the signal processor is also provided with two input ends which are;

the signal amplification demodulation module is used for amplifying an input signal and then demodulating the amplified input signal;

the analog complex multiplier is used for multiplying an input in-phase signal and an input quadrature signal serving as a complex number by another complex number serving as two input parameters and outputting a real part signal and an imaginary part signal of a multiplication result, and the another complex number is a weight coefficient;

the signal processor is used for respectively calculating two parameters (the real part and the imaginary part of the other complex number recorded above) corresponding to the weight coefficient of each analog complex multiplier according to the input reference signal and the system output signal, and sending the parameters to the corresponding analog complex multipliers; only two parameters corresponding to a set of weight coefficients corresponding to a set of L analog complex multipliers are calculated at the same time, namely only a set of L weight coefficients (each weight coefficient comprises two parameters) are calculated at the same time, the two parameters corresponding to the weight coefficients of each analog complex multiplier are calculated according to sequential cyclic grouping, the number of the analog complex multipliers is M, M is the number of antennas, M is a positive integer greater than or equal to 1, and L is greater than or equal to 1 and is less than M.

Specifically, the signal amplification and demodulation module comprises a radio frequency amplifier and a radio frequency demodulator, wherein the input end of the radio frequency amplifier is used as the input end of the signal amplification and demodulation module, and the output end of the radio frequency amplifier is connected with the input end of the radio frequency demodulator;

the radio frequency demodulator is used for demodulating an input signal, and an in-phase output end and a quadrature output end of the radio frequency demodulator are respectively used as an in-phase output end and a quadrature output end of the signal amplification demodulation module.

Further, the analog complex multiplier multiplies the input in-phase signal and the input quadrature signal as a complex number by another complex number which is input by two parameters, and outputs a real part signal and an imaginary part signal of a multiplication result, wherein a calculation formula is as follows:

Y_n＝Re(s_nw_n)

U_n＝Im(s_nw_n)

wherein, Y_nDenotes the real part signal, U, output from the nth analog complex multiplier_nDenotes the imaginary signal, s, output from the nth analog complex multiplier_nA complex number is the inphase signal and the orthogonal signal input by the nth analog complex multiplier

Refers to the in-phase signal input by the nth analog complex multiplier,

is the quadrature signal, w, input to the nth analog complex multiplier_nThe weight coefficient input by the nth analog complex multiplier is obtained

Refers to a parameter input to the nth analog complex multiplier,

refers to another parameter input by the nth analog complex multiplier, Re (.) refers to a real part taking operation, Im (·) refers to a virtual-real part operation, and n is a positive integer greater than or equal to 1 and less than or equal to M.

A weight coefficient optimization method of an array antenna beam forming receiving device is applied to the array antenna beam forming receiving device and is characterized in that when M/L is a positive integer, an output signal of a system real part is set as

The imaginary output signal of the system is

The system output signal is V ═ Y + jU; let R be reference signal, it is a complex number, its real part and imaginary part are input the signal processor by two input ends used for inputting the reference signal separately; let s be ═ s₁,s₂,......,s_M]^TIs a received signal vector containing the output signals of M signal amplifying and demodulating modules, and the received weight vector is w ═ w₁,w₂,......,w_M]^TComprisesM weight coefficients, w_i＝[w_(i-1)×L+1,w_(i-1)×L+2,......,w_(i-1)×L+L]^TIs the ith sub-weight vector, contains L weight coefficients corresponding to the ith group of analog complex multipliers, L is more than or equal to 1 and less than M, namely the vector w can be divided into multiple sub-vectors w_i，s_i＝[s_(i-1)×L+1,s_(i-1)×L+2,......,s_(i-1)×L+L]^TIs the ith sub-received signal vector, corresponding vector w_iComprises the output signals of the corresponding L-path signal amplification and demodulation modules,

is the ith sub-received signal vector s_iOf the autocorrelation matrix q_i＝E[(R-V)^*s_i]Is the error (R-V) and the ith sub-received signal vector s_iWhere E is an averaging operation, x is a complex conjugate operation, and H is a conjugate transpose operation, the optimization method includes the following steps:

step C1, randomly setting the receiving weight vector w ═ w₁,w₂,......,w_M]^TNumerical value, and satisfies | | w | | luminance²C is a real constant, and a received signal vector s ═ s is obtained₁,s₂,......,s_M]^TThe system outputs a signal V and a reference signal R; selecting the ith sub-received signal vector s_i＝[s_(i-1)×L+1,s_(i-1)×L+2,......,s_(i-1)×L+L]^TAnd ith sub-weight vector w_i＝[w_(i-1)×L+1,w_(i-1)×L+2,......,w_(i-1)×L+L]^T(ii) a Let i equal to 1;

step C2, calculating autocorrelation matrix

And a correlation vector q_i＝E[(R-V)^*s_i]；

Step C3, calculating the optimized sub-weight vector, wherein the calculation formula is as follows:

wherein 0< α < 1;

and the weight coefficient is adjusted to satisfy | | w | | non-woven phosphor²＝C；

Step C4, if i is less than M/L, i → i +1, go back to step C2; if i is equal to M/L, let i → 1 go back to step C2.

A weight coefficient optimization method of an array antenna beam forming receiving device is applied to the array antenna beam forming receiving device and is characterized in that when M/L is a non-positive integer, a system real part output signal is set as

The imaginary output signal of the system is

The system output signal is V ═ Y + jU; let R be reference signal, it is a complex number, its real part and imaginary part are input the signal processor by two input ends used for inputting the reference signal separately; let s be ═ s₁,s₂,......,s_M]^TIs a received signal vector containing the output signals of M signal amplifying and demodulating modules, and the received weight vector is w ═ w₁,w₂,......,w_M]^TThe weight coefficient is comprised of M weight coefficients,

is the ith sub-weight vector, which contains L weight coefficients corresponding to the ith group of analog complex multipliers, L is more than or equal to 1 and less than M, wherein the lower label of the a-th weight coefficient is i_aA is a positive integer, and a is more than or equal to 1 and less than or equal to L, then i is calculated_aTo achieve the purpose of circulation, let b equal 0, and then judge whether i-1 × L + a_a-bM>M, if not, keeping the current b value and making i_aIf yes, let b → b +1, continue to judge whether i-1 is multiplied by L + a-bM_a-bM>M, increasing the value of b until i_awhen-bM is less than or equal to M, i_a(i-1) × L + a-bM, then

Is the ith sub-received signal vector, corresponding vector w_iThe signal amplification and demodulation module comprises output signals of corresponding L paths of signal amplification and demodulation modules;

is the ith sub-received signal vector s_iOf the autocorrelation matrix q_i＝E[(R-V)^*s_i]Is the error (R-V) and the ith sub-received signal vector s_iWhere E is an averaging operation, x is a complex conjugate operation, and H is a conjugate transpose operation, the optimization method includes the following steps:

step D1, randomly setting the receiving weight vector w ═ w₁,w₂,......,w_M]^TNumerical value, and satisfies | | w | | luminance²C is a real constant, and a received signal vector s ═ s is obtained₁,s₂,......,s_M]^TThe system outputs a signal V and a reference signal R; selecting the ith sub-received signal vector

And ith sub-weight vector

Let i equal to 1;

step D2, calculating autocorrelation matrix

And a correlation vector q_i＝E[(R-V)^*s_i]；

D3, calculating the optimized sub-weight vector, wherein the calculation formula is as follows:

wherein 0< α < 1;

and the weight coefficient is adjusted to satisfy | | w | | non-woven phosphor²＝C；

D4, if i is less than M, i → i +1, and go back to D2; if i is equal to M, let i → 1 go back to step D2.

The invention has the beneficial effects that in the scheme of the invention, by adopting the array antenna beam forming receiving device and the weight coefficient optimization method thereof, the weight coefficient of the intelligent antenna beam is optimized and updated through a single-antenna or multi-antenna cyclic optimization algorithm, and good beam characteristics are ensured, so that the signal-to-noise ratio and the anti-interference capability of the receiving device are greatly improved, the complexity of a system and the algorithm is reduced, and the convergence speed of the algorithm is improved.

Drawings

Fig. 1 is a system block diagram of an array antenna beam forming receiving device in an embodiment of the present invention;

fig. 2 is a system block diagram of another array antenna beam forming receiving device in the embodiment of the present invention.

Detailed Description

The technical solution of the present invention is described in detail below with reference to the embodiments and the accompanying drawings.

The array antenna beam forming receiving device is characterized by also comprising a signal processor, two summers, a plurality of parallel signal amplification and demodulation modules and a plurality of analog complex multipliers, wherein the signal amplification and demodulation modules correspond to the analog complex multipliers one by one and correspond to the radio frequency filters one by one, the output end of each radio frequency filter is connected with the input end of the corresponding signal amplification and demodulation module, the in-phase output end and the quadrature output end of each signal amplification and demodulation module are respectively connected with two ends of one complex input end of the corresponding analog complex multiplier one by one, and two ends of the other complex input end of each analog complex multiplier are respectively connected with two output ends corresponding to the signal processor one by one The two ends of the complex output end of each analog complex multiplier are respectively connected with the input ends of two adders in a one-to-one correspondence mode, the real part of an adder output signal and the imaginary part of another adder output signal are respectively the output ends of the two adders, two parallel output signals are generated, namely the output signal of the system real part and the output signal of the system imaginary part, the system output signal is formed and is a complex number, the signal processor is provided with two input ends which are correspondingly connected with the output ends of the two adders, and the signal processor is also provided with two input ends which are used for inputting a reference signal;

the signal amplification demodulation module is used for amplifying an input signal and then demodulating the amplified input signal;

the analog complex multiplier is used for multiplying an input in-phase signal and an input quadrature signal serving as a complex number by another complex number serving as two input parameters and outputting a real part signal and an imaginary part signal of a multiplication result, and the another complex number is a weight coefficient;

the signal processor is used for respectively calculating two parameters (the real part and the imaginary part of the other complex number recorded above) corresponding to the weight coefficient of each analog complex multiplier according to the input reference signal and the system output signal, and sending the parameters to the corresponding analog complex multipliers; only two parameters corresponding to the weight coefficient corresponding to one analog complex multiplier are calculated at the same time, and the two parameters corresponding to the weight coefficient of each analog complex multiplier are circularly calculated in sequence.

The array antenna beam forming receiving device comprises a plurality of antennas, a plurality of radio frequency filters and two system output ends, wherein the antennas correspond to the radio frequency filters one by one, each antenna is connected with the input end of the corresponding radio frequency filter, the array antenna beam forming receiving device is characterized by also comprising a signal processor, two summers, a plurality of parallel signal amplification and demodulation modules and a plurality of analog complex multipliers, the signal amplification and demodulation modules correspond to the analog complex multipliers one by one and correspond to the radio frequency filters one by one, the output end of each radio frequency filter is connected with the input end of the corresponding signal amplification and demodulation module, the in-phase output end and the orthogonal output end of each signal amplification and demodulation module are respectively connected with the two ends of one complex input end of the corresponding analog complex multiplier one by one and correspond to the input ends of the signal processor one by one, the two ends of the other complex input end of each analog complex multiplier are respectively connected with the two corresponding output ends of the signal processor in a one-to-one correspondence manner, the two ends of the complex output end of each analog complex multiplier are respectively connected with the input ends of the two adders in a one-to-one correspondence manner, the real part of an adder output signal and the imaginary part of another adder output signal, the output ends of the two adders are respectively two system output ends, two parallel output signals are generated, namely the system real part output signal and the system imaginary part output signal, a system output signal is formed and is a complex number, the signal processor is provided with two input ends which are correspondingly connected with the output ends of the two adders, and the signal processor is also provided with two input ends which are;

the signal amplification demodulation module is used for amplifying an input signal and then demodulating the amplified input signal;

the analog complex multiplier is used for multiplying an input in-phase signal and an input quadrature signal serving as a complex number by another complex number serving as two input parameters and outputting a real part signal and an imaginary part signal of a multiplication result, and the another complex number is a weight coefficient;

the signal processor is used for respectively calculating two parameters (the real part and the imaginary part of the other complex number recorded above) corresponding to the weight coefficient of each analog complex multiplier according to the input reference signal and the system output signal, and sending the parameters to the corresponding analog complex multipliers; only two parameters corresponding to a set of weight coefficients corresponding to a set of L analog complex multipliers are calculated at the same time, namely only a set of L weight coefficients (each weight coefficient comprises two parameters) are calculated at the same time, the two parameters corresponding to the weight coefficients of each analog complex multiplier are calculated according to sequential cyclic grouping, the number of the analog complex multipliers is M, M is the number of antennas, M is a positive integer greater than or equal to 1, and L is greater than or equal to 1 and is less than M.

Examples

The array antenna beam forming receiving device of the embodiment of the invention has a system block diagram as shown in figure 1, and comprises a plurality of antennas, a plurality of radio frequency filters and two system output ends, wherein the antennas correspond to the radio frequency filters one by one, each antenna is connected with the input end of the corresponding radio frequency filter, the array antenna beam forming receiving device is characterized by also comprising a signal processor, two summers, a plurality of parallel signal amplification and demodulation modules and a plurality of analog complex multipliers, the signal amplification and demodulation modules correspond to the analog complex multipliers one by one and correspond to the radio frequency filters one by one, the output end of each radio frequency filter is connected with the input end of the corresponding signal amplification and demodulation module, the in-phase output end and the orthogonal output end of each signal amplification and demodulation module are respectively connected with the two ends of one complex input end of the corresponding analog complex multiplier one by one, the two ends of the other complex input end of each analog complex multiplier are respectively connected with the two corresponding output ends of the signal processor in a one-to-one correspondence manner, the two ends of the complex output end of each analog complex multiplier are respectively connected with the input ends of the two adders in a one-to-one correspondence manner, the real part of an adder output signal and the imaginary part of another adder output signal, the output ends of the two adders are respectively two system output ends, two parallel output signals are generated, namely the system real part output signal and the system imaginary part output signal, a system output signal is formed and is a complex number, the signal processor is provided with two input ends which are correspondingly connected with the output ends of the two adders, and the signal processor is also provided with two input ends which are.

The signal amplification and demodulation module is used for amplifying and then demodulating the input signal.

The signal amplification demodulation module can comprise a radio frequency amplifier and a radio frequency demodulator, wherein the input end of the radio frequency amplifier is used as the input end of the signal amplification demodulation module, the output end of the radio frequency amplifier is connected with the input end of the radio frequency demodulator, the radio frequency demodulator is used for demodulating an input signal, and the in-phase output end and the quadrature output end of the radio frequency demodulator are respectively used as the in-phase output end and the quadrature output end of the signal amplification demodulation module.

The analog complex multiplier is used for multiplying an input in-phase signal and an input quadrature signal as a complex number by another complex number which is an input parameter, and outputting a real part signal and an imaginary part signal of a multiplication result, wherein the another complex number is a weight coefficient.

The analog complex multiplier multiplies an input in-phase signal and an input quadrature signal as a complex number by another complex number which is an input two parameters, and outputs real and imaginary signals of the multiplication result, wherein the calculation formula can be as follows:

Y_n＝Re(s_nw_n)

U_n＝Im(s_nw_n)

wherein, Y_nDenotes the real part signal, U, output from the nth analog complex multiplier_nDenotes the imaginary signal, s, output from the nth analog complex multiplier_nA complex number is the inphase signal and the orthogonal signal input by the nth analog complex multiplier

Refers to the in-phase signal input by the nth analog complex multiplier,

is the quadrature signal, w, input to the nth analog complex multiplier_nThe weight coefficient input by the nth analog complex multiplier is obtained

Refers to a parameter input to the nth analog complex multiplier,

refers to another parameter input by the nth analog complex multiplier, Re (.) refers to operation of taking a real part, Im (.) refers to operation of a virtual part, n is a positive integer greater than or equal to 1 and less than or equal to M, M is the number of analog complex multipliers and also the number of antennas and is greater than or equal toA positive integer equal to 1.

The signal processor is used for respectively calculating two parameters (the real part and the imaginary part of the other complex number recorded above) corresponding to the weight coefficient of each analog complex multiplier according to the input reference signal and the system output signal, and sending the parameters to the corresponding analog complex multipliers; only two parameters corresponding to the weight coefficient corresponding to one analog complex multiplier are calculated at the same time, and the two parameters corresponding to the weight coefficient of each analog complex multiplier are circularly calculated in sequence.

In this example, the weight coefficient optimization method (both in the signal processor) of the array antenna beam forming receiving device has two kinds, and the real part of the system output signal is set as

The imaginary output signal of the system is

The system output signal is V ═ Y + jU; let n antenna, at the k time, the corresponding weight coefficient is expressed as

Is provided with h⁽ⁿ⁾(k) For the steering function corresponding to the kth time of the nth antenna, d⁽ⁿ⁾(k) And for the step function corresponding to the kth moment of the nth antenna, R is a reference signal and is a complex number, and the real part and the imaginary part of the complex number are respectively input into the signal processor by two input ends for inputting the reference signal.

In the first method, the mean square error between the output of the system output terminal and the reference signal is E [ | V-R | ]²]The corresponding mean square error at time k is E (k), where E is the averaging operation. The optimization of the weight coefficient adopts a minimum mean square error criterion in the first method, even if the mean square error of the received signal and the reference signal is minimum, so that the received signal is ensured to approach the reference signal to the maximum extent in a mode of minimum mean square error, and the effect is that the interference is inhibited while the expected signal is well received. The optimization criterion can be realized by a single-antenna cyclic optimization algorithm, namely, one-time updatingAnd obtaining a weight suboptimal solution for the weight coefficient of one antenna, then turning to the next antenna for updating, obtaining another weight suboptimal solution, and repeating the steps in sequence and repeatedly.

The optimization method specifically comprises the following steps:

step A1, randomly setting weight coefficient

And satisfy

Wherein C is a real constant; setting the guiding function value and the step length function value as h⁽¹⁾(1)＝1，d⁽¹⁾(1)＝D₀，D₀Obtaining a system output signal V and a reference signal R as a constant;

step a2, if k is equal to 1, the procedure proceeds to step A3, otherwise the following calculation is performed:

d⁽ⁿ⁾(k)＝h⁽ⁿ⁾(k-1)d⁽ⁿ⁾(k-1)

where ξ is a positive real number and 0< ξ < 1;

step A3, calculating a weight coefficient, wherein the calculation formula is as follows:

d⁽ⁿ⁾(k+1)＝h⁽ⁿ⁾(k)d⁽ⁿ⁾(k)

adjusting the weight coefficients according to:

|w₁(k)|²+|w₂(k)|²+...+|w_n(k+1)|²+...+|w_M(k)|²＝C

step A4, if | w_n(k+1)-w_n(k)|²Is less than or equal to positive real number close to zero, then enter step A5, otherwise let k → k +1 and return to step A2;

step A5, if n is less than M, n → n +1, and go back to step A3; if n is M, n → 1, let k → 1, h⁽ⁿ⁾(k) 1 and d⁽ⁿ⁾(k)＝D₀And returns to step a 3.

In the second method, the

For the correlation coefficient of the reference signal with the system output signal, the corresponding correlation coefficient at the k-th instant is r (k), p [ | V | ]²]For the output power at the output of the system, the corresponding output power at the k-th instant is p (k), where E is the averaging operation. The optimization of the weight coefficient adopts the minimum output power criterion under the condition of maximum correlation in the second method, namely the maximum correlation between the received signal and the reference signal is ensured, and simultaneously the output power of the system output end is minimized, and the generated effect is to furthest suppress interference on the premise of good reception of the expected signal. The optimization criterion can be realized by a single-antenna cyclic optimization algorithm, namely, the weight coefficient of one antenna is updated at one time to obtain a weight suboptimal solution, then the next antenna is turned to be updated to obtain another weight suboptimal solution, and the steps are repeated in sequence and circularly.

The optimization method specifically comprises the following steps:

step B1, randomly setting weight coefficient

And satisfy

Wherein C is a real constant, and guiding function values are respectively setAnd the value of the step size function is h⁽¹⁾(1) 1 and d⁽¹⁾(1)＝D₀，D₀Obtaining a system output signal V and a reference signal R as a constant;

if k is equal to 1, the step B2 is executed, and if not, the step B3 is executed as follows:

d⁽ⁿ⁾(k)＝h⁽ⁿ⁾(k-1)d⁽ⁿ⁾(k-1)

where ξ is a positive real number and 0< ξ < 1;

step B3, calculating the weight coefficient, the calculation formula is:

d⁽ⁿ⁾(k+1)＝h⁽ⁿ⁾(k)d⁽ⁿ⁾(k)

adjusting the weight coefficients according to:

|w₁(k)|²+|w₂(k)|²+...+|w_n(k+1)|²+...+|w_M(k)|²＝C

step B4, if | w_n(k+1)-w_n(k)|²If the real number is less than or equal to the positive real number close to zero, the step B5 is entered, otherwise, the step K → k +1 is entered, and the step B2 is returned;

step B5, if | r (k +1) -r (k) & gtdoes not smoke²Eta is less than or equal to eta and r (k +1) is more than or equal to sigma, eta is a positive real number close to zero, sigma is a pre-specified positive real number, and then k → 1, h⁽ⁿ⁾(k) 1 and d⁽ⁿ⁾(k)＝D₀Go to step B6; otherwise, continuing to judge, if n < M, then n → n +1, returning to step B3, if n ═ M, then let n → 1, k → 1, h⁽ⁿ⁾(k) 1 and d⁽ⁿ⁾(k)＝D₀Returning to step B3;

if k is equal to 1, the step B6 is executed, and if not, the step B7 is executed as follows:

d⁽ⁿ⁾(k)＝h⁽ⁿ⁾(k-1)d⁽ⁿ⁾(k-1)

step B7, calculating the weight coefficient, the calculation formula is:

d⁽ⁿ⁾(k+1)＝h⁽ⁿ⁾(k)d⁽ⁿ⁾(k)

adjusting the weight coefficients according to:

|w₁(k)|²+|w₂(k)|²+...+|w_n(k+1)|²+...+|w_M(k)|²＝C

step B8, if | w_n(k+1)-w_n(k)|²If not, entering the step B9, otherwise, enabling k → k +1, and returning to the step B6;

step B9, if | r (k +1) -r (k) & gtdoes not smoke²Eta and | p (k +1) -p (k) & ltu & gt²≦ is a positive real number close to zero, let k → 1, h⁽ⁿ⁾(k) 1 and d⁽ⁿ⁾(k)＝D₀Returning to the step B6, otherwise, continuing to judge, if n is less than M, then n → n +1, returning to the step B3; if n is equal to M, let n → 1, k → 1, h⁽ⁿ⁾(k) 1 and d⁽ⁿ⁾(k)＝D₀And returns to step B3.

Another array antenna beam forming receiving device in the embodiment of the invention, the system block diagram of which is shown in fig. 2, comprises a plurality of antennas, a plurality of radio frequency filters and two system output ends, wherein the antennas correspond to the radio frequency filters one by one, each antenna is connected with the input end of the corresponding radio frequency filter, the device is characterized by further comprising a signal processor, two summers, a plurality of parallel signal amplification and demodulation modules and a plurality of analog complex multipliers, the signal amplification and demodulation modules correspond to the analog complex multipliers one by one and correspond to the radio frequency filters one by one, the output end of each radio frequency filter is connected with the input end of the corresponding signal amplification and demodulation module, the in-phase output end and the quadrature output end of each signal amplification and demodulation module are respectively connected with the two ends of one complex input end of the corresponding analog complex multiplier one by one, the two ends of the complex output end of each analog complex multiplier are respectively connected with the input ends of the two adders in a one-to-one correspondence manner, the real part of an adder output signal and the imaginary part of another adder output signal are respectively two system output ends, two parallel output signals are generated, namely the system real part output signal and the system imaginary part output signal, so that a system output signal is formed and is a complex number, the signal processor is provided with two input ends which are correspondingly connected with the output ends of the two adders, and the signal processor is also provided with two input ends which are used for inputting reference signals.

The signal amplification and demodulation module is used for amplifying and then demodulating the input signal.

The signal amplification demodulation module can comprise a radio frequency amplifier and a radio frequency demodulator, wherein the input end of the radio frequency amplifier is used as the input end of the signal amplification demodulation module, the output end of the radio frequency amplifier is connected with the input end of the radio frequency demodulator, the radio frequency demodulator is used for demodulating an input signal, and the in-phase output end and the quadrature output end of the radio frequency demodulator are respectively used as the in-phase output end and the quadrature output end of the signal amplification demodulation module.

The analog complex multiplier is used for multiplying an input in-phase signal and an input quadrature signal as a complex number by another complex number which is an input parameter, and outputting a real part signal and an imaginary part signal of a multiplication result, wherein the another complex number is a weight coefficient.

In the analog complex multiplier, which multiplies an input in-phase signal and an input quadrature signal as a complex number by another complex number of two input parameters, and outputs real and imaginary signals of the multiplication result, the calculation formula may be:

Y_n＝Re(s_nw_n)

U_n＝Im(s_nw_n)

wherein, Y_nDenotes the real part signal, U, output from the nth analog complex multiplier_nDenotes the imaginary signal, s, output from the nth analog complex multiplier_nA complex number is the inphase signal and the orthogonal signal input by the nth analog complex multiplier

Refers to the in-phase signal input by the nth analog complex multiplier,

is the quadrature signal, w, input to the nth analog complex multiplier_nThe weight coefficient input by the nth analog complex multiplier is obtained

Refers to a parameter input to the nth analog complex multiplier,

refers to another parameter input by the nth analog complex multiplier, Re (.) refers to a real part taking operation, Im (·) refers to a virtual-real part operation, and n is a positive integer greater than or equal to 1 and less than or equal to M.

The signal processor is used for respectively calculating two parameters (the real part and the imaginary part of the other complex number recorded above) corresponding to the weight coefficient of each analog complex multiplier according to the input reference signal and the system output signal, and sending the parameters to the corresponding analog complex multipliers; only two parameters corresponding to a set of weight coefficients corresponding to a set of L analog complex multipliers are calculated at the same time, namely only a set of L weight coefficients (each weight coefficient comprises two parameters) are calculated at the same time, the two parameters corresponding to the weight coefficients of each analog complex multiplier are calculated according to sequential cyclic grouping, the number of the analog complex multipliers is M, M is the number of antennas, M is a positive integer greater than or equal to 1, and L is greater than or equal to 1 and is less than M.

Setting the real part output signal of the system as

The imaginary output signal of the system is

The system output signal is V ═ Y + jU; let R be reference signal, it is a complex number, its real part and imaginary part are respectively inputted into signal processor by two input ends for inputting reference signal, the mean square error of system output signal and reference signal is E [ | V-R |)²]，s＝[s₁,s₂,......,s_M]^TIs a received signal vector containing the output signals of M signal amplifying and demodulating modules, and the received weight vector is w ═ w₁,w₂,......,w_M]^TContains M weight coefficients, w_i＝[w_(i-1)×L+1,w_(i-1)×L+2,......,w_(i-1)×L+L]^TIs the ith sub-weight vector, contains L weight coefficients corresponding to the ith group of analog complex multipliers, L is more than or equal to 1 and less than M, namely the vector w can be dividedIs a multi-subvector w_i，s_i＝[s_(i-1)×L+1,s_(i-1)×L+2,......,s_(i-1)×L+L]^TIs the ith sub-received signal vector, corresponding vector w_iComprises the output signals of the corresponding L-path signal amplification and demodulation modules,

is a weight vector, which corresponds to the vector w_iThe element part of (a) takes a value of zero,

is the ith sub-received signal vector s_iThe autocorrelation matrix of (a) is then determined,

is the ith sub-received signal vector s_iCorrelation matrix with received signal vector s, q_i＝E[(R-V)^*s_i]Is the error (R-V) and the ith sub-received signal vector s_iOf the correlation vector q_R＝E[R^*s_i]Is a reference signal R and an ith sub-received signal vector s_iHere, E is an averaging operation, x is a complex conjugate operation, and H is a conjugate transpose operation.

In the method for optimizing weight coefficients or sub-weight vectors (both in a signal processor) of the array antenna beam forming receiving device, there are two cases: the second case is that M/L is a non-positive integer. The optimization principle of the weight coefficient or the sub-weight vector is as follows:

the mean square error of the system output signal and the reference signal is expressed as

e＝E[|V-R|²]＝E[|w^Hs-R|²]

The above formula is unfolded, and then e is subjected to partial derivation to obtain

Making the above formula zero to obtain an equation, and calculating the optimizationSub-weight vector w_i,optThen, there are:

further expansion and then merging can be obtained

This gives:

therefore, in case one, the sub-weight vector optimization method includes the following steps:

step C1, randomly setting the receiving weight vector w ═ w₁,w₂,......,w_M]^TNumerical value, and satisfies | | w | | luminance²C is a real constant, and a received signal vector s ═ s is obtained₁,s₂,......,s_M]^TThe output Y of the system output end and a reference signal R; selecting the ith sub-received signal vector s_i＝[s_(i-1)×L+1,s_(i-1)×L+2,......,s_(i-1)×L+L]^TAnd ith sub-weight vector w_i＝[w_(i-1)×L+1,w_(i-1)×L+2,......,w_(i-1)×L+L]^T(ii) a Let i equal to 1;

step C2, calculating autocorrelation matrix

And a correlation vector q_i＝E[(R-V)^*s_i]；

Step C3, calculating the optimized sub-weight vector, wherein the calculation formula is as follows:

wherein 0< α < 1;

and the weight coefficient is adjusted to satisfy | | w | | non-woven phosphor²＝C；

Step C4, if i is less than M/L, i → i +1, go back to step C2; if i is equal to M/L, let i → 1 go back to step C2.

In the second case, let

Is the ith sub-weight vector, which contains L weight coefficients corresponding to the ith group of analog complex multipliers, L is more than or equal to 1 and less than M, wherein the lower label of the a-th weight coefficient is i_aA is a positive integer, and a is more than or equal to 1 and less than or equal to L, then i is calculated_aTo achieve the purpose of circulation, let b equal 0, and then judge whether i-1 × L + a_a-bM>M, if not, keeping the current b value and making i_aIf yes, let b → b +1, continue to judge whether i-1 is multiplied by L + a-bM_a-bM>M, increasing the value of b until i_awhen-bM is less than or equal to M, i_a(i-1) × L + a-bM, then

Is the ith sub-received signal vector, corresponding vector w_iThe signal amplification and demodulation module comprises output signals of corresponding L paths of signal amplification and demodulation modules.

Therefore, in case two, the sub-weight vector optimization method includes the following steps:

step D1, randomly setting the receiving weight vector w ═ w₁,w₂,......,w_M]^TNumerical value, and satisfies | | w | | luminance²C is a real constant, and a received signal vector s ═ s is obtained₁,s₂,......,s_M]^TThe system outputs a signal V and a reference signal R; selecting the ith sub-received signal vector

And ith sub-weight vector

Let i equal to 1;

step D2, calculating autocorrelation matrix

And a correlation vector q_i＝E[(R-V)^*s_i]；

D3, calculating the optimized sub-weight vector, wherein the calculation formula is as follows:

wherein 0< α < 1;

and the weight coefficient is adjusted to satisfy | | w | | non-woven phosphor²＝C；

D4, if i is less than M, i → i +1, and go back to D2; if i is equal to M, let i → 1 go back to step D2.

Claims (4)

1. The array antenna beam forming receiving device comprises a plurality of antennas, a plurality of radio frequency filters and two system output ends, wherein the antennas correspond to the radio frequency filters one to one, each antenna is connected with the input end of the corresponding radio frequency filter, the array antenna beam forming receiving device is characterized by further comprising a signal processor, two summers, a plurality of parallel signal amplification demodulation modules and a plurality of analog complex multipliers, the signal amplification demodulation modules correspond to the analog complex multipliers one to one and correspond to the radio frequency filters one to one, the output end of each radio frequency filter is connected with the input end of the corresponding signal amplification demodulation module, the in-phase output end and the quadrature output end of each signal amplification demodulation module are respectively connected with the two ends of one complex input end of the corresponding analog complex multiplier one to one, and the two ends of the other complex input end of each analog complex multiplier are respectively connected with the two output ends of the corresponding signal processor one to one The two ends of the complex output end of each analog complex multiplier are respectively connected with the input ends of two adders in a one-to-one correspondence mode, the real part of an adder output signal and the imaginary part of another adder output signal are respectively two system output ends, two parallel output signals are generated, namely a system real part output signal and a system imaginary part output signal, a system output signal is formed and is a complex number, two input ends of a signal processor are correspondingly connected with the output ends of the two adders, and the two input ends of the signal processor are used for inputting a reference signal;

the signal amplification demodulation module is used for amplifying an input signal and then demodulating the amplified input signal;

the analog complex multiplier is used for multiplying an input in-phase signal and an input quadrature signal serving as a complex number by another complex number serving as two input parameters and outputting a real part signal and an imaginary part signal of a multiplication result, and the another complex number is a weight coefficient; the calculation formula of the real part signal and the imaginary part signal is as follows:

Y_n＝Re(s_nw_n)

U_n＝Im(s_nw_n)

wherein, Y_nDenotes the real part signal, U, output from the nth analog complex multiplier_nDenotes the imaginary signal, s, output from the nth analog complex multiplier_nA complex number is the inphase signal and the orthogonal signal input by the nth analog complex multiplier

Refers to the in-phase signal input by the nth analog complex multiplier,

is the quadrature signal, w, input to the nth analog complex multiplier_nThe weight coefficient input by the nth analog complex multiplier is obtained

Refers to a parameter input to the nth analog complex multiplier,

the method is characterized by comprising the following steps of inputting another parameter of an nth analog complex multiplier, wherein Re (eta) refers to a real part taking operation, Im (eta) refers to a virtual-real part operation, n is a positive integer which is greater than or equal to 1 and less than or equal to M, M is the number of analog complex multipliers and also is the number of antennas and is a positive integer which is greater than or equal to 1;

the signal processor is used for respectively calculating two parameters corresponding to the weight coefficient of each analog complex multiplier according to the input reference signal and the system output signal and sending the two parameters to the corresponding analog complex multipliers; only two parameters corresponding to the weight coefficient corresponding to one analog complex multiplier are calculated at the same time, and the two parameters corresponding to the weight coefficient of each analog complex multiplier are circularly calculated in sequence;

the signal processor optimizes the weight coefficient after calculating the weight coefficient, and the optimization method comprises a first method or a second method;

the method sets the real part output signal of the system as

The imaginary output signal of the system is

The system output signal is V ═ Y + jU; let n antenna, at the k time, the corresponding weight coefficient is expressed as

Is provided with h⁽ⁿ⁾(k) For the steering function corresponding to the kth time of the nth antenna, d⁽ⁿ⁾(k) A step function corresponding to the kth moment of the nth antenna; let R be a reference signal, which is a complex number whose real and imaginary parts are used to input the reference signalThe two input ends of the test signal are input into a signal processor, and the mean square error of the system output signal and the reference signal is E [ | V-R | ]²]If the corresponding mean square error at the kth time is E (k), where E is an averaging operation, the optimization method includes the following steps:

step A1, randomly setting weight coefficient

And satisfy

Wherein C is a real constant; setting the guiding function value and the step length function value as h⁽¹⁾(1)＝1，d⁽¹⁾(1)＝D₀，D₀Obtaining a system output signal V and a reference signal R as a constant;

step a2, if k is equal to 1, the procedure proceeds to step A3, otherwise the following calculation is performed:

d⁽ⁿ⁾(k)＝h⁽ⁿ⁾(k-1)d⁽ⁿ⁾(k-1)

where ξ is a positive real number and 0< ξ < 1;

step A3, calculating a weight coefficient, wherein the calculation formula is as follows:

d⁽ⁿ⁾(k+1)＝h⁽ⁿ⁾(k)d⁽ⁿ⁾(k)

adjusting the weight coefficients according to:

|w₁(k)|²+|w₂(k)|²+...+|w_n(k+1)|²+...+|w_M(k)|²＝C

step A4, if | w_n(k+1)-w_n(k)|²Is less than or equal to positive real number close to zero, then enter step A5, otherwise let k → k +1 and return to step A2;

step A5, if n is less than M, n → n +1, and go back to step A3; if n is M, n → 1, let k → 1, h⁽ⁿ⁾(k) 1 and d⁽ⁿ⁾(k)＝D₀And back to step a 3;

method for setting output signal of real part of system as

The imaginary output signal of the system is

The system output signal is V ═ Y + jU; let n antenna, at the k time, the corresponding weight coefficient is expressed as

Is provided with h⁽ⁿ⁾(k) For the steering function corresponding to the kth time of the nth antenna, d⁽ⁿ⁾(k) A step function corresponding to the kth moment of the nth antenna; let R be a reference signal, which is a complex number whose real part and imaginary part are input to the signal processor by two input terminals for inputting the reference signal,

for the correlation coefficient of the reference signal with the system output signal, the corresponding correlation coefficient at the k-th instant is r (k), p [ | V | ]²]For the output power of the system output signal, the corresponding output power at the k-th instant is p (k), where E is the averaging operation, the optimization method comprises the following steps:

step B1, randomly setting weight coefficient

And satisfy

Wherein C is a real constant, and the guiding function value and the step length function value are respectively set as h⁽¹⁾(1) 1 and d⁽¹⁾(1)＝D₀，D₀Obtaining a system output signal V and a reference signal R as a constant;

if k is equal to 1, the step B2 is executed, and if not, the step B3 is executed as follows:

d⁽ⁿ⁾(k)＝h⁽ⁿ⁾(k-1)d⁽ⁿ⁾(k-1)

where ξ is a positive real number and 0< ξ < 1;

step B3, calculating the weight coefficient, the calculation formula is:

d⁽ⁿ⁾(k+1)＝h⁽ⁿ⁾(k)d⁽ⁿ⁾(k)

adjusting the weight coefficients according to:

|w₁(k)|²+|w₂(k)|²+...+|w_n(k+1)|²+...+|w_M(k)|²＝C

step B4, if | w_n(k+1)-w_n(k)|²If the real number is less than or equal to the positive real number close to zero, the step B5 is entered, otherwise, the step K → k +1 is entered, and the step B2 is returned;

step B5, if | r (k +1) -r (k) & gtdoes not smoke²Eta is less than or equal to eta and r (k +1) is more than or equal to sigma, eta is a positive real number close to zero, sigma is a pre-specified positive real number, and then k → 1, h⁽ⁿ⁾(k) 1 and d⁽ⁿ⁾(k)＝D₀Go to step B6; otherwise, continuing to judge, if n < M, then n → n +1, returning to step B3, if n ═ M, then let n → 1, k → 1, h⁽ⁿ⁾(k) 1 and d⁽ⁿ⁾(k)＝D₀Returning to step B3;

if k is equal to 1, the step B6 is executed, and if not, the step B7 is executed as follows:

d⁽ⁿ⁾(k)＝h⁽ⁿ⁾(k-1)d⁽ⁿ⁾(k-1)

step B7, calculating the weight coefficient, the calculation formula is:

d⁽ⁿ⁾(k+1)＝h⁽ⁿ⁾(k)d⁽ⁿ⁾(k)

adjusting the weight coefficients according to:

|w₁(k)|²+|w₂(k)|²+...+|w_n(k+1)|²+...+|w_M(k)|²＝C

step B8, if | w_n(k+1)-w_n(k)|²If not, entering the step B9, otherwise, enabling k → k +1, and returning to the step B6;

step B9, if | r (k +1) -r (k) & gtdoes not smoke²Eta and | p (k +1) -p (k) & ltu & gt²≦ is a positive real number close to zero, let k → 1, h⁽ⁿ⁾(k) 1 and d⁽ⁿ⁾(k)＝D₀Returning to the step B6, otherwise, continuing to judge, if n is less than M, then n → n +1, returning to the step B3; if n is equal to M, let n → 1, k → 1, h⁽ⁿ⁾(k) 1 and d⁽ⁿ⁾(k)＝D₀And returns to step B3.

2. The array antenna beam forming receiving device according to claim 1, wherein the signal amplifying and demodulating module comprises a radio frequency amplifier and a radio frequency demodulator, an input terminal of the radio frequency amplifier is used as an input terminal of the signal amplifying and demodulating module, and an output terminal of the radio frequency amplifier is connected with an input terminal of the radio frequency demodulator;

the radio frequency demodulator is used for demodulating an input signal, and an in-phase output end and a quadrature output end of the radio frequency demodulator are respectively used as an in-phase output end and a quadrature output end of the signal amplification demodulation module.

3. The array antenna beam forming receiving device comprises a plurality of antennas, a plurality of radio frequency filters and two system output ends, wherein the antennas correspond to the radio frequency filters one by one, each antenna is connected with the input end of the corresponding radio frequency filter, the array antenna beam forming receiving device is characterized by also comprising a signal processor, two summers, a plurality of parallel signal amplification and demodulation modules and a plurality of analog complex multipliers, the signal amplification and demodulation modules correspond to the analog complex multipliers one by one and correspond to the radio frequency filters one by one, the output end of each radio frequency filter is connected with the input end of the corresponding signal amplification and demodulation module, the in-phase output end and the orthogonal output end of each signal amplification and demodulation module are respectively connected with the two ends of one complex input end of the corresponding analog complex multiplier one by one and correspond to the input ends of the signal processor one by one, the two ends of the other complex input end of each analog complex multiplier are respectively connected with the two corresponding output ends of the signal processor in a one-to-one correspondence manner, the two ends of the complex output end of each analog complex multiplier are respectively connected with the input ends of the two adders in a one-to-one correspondence manner, the real part of an adder output signal and the imaginary part of another adder output signal, the output ends of the two adders are respectively two system output ends, two parallel output signals are generated, namely the system real part output signal and the system imaginary part output signal, a system output signal is formed and is a complex number, the signal processor is provided with two input ends which are correspondingly connected with the output ends of the two adders, and the signal processor is also provided with two input ends which are;

the signal amplification demodulation module is used for amplifying an input signal and then demodulating the amplified input signal;

the analog complex multiplier is used for multiplying an input in-phase signal and an input quadrature signal serving as a complex number by another complex number serving as two input parameters and outputting a real part signal and an imaginary part signal of a multiplication result, and the another complex number is a weight coefficient; the calculation formula of the real part signal and the imaginary part signal is as follows:

Y_n＝Re(s_nw_n)

U_n＝Im(s_nw_n)

wherein, Y_nDenotes the real part signal, U, output from the nth analog complex multiplier_nDenotes the imaginary signal, s, output from the nth analog complex multiplier_nA complex number is the inphase signal and the orthogonal signal input by the nth analog complex multiplier

Refers to the in-phase signal input by the nth analog complex multiplier,

is the quadrature signal, w, input to the nth analog complex multiplier_nThe weight coefficient input by the nth analog complex multiplier is obtained

Refers to a parameter input to the nth analog complex multiplier,

the method is characterized by comprising the following steps of (1) inputting another parameter of an nth analog complex multiplier, Re (.) refers to a real part taking operation, Im (.) refers to a virtual-real part operation, and n is a positive integer which is greater than or equal to 1 and less than or equal to M;

the signal processor is used for respectively calculating two parameters corresponding to the weight coefficient of each analog complex multiplier according to the input reference signal and the system output signal and sending the two parameters to the corresponding analog complex multipliers; only two parameters corresponding to the weight coefficients corresponding to a group of L analog complex multipliers are calculated at the same time, namely only a group of L weight coefficients are calculated at the same time, and the two parameters corresponding to the weight coefficients of each analog complex multiplier are calculated in sequential cyclic grouping, wherein the number of the analog complex multipliers is M, the number of the antennas is M, the M is a positive integer greater than or equal to 1, and L is greater than or equal to 1 and is less than M;

after the signal processor calculates the weight coefficient, the weight coefficient is optimized, and the optimization method comprises a third method or a fourth method;

when M/L is a positive integer, the output signal of the real part of the three-set system is

The imaginary output signal of the system is

Then the systemThe output signal is V ═ Y + jU; let R be reference signal, it is a complex number, its real part and imaginary part are input the signal processor by two input ends used for inputting the reference signal separately; let s be ═ s₁,s₂,......,s_M]^TIs a received signal vector containing the output signals of M signal amplifying and demodulating modules, and the received weight vector is w ═ w₁,w₂,......,w_M]^TContains M weight coefficients, w_i＝[w_(i-1)×L+1,w_(i-1)×L+2,......,w_(i-1)×L+L]^TIs the ith sub-weight vector, contains L weight coefficients corresponding to the ith group of analog complex multipliers, L is more than or equal to 1 and less than M, namely the vector w can be divided into multiple sub-vectors w_i，s_i＝[s_(i-1)×L+1,s_(i-1)×L+2,......,s_(i-1)×L+L]^TIs the ith sub-received signal vector, corresponding vector w_iComprises the output signals of the corresponding L-path signal amplification and demodulation modules,

is the ith sub-received signal vector s_iOf the autocorrelation matrix q_i＝E[(R-V)^*s_i]Is the error (R-V) and the ith sub-received signal vector s_iWhere E is an averaging operation, x is a complex conjugate operation, and H is a conjugate transpose operation, the optimization method includes the following steps:

step C1, randomly setting the receiving weight vector w ═ w₁,w₂,......,w_M]^TNumerical value, and satisfies | | w | | luminance²C is a real constant, and a received signal vector s ═ s is obtained₁,s₂,......,s_M]^TThe system outputs a signal V and a reference signal R; selecting the ith sub-received signal vector s_i＝[s_(i-1)×L+1,s_(i-1)×L+2,......,s_(i-1)×L+L]^TAnd ith sub-weight vector w_i＝[w_(i-1)×L+1,w_(i-1)×L+2,......,w_(i-1)×L+L]^T(ii) a Let i equal to 1;

step C2, calculating autocorrelation matrix

And a correlation vector q_i＝E[(R-V)^*s_i]；

Step C3, calculating the optimized sub-weight vector, wherein the calculation formula is as follows:

wherein 0< α < 1;

and the weight coefficient is adjusted to satisfy | | w | | non-woven phosphor²＝C；

Step C4, if i is less than M/L, i → i +1, go back to step C2; if i is equal to M/L, let i → 1 go back to step C2;

when M/L is a non-positive integer, the output signal of the real part of the system is

The imaginary output signal of the system is

The system output signal is V ═ Y + jU; let R be reference signal, it is a complex number, its real part and imaginary part are input the signal processor by two input ends used for inputting the reference signal separately; let s be ═ s₁,s₂,......,s_M]^TIs a received signal vector containing the output signals of M signal amplifying and demodulating modules, and the received weight vector is w ═ w₁,w₂,......,w_M]^TThe weight coefficient is comprised of M weight coefficients,

is the ith sub-weight vector, which contains L weight coefficients corresponding to the ith group of analog complex multipliers, L is more than or equal to 1 and less than M, wherein the lower label of the a-th weight coefficient is i_aA is a positive integer, and a is more than or equal to 1 and less than or equal to L, then i is calculated_aFor the purpose of circulation, let b be (i-1) × L + a0, then judging whether i is_a-bM>M, if not, keeping the current b value and making i_aIf yes, let b → b +1, continue to judge whether i-1 is multiplied by L + a-bM_a-bM>M, increasing the value of b until i_awhen-bM is less than or equal to M, i_a(i-1) × L + a-bM, then

Is the ith sub-received signal vector, corresponding vector w_iThe signal amplification and demodulation module comprises output signals of corresponding L paths of signal amplification and demodulation modules;

is the ith sub-received signal vector s_iOf the autocorrelation matrix q_i＝E[(R-V)^*s_i]Is the error (R-V) and the ith sub-received signal vector s_iWhere E is an averaging operation, x is a complex conjugate operation, and H is a conjugate transpose operation, the optimization method includes the following steps:

step D1, randomly setting the receiving weight vector w ═ w₁,w₂,......,w_M]^TNumerical value, and satisfies | | w | | luminance²C is a real constant, and a received signal vector s ═ s is obtained₁,s₂,......,s_M]^TThe system outputs a signal V and a reference signal R; selecting the ith sub-received signal vector

And ith sub-weight vector

Let i equal to 1;

step D2, calculating autocorrelation matrix

And a correlation vector q_i＝E[(R-V)^*s_i]；

D3, calculating the optimized sub-weight vector, wherein the calculation formula is as follows:

wherein 0< α < 1;

and the weight coefficient is adjusted to satisfy | | w | | non-woven phosphor²＝C；

D4, if i is less than M, i → i +1, and go back to D2; if i is equal to M, let i → 1 go back to step D2.

4. The array antenna beam forming receiving device according to claim 3, wherein the signal amplifying and demodulating module comprises a radio frequency amplifier and a radio frequency demodulator, an input terminal of the radio frequency amplifier is used as an input terminal of the signal amplifying and demodulating module, and an output terminal of the radio frequency amplifier is connected with an input terminal of the radio frequency demodulator;

the radio frequency demodulator is used for demodulating an input signal, and an in-phase output end and a quadrature output end of the radio frequency demodulator are respectively used as an in-phase output end and a quadrature output end of the signal amplification demodulation module.

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