CN107579659B - Constant-current resonant DC conversion circuit and method adapting to high parasitic parameters of transformer - Google Patents
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Abstract
The invention discloses constant-current resonant DC conversion circuits and methods adapting to high parasitic parameters of transformers, comprising an inverter circuit, a resonance circuit, a compensation circuit and a rectification circuit, wherein the inverter circuit inverts an original power input current signal connected with the inverter circuit into an AC signal, the resonance circuit receives the AC signal provided by the inverter circuit, the compensation circuit is provided with a transformer model circuit, a compensation capacitor for compensating inductive reactive power consumed by the transformer model circuit and a second compensation capacitor for compensating the current precision of the transformer model circuit, the rectification circuit converts the AC signal output by the compensation circuit into a DC signal, and the DC signal is not changed along with the change of a load resistor.
Description
Technical Field
The invention relates to the field of design of constant-current resonant type direct-current conversion systems, in particular to constant-current resonant type direct-current conversion circuits and methods adaptive to high parasitic parameters of transformers.
Background
With the application of the storage battery pack to various high-power transportation systems, including the fields of automobiles, ships, aerospace and the like, along with the continuous improvement of power and voltage levels, the charging voltage of the storage battery pack is higher and higher, and the charging of the high-voltage storage battery pack by using the traditional voltage source topology often encounters several difficulties:
(1) the charging voltage of the high-voltage storage battery pack is very high, the application voltage source type topology needs larger gain, the single-stage conversion difficulty is very high, and the two-stage conversion efficiency is lower.
(2) When the storage battery is charged, the storage battery is in a constant-current charging state for most of time, and the voltage source type topology is applied to a constant-current working state, so that the storage battery is difficult to work at an optimal working point, and the working efficiency is low.
The application of a constant current topology solves this problem. The high-voltage storage battery pack is charged by adopting a constant-current topology, proper charging current is designed, the voltage gain problem does not need to be considered, and the single-stage conversion can adapt to application requirements. And when the current source type converter outputs the constant current, the current source type converter can be designed at the optimal working point, so that the working efficiency is ensured. Therefore, the constant current type topology has important significance when being applied to the charging occasion of the high-voltage storage battery pack.
However, the process of the LCL type constant current resonance topology design in the prior art is equivalent to an ideal model of the transformer, as shown in fig. 1, in the LCL type constant current resonance circuit in the prior art, at the input voltage UdcAnd an output voltage V0The transformer is provided with an inverter circuit, an LCL immittance transformation network and an ideal transformer model. In an actual circuit, a transformer has parasitic parameters mainly including leakage inductance and excitation inductance, so that the accuracy of the output current of the circuit is influenced, and the circuit has larger reactive power due to inductive components caused by the leakage inductance of the transformer, so that the efficiency of the circuit is influenced. The invention relates to a constant-current resonance type direct-current conversion topology design which aims at the basis of an LCL type resonance circuit in the prior art and is suitable for high parasitic parameters of a transformer.
Disclosure of Invention
The invention aims to provide constant-current resonance type direct-current conversion circuits and methods suitable for high parasitic parameters of transformers, which are constant-current resonance conversion system improved circuits based on a compensation capacitance principle, and can improve the current output precision and the system efficiency, so that the constant-current resonance conversion technology is better applied to the transformers with high parasitic parameters.
To achieve the above object, constant current resonance type dc conversion circuit adapted to high parasitic parameters of transformer according to the present invention includes:
the inverter circuit comprises a plurality of inverter modules, and the inverter module is used for inverting an original power supply input voltage signal connected with the inverter circuit into an alternating current voltage signal;
the resonance circuit is connected with the inverter circuit and receives an alternating voltage signal provided by the inverter circuit; the resonance circuit is provided with a resonance inductor and a resonance capacitor, so that an alternating voltage signal is converted into an alternating current signal;
the compensating circuit is provided with a transformer, an th compensating capacitor for compensating inductive reactive power consumed by the transformer and a second compensating capacitor for compensating the current precision of the transformer, wherein the th compensating capacitor is arranged on the primary side side of the transformer, and the second compensating capacitor is arranged on the secondary side side of the transformer;
and the rectifying circuit is connected with the compensating circuit, converts the alternating current signal output by the compensating circuit into a direct current signal and outputs the direct current signal to the load resistor.
Preferably, the resonant capacitor is connected in series with the resonant inductor;
the calculation formula of the resonance capacitance is as follows:
wherein L ispIs a resonant inductor; cpIs a resonant capacitor; omegaoIs the resonant frequency.
Preferably, the transformer comprises a primary side self-inductance and a secondary side self-inductance, and the secondary side self-inductance is equal to the sum of the excitation inductance of the transformer and the secondary side leakage inductance of the transformer;
the th compensation capacitor, the resonance inductor and a branch circuit on the side of the primary side of the transformer are connected in series, and a branch circuit formed by the side of the primary side of the transformer and the resonance inductor in series is connected with the resonance capacitor in parallel;
the second compensation capacitor is connected in series with a branch circuit on the secondary side side of the transformer, and the second compensation capacitor is connected in parallel with the rectifying circuit and the load resistor.
Preferably, the plurality of inversion modules are respectively th inversion module, second inversion module, third inversion module and fourth inversion module;
the branch where the th inversion module and the third inversion module are connected in series is connected in parallel with the branch where the second inversion module and the fourth inversion module are connected in series;
each inversion module is provided with an inversion switch tube, an inversion diode and an inversion capacitor, and any switch tube is respectively connected with the inversion diode and the inversion capacitor in parallel correspondingly.
Preferably, the direct current signal received by the load resistor is a constant current signal which does not change along with the change of the load resistor; the direct current I output by the load resistoroThe calculation formula of (2) is as follows:
Lmis the value of the excitation inductance, omega, of the transformeroIs the resonant frequency; l isr2The secondary leakage inductance value is obtained; l isp1Is the value of the resonance inductance; u shapedcThe original input voltage value is obtained; theta is a phase shift angle.
Preferably, the calculation formula of the second compensation capacitance is:
C2is a second compensation capacitance value, ωoIs the resonant frequency, L2The secondary side of the transformer is self-inductance.
Preferably, the th compensation capacitor is calculated by the formula:
Cpis the value of the resonant capacitance, C1Compensating the capacitance value, L, for the thr1Is the origin of the transformerSelf-induction at the edge.
Preferably, the constant-current resonance type direct current conversion circuit is suitable for a high-voltage storage battery pack charging system.
Preferably, the transformer is a loosely coupled transformer.
The invention also provides design methods using the constant-current resonance type direct-current conversion circuits, which comprises the following steps:
s1: according to the requirements of the applied system, the resonance frequency omega is estimatedoThe following can be obtained:
ωo＝2πfo；
wherein f is0Is the duty cycle of the switching tube of the inverter circuit;
s2: measuring secondary side self-inductance L of transformer2Calculating a second compensation capacitance C2The following can be obtained:
s3: setting output current ioAnd according to the output current ioTo calculate the resonant inductance L of the resonant circuitpAnd a resonance capacitor CpThe following can be obtained:
wherein θ is a phase shift angle, LmIs the excitation inductance of the transformer, udcThe original direct current input voltage of the inverter circuit is obtained;
s4 calculating th compensation capacitor C1The value of (c):
Lr1is the primary side self-inductance of the transformer.
Compared with the prior art, the invention has the beneficial effects that: (1) the circuit topology has the capability of constant current output under the condition of open loop; (2) the circuit topology disclosed by the invention is simple in design, reliable and practical; (3) the invention can still keep higher open-loop constant-current output precision when the parasitic parameters of the transformer are higher; (4) the circuit can be applied to charging of a high-voltage storage battery pack, and can solve the problem of insufficient voltage source type topological boost gain.
Drawings
FIG. 1 is a schematic diagram of a prior art constant current resonant topology;
FIG. 2 is a schematic diagram of the novel constant current resonant DC converter circuit of the present invention;
FIG. 2a is a schematic diagram of an equivalent constant current resonance topology of the present invention;
FIG. 3 is a detailed schematic diagram of the novel constant current resonant topology of the present invention;
FIG. 4 is the secondary side equivalent circuit of transformer of the present invention;
FIG. 5 shows a secondary side equivalent circuit of the transformer of the present invention;
FIG. 6 is a diagram of the frequency and current characteristics simulation analysis of the constant current of the novel constant current resonance circuit of the present invention;
fig. 7 is a simulation analysis diagram of the characteristics of the constant current of the novel constant current resonance circuit of the invention, such as frequency and phase.
Detailed Description
The present invention provides constant current resonance type dc conversion circuits and methods suitable for high parasitic parameters of transformers, and in order to make the present invention more comprehensible, the present invention is further described in with reference to the accompanying drawings and the detailed description.
The constant-current resonance type direct-current conversion circuit adaptive to the high parasitic parameters of the transformer can be applied to charging of a high-voltage storage battery pack, as shown in fig. 2.
Wherein FIG. 2a is a schematic diagram of equivalent circuits of FIG. 2 for convenient analysis of the circuit, as shown in FIG. 2 and FIG. 2a, the present invention is applied to an input voltage UdcAnd an output voltage U0An inverter circuit, a resonance circuit (LCL immittance transformation network), a compensation circuit and a rectification circuit are arranged between the two circuits. Drawing (A)The resonant circuit and the compensation circuit in fig. 2 are mainly equivalent in fig. 2 a.
As shown in fig. 3, the present invention includes four inverter modules with the same circuit structure, which are th inverter module 11, 12 th inverter module, 13 th inverter module and 14 th inverter module, wherein th inverter module 11 and 13 th inverter module are connected in series, 12 th inverter module and 14 th inverter module are connected in series, and the branch where th inverter module 11 and 13 are connected in series is connected in parallel with the branch where 12 th inverter module and 14 th inverter module are connected in series.
Each inversion module is provided with: a field effect transistor, a diode and a capacitor; the diode is connected in parallel with the drain and source of the field effect transistor in an inverse manner.
Wherein, in the th inverter module 11, the drain terminal Q of the th FET1And a negative terminal D of the th diode1A th capacitor C is connected in parallel between the drain and the source of the th FETq2。
In the second inverter module 12, the drain terminal Q of the second FET2And a negative terminal D of the second diode2Connecting; and a second capacitor C is connected in parallel between the drain and the source of the second field effect transistorq2。
In the third inverter module 13, the drain terminal Q of the third FET3And a negative terminal D of the third diode3Connecting; and a third capacitor C is connected in parallel between the drain and the source of the third field effect transistorq3。
In the fourth inverse transformation module 14, the drain terminal Q of the fourth FET4And a negative terminal D of a fourth diode4Connecting; a fourth capacitor C is connected in parallel between the drain and the source of the fourth field effect transistorq4。
Therefore, the inverter circuit of the present invention inputs the original DC voltage UdcIs converted into an alternating current signal.
The output end of the th inverter module 11 is set as point A, the second output end of the second inverter module 12 is set as point B, and a resonant circuit is connected between the th output end A and the second output end B of the inverter circuit.
As shown in FIG. 2, the resonant circuit of the present invention includes a resonant capacitor CpAnd a resonant inductor LpResonant capacitor CpAnd a resonant inductor LpAre connected in series.
The compensating circuit of the present invention includes a th compensating capacitor C1A second compensation capacitor C2And transformer Tr, th compensation capacitor C1A second compensation capacitor C arranged on the primary side side of the transformer Tr2Is arranged at the side of secondary side of transformer Tr, the ratio of the number of turns of primary side coil to the number of turns of secondary side coil of transformer Tr is n/1, wherein, the transformer Tr can generate primary side self-inductance L of transformerr1Transformer excitation inductance LmAnd secondary leakage inductance Lr2And the secondary side self-inductance of the transformer Tr is denoted as L2Then L is2＝Lr2+Lm. Resonant inductor Lp th compensation capacitor C1(also called primary side compensation capacitor) and primary side self-inductance Lr1Sequentially connected in series, a resonant capacitor CpConnected in parallel with the branch of the primary side of the transformer, and secondary side leakage inductance Lr2And a second compensation capacitor C2(also called secondary side compensation capacitor) are connected in series.
The equivalent resonant circuit in fig. 2a is provided with a th resonant inductor Lp1A second resonant inductor Lp2And a resonance capacitor Cp th resonant inductor Lp1And a second resonant inductor Lp2Series resonant capacitor CpInductance L resonant with thp1Are connected in series; and a resonant capacitor CpAnd a second resonant inductor Lp2And (4) connecting in parallel.
Wherein the second resonant inductor Lp2Is a virtual inductor, does not actually exist, is a virtual quantity introduced to serve as a convenient analytical circuit, so the th resonant inductor L in fig. 2ap1Equivalent to the resonant inductor L in fig. 2p。
The equivalent compensation circuit in fig. 2a comprises a th compensation capacitor C1A second compensation capacitor C2And a transformer T-type equivalent model. Leakage inductance L in transformer T-shaped equivalent modelr1-Lp2ViceEdge leakage inductance Lr2And transformer excitation inductance LmWherein the th compensation capacitor C1Leakage inductance Lr1-Lp2Secondary leakage inductance Lr2And a second compensation capacitor C2Are connected in series; and the secondary leakage inductance Lr2And a second compensation capacitor C2Series branch circuit and transformer excitation inductance LmAnd (4) connecting in parallel.
Inductance L due to second resonancep2Are all connected in series with a leakage inductance Lr1-Lp2Then the second resonant inductor Lp2And leakage inductance Lr1-Lp2component-L ofp2Cancel out, in order to make the th resonance inductance Lp1Resonant capacitor CpA second resonant inductor Lp2Forming LCL immittance converter, having the function of converting voltage source into current source, and setting th resonant inductor Lp1Equal to the second resonant inductance Lp2。
Compensation circuit and load resistor R of the inventionLDA full-bridge rectification circuit can be arranged between the compensation circuit and the compensation circuit to perform rectification and convert the alternating current signal output by the compensation circuit into an output direct current signal. Wherein the second compensation capacitor C2And a rectifying circuit and a load resistor RLDAnd (4) connecting in parallel.
th compensation capacitor C in the compensation circuit of the invention1The function of the system is to compensate the inductive reactive power of the system, reduce the circulating energy and increase the efficiency of the system. Second compensation capacitor C in compensation circuit2The constant current resonant type direct current conversion circuit has the function of compensating the current precision problem caused by the parasitic inductance of the transformer and improving the output current precision of the constant current resonant type direct current conversion circuit.
The principle of the constant current resonance type dc conversion circuit of the present invention is described in detail below with reference to fig. 2 a:
for convenience of analysis C1And C2The transformer excitation inductance L of the T-shaped equivalent model of the transformer in FIG. 2a can be obtainedmThe secondary side of (also called the secondary side, side away from the inverter circuit) is equivalent to fig. 4, and the secondary side (also called the primary side, side near the inverter circuit) is equivalent to fig. 5.
As shown in fig. 4, the minor edge is complementedConverting the compensation circuit to the primary side for equivalence, and setting the equivalent impedance of the secondary side as Zr(ii) a At this time, the second resonant inductor Lp2 th compensation capacitor C1Leakage inductance Lr1-Lp2And secondary equivalent impedance ZrThe branch circuit and the resonant capacitor C connected in seriespAnd (4) connecting in parallel.
The input voltage of the AC signal output from the inverter circuit to the resonant circuit is set to
Corresponding to an input current of
Wherein, the secondary equivalent impedance ZrThe calculation formula of (2) is as follows:
in the formula, LmFor transformer excitation inductance, RLDIs a load resistance, Lr2Secondary leakage inductance; omegaoWhich is the operating frequency of the field effect transistor of the inverter circuit and is a set constant value, and j represents the imaginary part of the complex number.
To ensure the input voltage
And input current
Is zero, no imaginary part of the total impedance of the circuit, i.e. th compensation capacitor C, can occur1Leakage inductance Lr1-Lp2And secondary equivalent impedance ZrThe imaginary part of (c) is in series resonance, which can be given by equations (2) and (3):
wherein ω is the operating frequency of the field effect transistor of the inverter.
As shown in fig. 5, the primary side compensation circuit is converted to the secondary side for equivalence, and then the equivalent primary side compensation circuit and the second compensation capacitor C are obtained2Are all connected with a load resistor RLDParallel connection; equivalent resonant circuit and load resistor R after equivalenceLDAnd (4) connecting in parallel.
Second compensation capacitor C2Secondary leakage inductance L with transformerr2And transformer excitation inductance LmAt resonance with RLDThe impedance of the parallel equivalent resonant circuit is infinite, which is equivalent to an open circuit.
So that the second compensation capacitor C2The values of (A) are:
according to the norton-thevenin theorem, it is possible to obtain:
wherein the content of the first and second substances,
compensating the capacitance C for passing through th1The alternating current of (1);
for compensating the output of the circuit to the load resistor RLDThe alternating current of (1).
In FIG. 4, the inductance L is due to the th resonancep1Resonant capacitor CpA second resonant inductor Lp2The LCL immittance converter is formed to act as a compensation capacitor C flowing through a th1Current i of1The calculation formula of (2) is as follows:
where θ is the phase shift angle.
The load resistance R can be obtained by bringing the formula (5-2) into the formula (5-1)LDOutput current I of the direct current signaloExpression (c):
from the formula (6), the load resistance RLDOutput current I ofoOf only the input voltage UdcPhase shift angle theta, resonance frequency omegaoAnd a resonant inductance L of the resonant circuitp1And a transformer excitation inductance L of the compensation circuitmAnd secondary leakage inductance Lr2(ii) related; and a load resistance RLDThe size is irrelevant, so the constant current resonance type direct current conversion circuit realizes the constant current characteristic. Wherein the load resistance RLDOutput current I ofoIs recorded as Uo
Wherein, for equations (1) and (2), ωoFor the resonant frequency, in order to put the present invention in a resonant state, the following condition should be satisfied when designing a resonant circuit:
in summary, the dc current finally output by the constant current resonant dc conversion circuit of the present invention is independent of the load resistance.
FIG. 6 is a simulation analysis diagram of the characteristics of the constant current and the frequency of the constant current resonance circuit of the invention; fig. 7 is a simulation analysis diagram of the frequency and phase characteristics of the constant current of the novel constant current resonance circuit of the invention. As shown in FIG. 6, the abscissa is frequency (unit: Hz); the ordinate is the output current Io(unit: ampere). As shown, the abscissa is frequency (unit: Hertz); the ordinate is the phase angle.
In the simulation circuit, the resonance frequency ω in the constant current resonance type dc conversion circuit of the present invention is setoIs 100 khz; resonant frequency omegaoAt load resistance RLDOutput current I ofoNon-following load resistance RLDIs varied regardless of the load resistance RLDEither increasing or decreasing.
The phase of the circuit is at the resonant frequency omegaoThe frequency of the resonant frequency omega is always zero, and the simulation result proves that the circuit works at the resonant frequency omegaoThe output current can be kept constant in the vicinity.
The constant-current resonant DC conversion circuit can also be provided with an overvoltage protection circuit for protecting the circuit.
Illustratively, as shown in fig. 2, when the circuit of the present invention is applied to charging a high-voltage battery pack, the transformer Tr is high-frequency transformers, and the specific design method of the circuit is as follows:
(1) according to the design requirements of the high-voltage storage battery pack charging system on volume and weight, the working frequency omega of the field effect transistor is preliminarily estimatedo：
ωo＝2πfo(8)
Wherein f is0Is the duty cycle of the fet.
(2) Measuring secondary self-inductance L of high-frequency transformer used2According to equation (4), calculating the second compensation capacitance C2A value of (b), wherein L2＝Lr2+LmI.e. secondary side self-inductance L of the transformer2Equivalent to secondary leakage inductance Lr2And transformer excitation inductance LmAnd, therefore, the following can be obtained:
(3) designing output current i according to the magnitude of current required by charging of the high-voltage storage battery packoAccording to the output current ioAnd according to equation (6), the resonant inductance L is calculatedpAnd a resonance capacitor CpThe value of (c) can be given as:
wherein θ is a phase shift angle, LmFor transformer excitation inductance udcIs a dc input voltage.
(4) To ensure the input voltage
And input currentIs zero and no imaginary part can appear in the total impedance of the circuit, i.e. th compensation capacitor C1Leakage inductance Lr1-Lp2And secondary equivalent impedance ZrSo that the th compensation capacitor C can be obtained according to the formula (1) and the formula (2)1：
Wherein L isr1Is the primary side self-inductance of the transformer.
In summary, according to the calculation results, the working efficiency of the resonant converter is measured in combination with experiments, and if the design requirements of the system cannot be met, each resonant parameter of the constant-current resonant type dc conversion circuit of the present invention is redesigned, and iteration is repeated until the optimal parameter value is reached.
For example, the invention has strong adaptability to the parasitic parameters of the transformer, and when the transformer is replaced by a loosely coupled transformer, the constant current can still be output in an open loop. The circuit and method for applying the loosely coupled transformer is the same as the circuit applied to charging the high voltage battery pack, except that the transformer is changed to a loosely coupled transformer. In order to reduce the parasitic resistance of the transformer, a larger inductance value can be achieved by using fewer turns, and a ferrite sheet is clamped in the middle of the coil, so that the inductance value of the coil can be greatly increased, the power transmission capability of the transformer is improved, and meanwhile, the working efficiency is improved.
Therefore, the non-contact power supply system of the circuit provided by the invention can output constant current in an open loop mode, and has higher practicability compared with the traditional inductive coupling energy transmission circuit which does not have the output capacity of open loop constant voltage or current.
While the present invention has been described in detail with reference to the preferred embodiments, it should be understood that the above description should not be taken as limiting the invention. Various modifications and alterations to this invention will become apparent to those skilled in the art upon reading the foregoing description. Accordingly, the scope of the invention should be determined from the following claims.
Claims (7)
1, constant current resonance type DC conversion circuit adapting to transformer high parasitic parameter, characterized in that, it includes:
the inverter circuit comprises a plurality of inverter modules, and the inverter module is used for inverting an original power supply input voltage signal connected with the inverter circuit into an alternating current voltage signal;
the resonance circuit is connected with the inverter circuit and receives an alternating voltage signal provided by the inverter circuit; the resonance circuit is provided with a resonance inductor and a resonance capacitor, so that an alternating voltage signal is converted into an alternating current signal;
the compensating circuit is provided with a transformer, an th compensating capacitor for compensating inductive reactive power consumed by the transformer and a second compensating capacitor for compensating the current precision of the transformer, wherein the th compensating capacitor is arranged on the primary side side of the transformer, and the second compensating capacitor is arranged on the secondary side side of the transformer;
the rectifying circuit is connected with the compensating circuit, converts an alternating current signal output by the compensating circuit into a direct current signal and outputs the direct current signal to the load resistor;
the resonance capacitor is connected with the resonance inductor in series;
the calculation formula of the resonance capacitance is as follows:
wherein L ispIs a resonant inductor; cpIs a resonant capacitor; omegaoIs the resonant frequency;
the transformer comprises a primary side self-inductance and a secondary side self-inductance, wherein the secondary side self-inductance is equal to the sum of the excitation inductance of the transformer and the secondary side leakage inductance of the transformer;
the th compensation capacitor and the resonance inductor are connected in series with a branch circuit on the primary side side of the transformer;
a branch formed by connecting the side of the primary side of the transformer and the resonance inductor in series is connected with the resonance capacitor in parallel;
the second compensation capacitor is connected in series with a branch circuit on the secondary side side of the transformer, and the second compensation capacitor is connected in parallel with the rectifying circuit and the load resistor;
the direct current signal received by the load resistor is a constant current signal which does not change along with the change of the load resistor;
the direct current I output by the load resistoroThe calculation formula of (2) is as follows:
Lmis the value of the excitation inductance, omega, of the transformeroIs the resonant frequency; l isr2The secondary leakage inductance value is obtained; l isp1Is the value of the resonance inductance; u shapedcThe original input voltage value of the inverter circuit is obtained; theta is a phase shift angle.
2. The constant current resonance type DC conversion circuit according to claim 1,
the plurality of inversion modules are respectively an th inversion module (11), a second inversion module (12), a third inversion module (13) and a fourth inversion module (14);
the inversion module (11) and the third inversion module (13) are connected in series, the second inversion module (12) and the fourth inversion module (14) are connected in series, and the branch where the inversion module (11) and the third inversion module (13) are connected in series is connected in parallel with the branch where the inversion module (12) and the fourth inversion module (14) are connected in series;
each inversion module is provided with an inversion switch tube, an inversion diode and an inversion capacitor, and any switch tube is respectively connected with the inversion diode and the inversion capacitor in parallel correspondingly.
3. The constant current resonance type DC conversion circuit according to claim 1,
the calculation formula of the second compensation capacitor is as follows:
C2is a second compensation capacitance value, ωoIs the resonant frequency, L2The secondary side of the transformer is self-inductance.
4. The constant current resonance type DC conversion circuit according to claim 1,
the calculation formula of the th compensation capacitor is as follows:
Cpis the value of the resonant capacitance, C1Compensating the capacitance value, L, for the thr1Is the primary side self-inductance of the transformer.
5. The constant current resonance type DC conversion circuit according to claim 1,
it is suitable for high-voltage storage battery charging system.
6. The constant current resonance type DC conversion circuit according to claim 1,
the transformer is a loosely coupled transformer.
7, design methods using constant current resonance type DC conversion circuits according to any of claims 1-6, characterized by the steps of:
s1: pre-estimated resonance frequency omegaoThe following can be obtained:
ωo＝2πfo；
wherein f is0Is the duty cycle of the switching tube of the inverter circuit;
s2: measuring secondary side self-inductance L of transformer2Calculating a second compensation capacitance C2The following can be obtained:
s3: setting output current ioAnd according to the output current ioTo calculate the resonant inductance L of the resonant circuitpAnd a resonance capacitor CpThe following can be obtained:
wherein θ is a phase shift angle, LmIs the excitation inductance of the transformer, udcThe original direct current input voltage of the inverter circuit is obtained;
s4 calculating th compensation capacitor C1The value of (c):
Lr1is the primary side self-inductance of the transformer.
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