CN107529348B - Power supply circuit for driving creeping discharge element - Google Patents
Power supply circuit for driving creeping discharge element Download PDFInfo
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- CN107529348B CN107529348B CN201680018798.XA CN201680018798A CN107529348B CN 107529348 B CN107529348 B CN 107529348B CN 201680018798 A CN201680018798 A CN 201680018798A CN 107529348 B CN107529348 B CN 107529348B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0009—Devices or circuits for detecting current in a converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
- H02M1/007—Plural converter units in cascade
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Inverter Devices (AREA)
Abstract
According to the power supply circuit for driving a creeping discharge element of the embodiment, a creeping discharge element is driven, a discharge electrode and an inductive electrode of which are arranged with a dielectric interposed therebetween, and a switching circuit is formed by connecting two series circuits including a positive side switching element and a negative side switching element in parallel and is supplied with a direct-current power supply. The smoothing capacitor is connected in parallel with the switching circuit, and the primary side of the transformer is connected between output terminals of the switching circuit. The current detection means detects a current flowing through the negative-side switching element, and the control means turns off the negative-side switching element based on a zero-crossing point of the current detected by the current detection means.
Description
Technical Field
Embodiments of the present invention relate to a power supply circuit for driving a creeping discharge element.
Background
The power supply circuit for driving the creeping discharge element includes, for example, a switching circuit for switching a dc voltage source, a resonant reactor, a high-voltage transformer for boosting a voltage, and a creeping discharge element. Further, a high-frequency high voltage is generated by utilizing a resonance phenomenon generated by capacitance components of the resonant reactor and the creeping discharge element. In such a configuration, the capacitance component of the creeping discharge element greatly varies depending on not only the installation environment but also the growth state of the streamer during discharge. Therefore, as disclosed in patent document 1, it is necessary to limit the electric power determined by the voltage and the current and operate the resonance frequency within a certain range.
Documents of the prior art
Patent document
Patent document 1: japanese patent No. 4029422.
Disclosure of Invention
Problems to be solved by the invention
Therefore, a power supply circuit for driving a creeping discharge element is provided, which can stably operate without limiting the output range even if the stray capacitance of the creeping discharge element varies due to the external environment and discharge.
Means for solving the problems
According to the power supply circuit for driving a creeping discharge element of the embodiment, a creeping discharge element having a discharge electrode and an inductive electrode arranged with a dielectric interposed therebetween is driven, and a switching circuit is formed by connecting two series circuits including positive-side and negative-side switching elements in parallel and supplied with a dc power supply. The smoothing capacitor is connected in parallel with the switching circuit, and the primary side of the transformer is connected between output terminals of the switching circuit. The current detection means detects a current flowing through the negative-side switching element, and the control means turns off the negative-side switching element based on a zero-crossing point of the current detected by the current detection means.
Drawings
Fig. 1 is a diagram showing embodiment 1 and showing an electrical configuration of a power supply circuit.
Fig. 2 is a timing chart showing the operation of the power supply circuit.
Fig. 3 is a time chart showing an operation when the load capacity is small.
Fig. 4 is a time chart showing an operation when the load capacity is large.
Fig. 5 is a diagram showing an electrical configuration of the drive signal generation circuit.
Fig. 6 is a timing chart showing the operation of the drive signal generation circuit.
Fig. 7 is a flowchart centered on MCU-based control content.
Fig. 8 is a timing chart showing a state in which the power supply circuit intermittently operates.
Fig. 9 is a diagram showing an electrical configuration of the power detection circuit.
Fig. 10 is a timing chart showing power control in the power supply circuit.
Fig. 11 is a diagram showing embodiment 2 and showing an electrical configuration of a power supply circuit.
Fig. 12 is a timing chart showing the operation of the power supply circuit.
Fig. 13 is a diagram showing an electrical configuration of the drive signal generation circuit.
Fig. 14 is a timing chart showing the operation of the drive signal generation circuit.
Detailed Description
(embodiment 1)
Hereinafter, embodiment 1 will be described with reference to fig. 1 to 10. Fig. 1 shows an electrical configuration of a power supply circuit in the present embodiment. The rectifier circuit 1 includes, for example, a three-phase rectifier 3, a current-limiting reactor 4, and a smoothing capacitor 5 connected to a commercial three-phase ac power supply 2, and converts 200v (vac) of three-phase ac into 280v (vdc) of dc.
The step-down circuit 6 connected to the rectifier circuit 1 includes a series circuit of switching elements 7 and 8, and a series circuit of a reactor 9 and a smoothing capacitor 10 connected in parallel to the switching element 8, and steps down the output voltage of the rectifier circuit 1 to 20V to 200V. For the switching elements 7 and 8, for example, an IGBT (insulated Gate bipolar Transistor) having a free wheel diode is used, but a power device such as a MOSFET (Field Effect Transistor) may be used. In addition, a semiconductor device such as a rectifier, which is not a self-extinguishing element, may be used as the switching element 8.
The series resonant circuit 11 connected to the step-down circuit 6 includes a switching circuit (H-bridge circuit) 12 including switching elements 12a, 12b, 12c, and 12 d. A primary winding 15 of a high-frequency high-voltage transformer 14 is connected between output terminals of the switching circuit 12 via a resonant reactor 13. A creeping discharge element 17 (discharge element capacitance) indicated by a capacitor is connected to the secondary winding 16 of the high-frequency high-voltage transformer 14. The creeping discharge element 17 has a dielectric 17c disposed between a discharge electrode 17a and an inductive electrode 17 b.
Next, the operation of the present embodiment will be described with reference to fig. 2 to 10. As shown in fig. 2, the drive signals of the switching elements 12a and 12b are output so that the elements 12a and 12b are turned on at a load of 50% of the switching frequency set to the creeping discharge period. The MCU19 turns off (turns off) at the timing when the switching elements 12a and 12c are simultaneously turned on and the zero-crossing point of the resonance current flowing through the resonance reactor 13 and the high-frequency high-voltage transformer 14 is detected by the current detection element 18 b. Similarly, the MCU19 turns off when the switching elements 12a and 12d are turned on simultaneously and when the zero-crossing point of the resonance current is detected. The resonant frequency of the resonant current is higher than the switching frequency of the switching elements 12a and 12b, and therefore is faster than the control cycle of the MCU 19.
Here, the resonance frequency changes depending on the stray capacitance of the creeping discharge element 17 itself and the capacitance component corresponding to the growth state of the streamer generated at the time of discharge. In particular, when the creeping discharge element 17 is installed outdoors, the stray capacitance changes due to, for example, environmental factors such as rain, and the collision of dust with the creeping discharge element 17. Fig. 3 and 4 show secondary-side voltage and current waveforms of the high-frequency high-voltage transformer 14 when a load fluctuation occurs, and the resonance frequency and the zero-crossing point of the current are different depending on the magnitude of the load. In the creeping discharge element 17 in which such load fluctuation occurs, if the zero-crossing point of the resonance current is not detected and the off command of the switching elements 12c and 12d is generated, the normal resonance operation cannot be maintained.
In addition, when the load capacitance shown in fig. 4 is large, the resonance frequency becomes 2 times the switching frequency. In such a load state, there is a possibility that short-circuit occurs between the switching elements 12a to 12d and 12b to 12c of the switching circuit 12. Therefore, when the zero-crossing point of the resonant current is detected and the resonant frequency is close to 2 times the switching frequency, the switching frequency is lowered and the zero-current period is generated as in the case where the load capacity is small, thereby enabling safe operation.
In this way, in the power supply circuit 20 for driving the creeping discharge element 17 having a large load variation, if the series resonant circuit 11 is not controlled based on the zero-crossing point of the current, not only the operable range is limited, but also the reliability of the circuit element is reduced. In order to stably generate the drive signal in accordance with the load environment, a circuit is used which detects the zero-crossing point of the resonance current and generates an interrupt signal for turning off the switching element 12c (and 12d) as shown in fig. 5.
In this example, a circuit in a case where a shunt resistor is used as the current detection element 18 is shown. Since the current detected via the shunt resistor 18 is a weak signal, the signal is amplified by the differential amplifier circuit 21, and the SN ratio is improved. The differential amplifier circuit 21 includes an operational amplifier 22, and a non-inverting input terminal of the operational amplifier 22 is connected to one end (an emitter of the switching element 12 c) of the shunt resistor 18 via a resistor element 23 and is pulled up via a resistor element 24. The inverting input terminal of the operational amplifier 22 is connected to the other end (ground) of the shunt resistor 18 via a resistor element 25, and is connected to the output terminal of the operational amplifier 22 via a resistor element 26.
The signal amplified by the differential amplifier circuit 21 is converted into a digital signal based on the zero-crossing point of the current by a digital conversion circuit 27 at the next stage. The digital conversion circuit 27 includes a comparator 28, and a non-inverting input terminal of the comparator 28 is connected to an output terminal of the differential amplifier circuit 21 via a resistance element 29 and is grounded via a capacitor 30. The inverting input terminal of the comparator 28 is connected to a common connection point of a series circuit of the resistance elements 31 and 32 that divide the dc power supply voltage, and is grounded via a capacitor 33. The output terminal of the comparator 28 is pulled up via the resistance element 34 and grounded via the capacitor 35.
The digital conversion circuit 27 is given hysteresis characteristics in advance so that a high-level signal can be output when no current normally flows, and the comparison signal of the comparator 28 is changed until the current value becomes negative. With this configuration, the output signal of the digital conversion circuit 27 changes from high level to low level at the zero-crossing point of the resonance current.
The output signal of the Digital converter circuit 27 is input to the MCU19 via an insulator (Digital Isolator) 36 for insulating the main circuit from the control circuit and a low-pass filter 39 including a resistor 37 and a capacitor 38. As described above, the differential amplifier circuit 21 to the low-pass filter 39 constitute the drive signal generation circuit 40. The falling edge of the output signal of the drive signal generation circuit 40 becomes an interrupt signal to the MCU19, i.e., a zero-crossing signal.
Since the zero-cross signal input to the MCU19 is a signal having a frequency of, for example, several 10kHz to 100kHz, the insulator 36 uses a digital isolator capable of high-speed conversion. The MCU19 outputs an off command (drive signal) to the switching elements 12c and 12d at the falling edge (off interrupt) of the input interrupt signal. Then, as shown in fig. 6, the switching elements 12c and 12d are turned off by the off command after being subjected to software processing in the MCU19 and a delay of a not-shown switch driving circuit. In this case, since it is necessary to turn off the resonant current while the resonant current is negative, the gate load of the drive circuit is set to a constant that can be turned off with a minimum load.
Fig. 7 is a control flowchart of the series resonant circuit 11 shown centering on processing by the MCU 19. First, when the switching elements 12a and 12c are simultaneously turned on (S1), the simultaneous on state is maintained until the off-state of the switching element 12c is input (S2: no). When the off-interruption of the switching element 12c is input (S2: YES), the switching element 12c is turned off (S3). After the switching element 12a is turned on, the on state is continued for a period obtained by subtracting a dead time set for preventing short-circuiting from 1/2 of the switching period (S4, S5).
After the dead time has elapsed (S6), the switching elements 12b and 12d are simultaneously turned on (S7), and the switching element 12d is turned off (S9) by inputting the off-interrupt signal of the switching element 12d (S8: yes), as in the case of the switching elements 12a and 12 c. The on state of the switching element 12b is maintained for a period obtained by subtracting the dead time from 1/2 in the switching cycle (S10, S11). After the dead time has elapsed (S12), if the operation stop command is not input (S13: NO), the process returns to step S1, and if the operation stop command is input (S13: YES), the operation is ended.
Next, a power control method in the power supply circuit 20 will be described with reference to fig. 8 to 10. The output voltage of the step-down circuit 6 is controlled to input electric power to the creeping discharge element 17. The power is preferably detected on the secondary side of the high-frequency high-voltage transformer 14. However, when the high-frequency high-voltage transformer 14 is used outdoors, the output power of the step-down voltage circuit 6 on the primary side of the high-frequency high-voltage transformer is detected because the insulating mechanism for preventing lightning strike is enlarged. However, the output power of the step-down circuit 6 includes discharge power, loss of the switching elements 12a to 12d, loss of the high-frequency high-voltage transformer 14, and loss due to wiring resistance from the high-frequency high-voltage transformer 14 to the creeping discharge element 17. Further, when the current is detected by the current detection element 18 such as a shunt resistor, the current detection element 18 also includes a loss. Therefore, when controlling the discharge power, there is a problem of deterioration in accuracy due to the primary side loss that changes according to the temperature characteristics and the load fluctuation.
Further, since the creeping discharge element 17 has a shortened lifetime due to discharge, it may be intermittently operated (load operation) as shown in fig. 8 in order to reduce the shortened lifetime. This makes it difficult to detect electric power. Further, depending on the creeping discharge element, it is conceivable that the discharge power differs depending on whether the applied voltage is positive or negative, and the discharge power includes reactive power for supplying current to the capacitance component of the discharge electrode.
Therefore, as shown in fig. 9, the discharge power is controlled by a circuit that detects the average power of the primary power of the high-frequency high-voltage transformer 14. A series circuit of the resistance elements 41 and 42 is connected in parallel with the primary winding 15, and both ends of the resistance element 42 are connected to input terminals of the insulator 43. That is, the terminal voltage of the primary winding 15 is divided and input to the multiplier 46 via the insulator 43, the differential amplifier circuit 44, and the low-pass filter 45.
The differential amplifier circuit 44 includes an operational amplifier 47, and a non-inverting input terminal of the operational amplifier 47 is connected to one output terminal of the insulator 43 via a resistance element 48 and is grounded via a resistance element 49. The inverting input terminal of the operational amplifier 47 is connected to the other output terminal of the insulator 43 via the resistance element 50, and is connected to the output terminal of the operational amplifier 47 via the resistance element 51. The low-pass filter 45 includes a resistance element 52 and a capacitor 53.
A current detection element 54 is inserted into one end of the primary winding 15, and a detection output terminal of the current detection element 54 is connected to an input terminal of the multiplier 46. The multiplier 46 multiplies the terminal voltage of the primary winding 15 by the primary current detected by the current detection element 54 to obtain the primary power. The multiplication result of the multiplier 46 is input to the MCU19 through the inverting amplification circuits 55 and 56 and the low-pass filter 57.
The inverting amplifier circuit 55 includes an operational amplifier 58. The inverting input terminal of the operational amplifier 58 is connected to the output terminal of the multiplier 46 via the resistance element 59, and is connected to the output terminal of the operational amplifier 58 via a parallel circuit of the resistance element 60 and the capacitor 61. The non-inverting input terminal of the operational amplifier 58 is grounded via a resistance element 62.
The inverting amplifier circuit 56 of the next stage includes an operational amplifier 63. The inverting input terminal of the operational amplifier 63 is connected to the output terminal of the inverting amplifier circuit 55 via a resistance element 64, and is connected to the output terminal of the operational amplifier 63 via a resistance element 65. The non-inverting input terminal of the operational amplifier 63 is grounded via the resistance element 66. The low-pass filter 57 includes a resistance element 67 and a capacitor 68. The above constitutes the power detection circuit 69.
Fig. 10 is a waveform diagram showing a state in which the primary-side power of the high-frequency high-voltage transformer 14 is detected during the load operation from the start of discharge to the stop of discharge, and the output voltage of the step-down circuit 6 is controlled during the next load operation. The output voltage of the step-down circuit 6 is voltage-controlled based on the average value of the discharge power at the time of discharge stop in the previous load operation. The voltage-reducing circuit 6 is controlled to a target voltage determined by PI (proportional integral) control in the discharge stop by the MCU 19. By performing voltage control based on the average value of the discharge power of the load operation in this manner, it is possible to perform power control in which the positive and negative power changes on the primary side of the high-frequency high-voltage transformer 14 and the discharge operation is performed with a faster control cycle.
As described above, according to the present embodiment, in the power supply circuit 20 that drives the creeping discharge element 17, the switching circuit 12 is formed by connecting in parallel a series circuit including the positive side switching elements 12a and 12b and the negative side switching elements 12c and 12d, and is supplied with the dc power. The smoothing capacitor 10 is connected in parallel with the switching circuit 12, and the primary side of the high-frequency high-voltage transformer 14 is connected between the output terminals of the switching circuit 12. The current detection elements 18a and 18b are respectively disposed between the emitters of the negative- side switching elements 12d and 12c and the negative-side power supply line. When the resonant current flowing through the MCU19 is detected, the negative- side switching elements 12d and 12c are turned off based on the zero-crossing point of the current. Thus, even if the primary side loss changes due to temperature characteristics, load variations, or the like, the resonance state can be reliably maintained, and the discharge power can be controlled with high accuracy.
(embodiment 2)
Fig. 10 to 14 show embodiment 2, and the same portions as those in embodiment 1 are given the same reference numerals to omit descriptions, and different portions are described. As shown in fig. 11, in the power supply circuit 71 according to embodiment 2, one current detection element 18 is connected between the common connection point of the switching elements 12c and 12d, that is, between the emitters of both and the negative terminal of the smoothing capacitor 10.
Next, the operation of embodiment 2 will be described with reference to fig. 11 to 14. In addition, the control content based on the MCU19 is the same as that shown in fig. 7. As shown in fig. 12, as in embodiment 1, switching elements 12c and 12d are switched based on the zero-crossing point of the resonance current flowing through series resonant circuit 11. However, in the case of embodiment 2, the zero-crossing point of the resonance current generated when the switching elements 12a and 12c are turned on and the zero-crossing point of the resonance current generated when the switching elements 12b and 12d are turned on are mixed and detected by one current detection element 18.
Fig. 13 shows the configuration of the drive signal generation circuits 40c and 40d corresponding to the switching elements 12c and 12d, respectively. Basically, the configuration is the same as that of the drive signal generation circuit 40 of embodiment 1, but in embodiment 2, the connection between the current detection element 18 and the differential amplifier circuit 21c on the drive signal generation circuit 40c side is the same as that of embodiment 1, whereas the connection between the current detection element 18 and the differential amplifier circuit 21d on the drive signal generation circuit 40d side is reversed in the inverting input terminal and the non-inverting input terminal. By replacing the input signals of the respective amplifier circuits 21c and 21d in this manner, the off-interrupt signal can be generated at the zero-crossing point of the resonance current flowing through each of the switching elements 12c and 12 d.
Fig. 14 is a timing chart showing the operation of the drive signal generation circuits 40c and 40 d. The output signal of the drive signal generation circuit 40c changes from a high level to a low level when a negative current flows through the current detection element 18, and returns from the low level to the high level when the current value becomes zero. On the other hand, the output signal of the drive signal generation circuit 40d changes from high level to low level when a current of positive polarity flows through the current detection element 18, and returns from low level to high level when the current value becomes zero.
The off-interruption based on the output signal of the drive signal generation circuit 40c occurs after a delay of a dead time amount is performed even at the time of off-interruption based on zero-crossing detection on the switching element 12d side. However, at this time, since both the switching elements 12a and 12c are turned off, there is no problem even if the off-state interruption by the drive signal generation circuit 40c occurs. The same applies to the drive signal generation circuit 40d side.
As described above, according to embodiment 2, the single current detection element 18 is connected between the common connection point of the switching elements 12c and 12d and the negative terminal of the smoothing capacitor 14. In this way, even with a configuration in which the resonant currents flowing through the switching elements 12a to 12d are detected in a mixed state, the zero-crossing point of the resonant current can be detected, and the creeping discharge element 17 in which the load fluctuation occurs can control the discharge power with high accuracy while maintaining the resonant frequency.
Although several embodiments of the present invention have been described, these embodiments are presented as examples and are not intended to limit the scope of the invention. These new embodiments can be implemented in other various ways, and various omissions, substitutions, and changes can be made without departing from the spirit of the invention. These embodiments and modifications are included in the scope and gist of the invention, and are included in the scope equivalent to the invention described in the claims.
Industrial applicability of the invention
As described above, the creeping discharge element driving power supply circuit according to the present embodiment is useful as a power supply for driving a creeping discharge element.
Claims (2)
1. A power supply circuit for driving a creeping discharge element, which drives a creeping discharge element having a discharge electrode and an inductive electrode arranged with a dielectric interposed therebetween, the power supply circuit comprising:
a switching circuit in which two series circuits including positive-side and negative-side switching elements are connected in parallel and supplied with a direct-current power supply;
a smoothing capacitor connected in parallel to the switching circuit;
a transformer having a primary side connected between output terminals of the switching circuit;
a current detection unit that detects a current flowing through the negative-side switching element; and
a control unit for turning off the negative-side switching element based on a zero-crossing point of the current detected by the current detection unit,
the current detection means includes two current detection elements connected between the negative-side switching element and the negative-side power supply line of each group.
2. A power supply circuit for driving a creeping discharge element, which drives a creeping discharge element having a discharge electrode and an inductive electrode arranged with a dielectric interposed therebetween, the power supply circuit comprising:
a switching circuit in which two series circuits including positive-side and negative-side switching elements are connected in parallel and supplied with a direct-current power supply;
a smoothing capacitor connected in parallel to the switching circuit;
a transformer having a primary side connected between output terminals of the switching circuit;
a current detection unit that detects a current flowing through the negative-side switching element; and
a control unit for turning off the negative-side switching element based on a zero-crossing point of the current detected by the current detection unit,
the current detection means includes a current detection element inserted in a negative power supply line connecting the switching circuit and the smoothing capacitor.
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2015068862A JP6184436B2 (en) | 2015-03-30 | 2015-03-30 | Power circuit for driving creeping discharge elements |
| JP2015-068862 | 2015-03-30 | ||
| PCT/JP2016/060127 WO2016158950A1 (en) | 2015-03-30 | 2016-03-29 | Power circuit for driving creeping discharge element |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN107529348A CN107529348A (en) | 2017-12-29 |
| CN107529348B true CN107529348B (en) | 2020-04-07 |
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| CN201680018798.XA Active CN107529348B (en) | 2015-03-30 | 2016-03-29 | Power supply circuit for driving creeping discharge element |
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|---|---|
| JP (1) | JP6184436B2 (en) |
| CN (1) | CN107529348B (en) |
| DE (1) | DE112016001471T5 (en) |
| WO (1) | WO2016158950A1 (en) |
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| JP6462637B2 (en) | 2016-08-10 | 2019-01-30 | 株式会社東芝 | Creeping discharge element driving apparatus and creeping discharge element driving method |
| JP2019080367A (en) * | 2017-10-20 | 2019-05-23 | 日本特殊陶業株式会社 | High voltage pulse power supply and power control method thereof |
| TW202128865A (en) | 2019-11-18 | 2021-08-01 | 美商陶氏全球科技有限責任公司 | Heat aging-resistant and flexible polyolefin formulation |
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| JPH088773B2 (en) * | 1986-10-06 | 1996-01-29 | 共栄電測株式会社 | High frequency power output controller |
| JPH09241007A (en) * | 1996-03-08 | 1997-09-16 | Ebara Corp | Ozone generating method and device |
| JP4029422B2 (en) * | 2001-12-19 | 2008-01-09 | 俊介 細川 | Power supply for driving creeping discharge elements |
| US7420829B2 (en) * | 2005-08-25 | 2008-09-02 | Monolithic Power Systems, Inc. | Hybrid control for discharge lamps |
| CN101127486A (en) * | 2006-07-31 | 2008-02-20 | 富士电机控股株式会社 | Power supply circuit and control method thereof |
| WO2009091273A1 (en) * | 2008-01-18 | 2009-07-23 | Nandor Burany | Corona discharge treater with resonant voltage multiplication |
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- 2016-03-29 CN CN201680018798.XA patent/CN107529348B/en active Active
- 2016-03-29 WO PCT/JP2016/060127 patent/WO2016158950A1/en active Application Filing
- 2016-03-29 DE DE112016001471.6T patent/DE112016001471T5/en not_active Ceased
Also Published As
| Publication number | Publication date |
|---|---|
| DE112016001471T5 (en) | 2017-12-14 |
| CN107529348A (en) | 2017-12-29 |
| WO2016158950A1 (en) | 2016-10-06 |
| JP2016189666A (en) | 2016-11-04 |
| JP6184436B2 (en) | 2017-08-23 |
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