CN107493117B - The two-dimentional joint acquisition method of direct expansion msk signal under a kind of high dynamic - Google Patents
The two-dimentional joint acquisition method of direct expansion msk signal under a kind of high dynamic Download PDFInfo
- Publication number
- CN107493117B CN107493117B CN201610406996.5A CN201610406996A CN107493117B CN 107493117 B CN107493117 B CN 107493117B CN 201610406996 A CN201610406996 A CN 201610406996A CN 107493117 B CN107493117 B CN 107493117B
- Authority
- CN
- China
- Prior art keywords
- signal
- code
- estimated value
- bpsk
- direct expansion
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Fee Related
Links
- 238000000034 method Methods 0.000 title claims abstract description 36
- 238000012937 correction Methods 0.000 claims abstract description 7
- 230000000694 effects Effects 0.000 claims abstract description 7
- 238000001914 filtration Methods 0.000 claims abstract description 7
- 238000000605 extraction Methods 0.000 claims abstract description 4
- 238000005070 sampling Methods 0.000 claims description 12
- 230000007480 spreading Effects 0.000 claims description 10
- 238000001228 spectrum Methods 0.000 claims description 9
- 230000004044 response Effects 0.000 claims description 7
- 238000012545 processing Methods 0.000 claims description 5
- 230000001934 delay Effects 0.000 claims description 2
- 230000008901 benefit Effects 0.000 abstract description 5
- 238000001514 detection method Methods 0.000 description 8
- 230000008859 change Effects 0.000 description 7
- 238000013461 design Methods 0.000 description 6
- 230000008569 process Effects 0.000 description 5
- 238000012935 Averaging Methods 0.000 description 3
- 230000005540 biological transmission Effects 0.000 description 3
- 238000004891 communication Methods 0.000 description 3
- 238000010586 diagram Methods 0.000 description 3
- 230000006872 improvement Effects 0.000 description 3
- 230000001360 synchronised effect Effects 0.000 description 3
- 238000004458 analytical method Methods 0.000 description 2
- 238000005516 engineering process Methods 0.000 description 2
- 239000000284 extract Substances 0.000 description 2
- 230000009466 transformation Effects 0.000 description 2
- 238000004364 calculation method Methods 0.000 description 1
- 230000021615 conjugation Effects 0.000 description 1
- 238000005562 fading Methods 0.000 description 1
- PCHJSUWPFVWCPO-UHFFFAOYSA-N gold Chemical group [Au] PCHJSUWPFVWCPO-UHFFFAOYSA-N 0.000 description 1
- 239000000203 mixture Substances 0.000 description 1
- 230000004048 modification Effects 0.000 description 1
- 238000012986 modification Methods 0.000 description 1
- 238000005457 optimization Methods 0.000 description 1
- 230000005855 radiation Effects 0.000 description 1
- 238000005316 response function Methods 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/69—Spread spectrum techniques
- H04B1/707—Spread spectrum techniques using direct sequence modulation
- H04B1/7073—Synchronisation aspects
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/69—Spread spectrum techniques
- H04B1/707—Spread spectrum techniques using direct sequence modulation
- H04B1/7073—Synchronisation aspects
- H04B1/7075—Synchronisation aspects with code phase acquisition
Landscapes
- Engineering & Computer Science (AREA)
- Computer Networks & Wireless Communication (AREA)
- Signal Processing (AREA)
- Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
Abstract
The present invention provides a kind of two-dimentional joint acquisition method of direct expansion msk signal under high dynamic, comprising the following steps: handles the received switched filter of intermediate frequency direct expansion msk signal, down coversion, low-pass filtering, extraction, obtains approximate DS-BPSK signal signal；Pairing approximation DS-BPSK signal signal and local code carry out joint acquisition, obtain the estimated value of code phase error and the estimated value of Doppler shift；It is subsequent to carry out accurate code tracking and despread-and-demodulation after carrying out Doppler effect correction based on above-mentioned estimated value pairing approximation DS-BPSK signal signal, obtain information.The present invention has that algorithm complexity is small, is completed at the same time pseudo-code phase and Doppler shift capture, the advantages such as evaluated error is small under high dynamic, is highly suitable for the application environment of high dynamic low signal-to-noise ratio.
Description
Technical field
The present invention relates to a kind of digital communication technology, under especially a kind of high dynamic, the two dimension of direct expansion msk signal, which is combined, catches
Obtain method.
Background technique
Currently, spread spectrum system mostly uses BPSK, QPSK modulation system, but both modulation systems can not be suitable for existing sternly
Weight non-linear distortion, the application environment of Doppler frequency shift and multipath fading.Direct expansion MSK communication system has spread spectrum system simultaneously
Constant-envelope, the availability of frequency spectrum of the advantages that low property intercepted and captured, the random address ability of multi-user, strong anti-interference performance and msk signal
The advantages that high, energy is concentrated, side lobe attenuation is fast, out-of-band radiation power is low, insensitive to non-linear distortion, tactical data link,
The fields such as civil aviation Ground-to-Air Data Link, missile guidance instruction transmission, satellite communication are widely applied.So direct expansion MSK
Signal still has a good application prospect in the field that DS-BPSK signal/QPSK signal can not be applicable in.
There are two types of classical msk signal catching methods, and one is based on relevant Code acquisition is slided, this method realizes letter
Single but capture time is very long；Another kind is the Code acquisition based on matched filtering.The capture relevant peaks of both methods are easily by more
The general influence for strangling frequency deviation, it is clear that the capture not being suitable under high dynamic.
It is nonlinear transformation combination FFT to the most classic estimation method of Doppler shift, specifically in the environment of high dynamic
Method is that will receive signal to do square or the multiple nonlinear transformation of side, further according to the index of spectrum peak after signal FFT processing
Offset estimation value is acquired, however the method can not work under low signal-to-noise ratio.G.J.R.Povey et al. is proposed first based on number
Partial-matched filter combines the Capturing Models of (PMF-FFT) with FFT, although this method alleviate to a certain extent it is more
The general influence for strangling frequency deviation to acquiring pseudo code performance, and the two dimension capture of pseudo-code phase and carrier wave frequency deviation is realized, but it is this
Method is mainly adapted to mpsk signal, and the search range of Doppler shift is smaller, still not applicable under high dynamic environment.Closely
Nian Lai has scholar to propose the code capture method under difference capture, the high dynamics such as two-step capturing successively, but be difficult to low signal-to-noise ratio with
Balance is obtained between estimated accuracy.Thus, how accurately and rapidly to be completed under high dynamic environment spread-spectrum signal pseudo-code phase and
The Combined estimator of Doppler shift becomes the key technology of direct expansion MSK all-digital receiver.
Summary of the invention
The purpose of the present invention is to provide a kind of two-dimentional joint acquisition methods of direct expansion msk signal under high dynamic, realize big
The capture of direct expansion msk signal under Doppler shift, so that direct expansion msk signal under high dynamic environment, realizes Doppler's frequency first
Offset compensation realizes the Code acquisition of signal in the case where inherent spurious frequency deviation does not influence relevant peaks.And under low signal-to-noise ratio, it can obtain
Higher detection probability is obtained, while obtaining higher precision, is handled with ensuring to receive signal in entering signal tracking (essence is synchronous)
It has just been obtained before module preferable thick synchronous.
The present invention the following steps are included:
By the received switched filter of intermediate frequency direct expansion msk signal, down coversion, low-pass filtering, extraction processing, obtain approximate straight
Expand bpsk signal,
Pairing approximation DS-BPSK signal signal and local code carry out joint acquisition, obtain estimated value and the Doppler of code phase error
The estimated value of frequency deviation,
After carrying out Doppler effect correction and despreading based on above-mentioned estimated value pairing approximation DS-BPSK signal signal, information is obtained, and lead to
Emit after crossing MSK modulation；Wherein
Joint acquisition includes:
Pairing approximation DS-BPSK signal signal and local code do convolution after delay disposal respectively, in local code and approximate DS-BPSK signal
When signal alignment, the maximum correlation peak position obtained by convolution obtains the estimated value of code phase error, is believed by relevant peaks
Number phase obtain Doppler shift estimated value.
As an improvement of the present invention, change delay sampling point, approximate DS-BPSK signal signal after obtaining several delays with
Local code, and to two signal convolution under same delay sampling point, it makes even to the estimated value of all Doppler shifts of acquisition
Mean value is as Doppler effect correction, the estimated value of despreading.
As an improvement of the present invention, what is obtained after being averaged to the phase of the multiple relevant peaks obtained after convolution is more
General Le offset estimation value is as Doppler effect correction, the estimated value of despreading.
As an improvement of the present invention, all related operations in algorithm can all replace convolution operation with FFT.
The present invention has the advantage that all correlations in (1) algorithm compared with traditional direct expansion msk signal catching method
Operation can all replace convolution operation with FFT, substantially reduce the complexity of algorithm；(2) to pseudo-code phase and carrier wave frequency deviation
It scans for simultaneously, capture time is M spreading code period, can be joined according to capture time and acquisition probability performance flexible choice
Number M；(3) delay multiplication processing is carried out by the way that signal and local code will be received, then correlation obtains relevant peaks and estimates code phase difference
And Doppler shift, it can control doppler range by adjusting retardation and delay number, reach and estimated accuracy
Between balance, be suitable for high dynamic environment；(4) direct expansion msk signal is handled with reception switched filter, is converted into
DS-BPSK signal signal solves the problems, such as that msk signal form is complicated, can will be suitable for the quick capturing method of DS-BPSK signal signal
Applied to direct expansion msk signal.
The present invention is described further with reference to the accompanying drawings of the specification.
Detailed description of the invention
Fig. 1 is the system composition block diagram of the embodiment of the present invention.
Fig. 2 is the Combined estimator module by signal process flow diagram of the embodiment of the present invention.
Fig. 3 be the embodiment of the present invention detection probability and false-alarm probability with input signal-to-noise ratio change curve schematic diagram.
Specific embodiment
Direct expansion msk signal carry out accurate despread-and-demodulation condition be signal synchronization, including pseudo-code and carrier synchronization.Signal
It synchronizes and is divided into that thick synchronization is synchronous with essence, and the present invention lays particular emphasis on signal and slightly synchronizes, is i.e. pseudo-code and Doppler shift capture.
Signal is sent using the form of " pilot code+transmission data ", is previously inserted into M complete 1 data symbols in transmission data
Number, spreading code and carrier synchronization to receiver end.Pilot code by after the compensation such as Doppler shift, code phase, believe by data
Number part can just carry out accurate despread-and-demodulation.
Serial mode generation, that is, signal and carrier wave cos (2 π f after spreading can be used in direct expansion msk signal1T) BPSK is carried out
Modulation obtains DS-BPSK signal signal, then converted filter g (t) can produce direct expansion msk signal.The impulse of switched filter is rung
It should be
Wherein,fcFor carrier frequency, T is spreading code chip width.
For this serial producing method of direct expansion msk signal, uses in receiving end and match with switched filter g (t)
Filter h (t) received, it is corresponding receive switched filter impulse response be
The output signal of switched filter is again through f1Down coversion, low-pass filtering, then carry out K times and extract, obtain approximate direct expansion
BPSK baseband signal.This extracting multiple is consistent with over-sampling multiple, exports baseband signal at this time and is represented by
Wherein, τ is code phase error；0 is set as initial phase for the convenience of analysis；RcFor spread-spectrum code rate；fd
For Doppler shift；ωnWhite noise is answered for Gauss；Due to pilot code partial data be 1, formula (3) it is rewritable at:
Pairing approximation DS-BPSK signal signal and local code carry out joint acquisition, comprising the following steps:
Step S101, will receive signal y (n) and carries out delay disposal, i.e., will receive signal and do after the delay of D sampling point and not
The conjugate multiplication of postpones signal is handled, and process is as follows:
Wherein, ω ' (n) is the noise after delay disposal.
Step S102, is modified local code c (n), that is, does same delay disposal:
cD(n)=c*(n)c(n+D) (6)
Step S103, by the signal y after delay disposalD(n) with local correcting code cD(n) convolution obtains:
Wherein, N is the spreading code period, and convolution can be carried out by correlator.
Step S104, by formula (7) it is found that when local code is with signal alignment is received, relevant peaks obtained by convolution are maximum:
So far, the estimated value of code phase errorIt can be obtained by relevant peaks position.
Compared with traditional Code acquisition algorithm, it is evident that this method eliminates Doppler frequencies to export relevant peaks peak to capture
The influence of value.
Step S105 is by the estimated value that Doppler shift can be obtained in the phase of relevant peaks signal
Wherein, arg [z] is the angle of plural number z；Indicate that relevant peaks export result.
The estimated value that formula (9) indicates is based only on a delay, in order to improve accuracy, introduces the concepts postponed more.Therefore,
Joint acquisition process change are as follows:
Step S201, initialization delay amount D=Dmax-d,DmaxFor maximum delay amount, d is delay number, herein maximum delay
Measure DmaxWith delay number d be it is controllable, to obtain biggish detection probability.
Step S202: while signal y (n) and local code c (n) will be received and do delay disposal, postpone the same above-mentioned steps of principle
S102 and S103 obtains yD(n) and cD(n)。
Step S203, by yD(n) and cD(n) input correlator carries out convolution, searches for correlation peak location in correlation output, can
M relevant peaks are obtained, relevant peaks position is code phase error estimated value herein
The estimated value of Doppler shift can be obtained with (9) by the phase of relevant peaks signal in step S204.
Step S205 judges whether D > DmaxIf Rule of judgment be it is no, change the value of D, D=D+1, return step S202；
If Rule of judgment be it is yes, enter step S206.
Step S206 averages to the estimated value of the Doppler shift of all acquisitions, as last Doppler shift
Estimated value
Wherein, d is delay number, as d=0, as single delay；DmaxTo postpone maximum value.
The Doppler shift estimation that the relevant peaks that above procedure is all based on a data symbol are made, can use M here
The method that the relevant peaks phase average of the pilot code of a symbol replaces the relevant peaks phase of a symbol improves precision, therefore catches
Obtain process modification are as follows:
Step S301, initialization delay amount D=Dmax-d,DmaxFor maximum delay amount, d is delay number, herein maximum delay
Measure DmaxWith delay number d be it is controllable, to obtain biggish detection probability.
Step S302: while signal y (n) and local code c (n) will be received and do delay disposal, postpone the same above-mentioned steps of principle
S102 and S103 obtains yD(n) and cD(n)。
Step S303, by yD(n) and cD(n) input correlator carries out convolution, searches for correlation peak location in correlation output, can
M relevant peaks are obtained, relevant peaks position is code phase error estimated value herein
Step S304, the same formula of estimated value (9) that Doppler shift can be obtained by the phase of relevant peaks signal.
The phase of M relevant peaks of gained is averaged by step S305:
Wherein,For the averaging of income phase value for postponing D；For the output valve of relevant peaks.
Step S306 judges whether D > DmaxIf Rule of judgment be it is no, change the value of D, D=D+1, return step S302；
If Rule of judgment be it is yes, enter step S307.
Step S307 averages to the estimated value of the Doppler shift of all acquisitions, as last Doppler shift
Estimated value
Wherein, d is delay number, as d=0, as single delay；DmaxTo postpone maximum value.
According to formula (12) it is found that Doppler shift search range of the invention are as follows:
Then, maximum Doppler estimates frequency deviation are as follows:
The innovation of the invention consists in that the matching output correlation peak using delay multiplication signal can obtain pseudo-code simultaneously
The estimated value of phase and Doppler shift realizes pseudo-code-Doppler shift two dimension joint acquisition, and postpones number d and delay maximum
Value DmaxIt is controllable, to obtain balance between detection probability and Doppler's estimation range.
Embodiment
The present invention is a kind of two-dimentional joint acquisition method of direct expansion msk signal under high dynamic.It, first will be in reception such as Fig. 1
The received switched filter of frequency direct expansion msk signal, down coversion, low-pass filtering, extraction processing, obtain approximate DS-BPSK signal signal,
This approximate DS-BPSK signal signal is sent into Combined estimator module again, obtains the estimated value of code phase error and Doppler shift, into
And complete the work of Code acquisition link.Signal is received after Doppler effect correction/despreading module, MSK modulated signal can be obtained.
System sampling frequency fs=245.52MHz, IF frequency fc=76.725MHz, over-sampling multiple K=12, spreading code
Rate is Rc=20.46Mchip/s, data rate 20kbps, spreading code use Gold sequence, code length N=1023, pilot code
Symbol numbers M=20.
The reception switched filter that intermediate frequency direct expansion msk signal is h (t) through impulse response is received, approximate DS-BPSK signal is obtained
Signal.Receive switched filter impulse response be
Wherein,For the spreading code period.The frequency response of switched filter is
The design of filter of the present invention uses convex optimisation technique, it is necessary first to convert convex optimization for filter design problem
The peakedness coefficient of switched filter can be established as convex Optimized model by problem:
Wherein, sup is infimum；The π of ω=2 f is angular frequency；D (ω) is given frequency response function；H (ω) is institute
The frequency response of the filter of design,H (n) is filter coefficient, N0For filter order.
The filter coefficient h (n) of practical application is acquired by the tool box cvx of Matlab software.
Signal after received switched filter is again through f1Down coversion, whereinLow-pass filtering after down coversion,
It extracts for K times again, this extracting multiple is consistent with over-sampling multiple.Since pilot code partial data is 1, obtaining baseband signal at this time is
Wherein, τ is code phase error；For initial phase；RcFor spread-spectrum code rate；fdFor Doppler shift；ωnFor height
This multiple white noise；In order to facilitate analysis, initial phase is set
As shown in Fig. 2, the step of joint acquisition module, is as follows:
Step 1: initialization delay amount D=Dmax-d。
DmaxFor maximum delay amount, d is delay number, herein maximum delay amount DmaxWith delay number d be it is controllable, to obtain
Biggish detection probability.
Step 2: while signal y (n) and local code c (n) will be received and do delay disposal.
Delay disposal process are as follows: by D sampling point of signal delay, be multiplied, postponed with the undelayed signal after conjugation is taken
Treated signal yD(n) and local correcting code cD(n)。
Step 3: by yD(n) and cD(n) correlator is inputted, correlation peak location is searched in correlation output, M correlation can be obtained
Peak.Relevant peaks position is code phase error estimated value herein
Step 4: the phase of M relevant peaks of gained is averaged:
Wherein,For the averaging of income phase value for postponing D；For the output valve of relevant peaks.
Step 5: judging whether D > Dmax。
If Rule of judgment be it is no, change the value of D, D=D+1, return step 2；If Rule of judgment be it is yes, enter step 6.
Step 6: (d+1) secondary phase calculation result is averaging, and calculates Doppler shift estimated value:
According to formula (20) it is found that Doppler shift search range of the invention are as follows:
Then, maximum Doppler estimates frequency deviation are as follows:
Fig. 3 is input signal-to-noise ratio SNR=[- 30dB, -5dB], fd=280kHz, maximum delay amount Dmax=36, postpone number d
=5, false-alarm probability PfWhen=0.001, obtained detection probability and false-alarm probability with signal-to-noise ratio change curve.Calculating formula (21)
Can obtain: Doppler shift estimation range is [- 284.17kHz, 284.17kHz].
As seen from the figure when signal-to-noise ratio reaches -20dB, detection probability reaches 0.9155, due to using constant false alarm thresholding
Design standard, false-alarm probability are hardly influenced by signal-to-noise ratio.It can be seen that pseudo-code-Doppler's joint acquisition method that the present invention designs
Pseudo-code phase and carrier wave frequency deviation can accurately be captured under high dynamic environment.
It can thus be seen that under the high dynamic that the present invention designs direct expansion msk signal two-dimentional combined estimation method, and it is existing
Catching method compare, have that algorithm complexity is small, is completed at the same time pseudo-code phase and Doppler shift capture, estimates under high dynamic
The advantages such as error is small, are highly suitable for the application environment of high dynamic low signal-to-noise ratio, have stronger practical value.
Claims (5)
1. the two-dimentional joint acquisition method of direct expansion msk signal under a kind of high dynamic, which comprises the following steps:
By the received switched filter of intermediate frequency direct expansion msk signal, down coversion, low-pass filtering, extraction processing, approximate direct expansion is obtained
Bpsk signal,
Pairing approximation DS-BPSK signal signal and local code carry out joint acquisition, obtain the estimated value and Doppler shift of code phase error
Estimated value,
After carrying out Doppler effect correction based on above-mentioned two estimated value pairing approximation DS-BPSK signal signal, accurate code tracking reconciliation is carried out
Information is obtained after expanding demodulation；Wherein
Joint acquisition includes:
Pairing approximation DS-BPSK signal signal and local code do convolution after the delay disposal of D sampling point respectively, local code with it is approximate straight
When expanding bpsk signal alignment, the maximum correlation peak position obtained by convolution obtains the estimated value of code phase error, by correlation
The phase of signal obtains the estimated value of Doppler shift at peak.
2. the approximation after obtaining several delays is straight the method according to claim 1, wherein changing delay sampling point D
Expand BPSK delay disposal signal and local correcting code, and to two signal convolution under same delay sampling point, owns to acquisition
The estimated value of Doppler shift be averaged the estimated value as Doppler effect correction, despreading, wherein how general after being averaged
Strangling offset estimation value is
Wherein, the phase of relevant peaksD is delay sampling point, DmaxFor maximum delay amount, d is delay number, RD
(*) is approximate DS-BPSK signal signal and local code does signal after delay disposal after convolution respectively,For code phase error estimation
Value, RcFor spread-spectrum code rate.
3. according to the method described in claim 2, it is characterized in that, being averaged to the phase of the multiple relevant peaks obtained after convolution
After value obtain Doppler shift estimated value, wherein to the phase of multiple relevant peaks be averaged for
The Doppler shift estimated value obtained after being averaged to the phase of multiple relevant peaks is
Wherein, M is the quantity of relevant peaks.
4. method according to claim 1,2 or 3, which is characterized in that intermediate frequency direct expansion msk signal is produced using serial mode
It is raw, specifically: signal and carrier wave cos (2 π f after spread spectrum1T) BPSK is carried out to modulate to obtain DS-BPSK signal signal, then converted filter
Wave device generates direct expansion msk signal, and the impulse response of switched filter is
Wherein,fcFor carrier frequency, T is spreading code chip width.
5. according to the method described in claim 4, it is characterized in that, using the filter h to match with switched filter g (t)
(t) intermediate frequency direct expansion msk signal is received, the corresponding impulse response for receiving switched filter is
Wherein,fcFor carrier frequency, T is spreading code chip width.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201610406996.5A CN107493117B (en) | 2016-06-12 | 2016-06-12 | The two-dimentional joint acquisition method of direct expansion msk signal under a kind of high dynamic |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201610406996.5A CN107493117B (en) | 2016-06-12 | 2016-06-12 | The two-dimentional joint acquisition method of direct expansion msk signal under a kind of high dynamic |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN107493117A CN107493117A (en) | 2017-12-19 |
| CN107493117B true CN107493117B (en) | 2019-08-09 |
Family
ID=60642319
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201610406996.5A Expired - Fee Related CN107493117B (en) | 2016-06-12 | 2016-06-12 | The two-dimentional joint acquisition method of direct expansion msk signal under a kind of high dynamic |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN107493117B (en) |
Families Citing this family (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN109088838B (en) * | 2018-09-08 | 2020-11-06 | 南京理工大学 | Pseudo code-Doppler fast capturing method of direct sequence spread spectrum DPSK signal under high dynamic condition |
| CN109412644B (en) * | 2018-09-13 | 2021-02-12 | 南京理工大学 | Doppler frequency estimation method for direct sequence spread spectrum MSK signal |
| CN109150233B (en) * | 2018-09-13 | 2021-02-12 | 南京理工大学 | Modulation and demodulation method for direct sequence spread spectrum DPSK signal |
| CN109617570B (en) * | 2018-12-25 | 2020-09-18 | 西安空间无线电技术研究所 | Full-digital synchronization method for broadband frequency hopping direct sequence spread spectrum signal without data assistance |
| CN110601718B (en) * | 2019-09-05 | 2022-11-04 | 珠海市杰理科技股份有限公司 | Spread spectrum communication capturing method, device and system |
| CN111082835A (en) * | 2019-12-03 | 2020-04-28 | 南京理工大学 | Pseudo code and Doppler combined capturing method of direct sequence spread spectrum signal under high dynamic condition |
| CN114531329B (en) * | 2022-01-28 | 2023-08-22 | 西安电子科技大学 | Multipath MSK signal carrier frequency estimation method, system and application |
| CN116938657B (en) * | 2023-09-15 | 2023-12-29 | 武汉船舶通信研究所(中国船舶集团有限公司第七二二研究所) | DSSS-OQPSK signal demodulation method and device |
Family Cites Families (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104218972B (en) * | 2014-08-27 | 2016-05-04 | 西安空间无线电技术研究所 | A kind of spreading code phase place and three-dimensional quick capturing method of carrier doppler of jumping |
| CN104639100B (en) * | 2015-02-12 | 2017-09-22 | 南京理工大学 | Produce the method and switched filter design method of DS msk signal |
| CN104833988B (en) * | 2015-04-30 | 2017-12-22 | 西安空间无线电技术研究所 | The capture systems and method of the lower high data rate direct sequence signal of large doppler dynamic |
| CN105141340B (en) * | 2015-07-24 | 2018-01-05 | 南京理工大学 | The digital method of reseptance of DS msk signal |
| CN105162493B (en) * | 2015-08-04 | 2017-07-14 | 北京理工大学 | Doppler domain and the two-dimentional catching method of delay domain and device |
-
2016
- 2016-06-12 CN CN201610406996.5A patent/CN107493117B/en not_active Expired - Fee Related
Also Published As
| Publication number | Publication date |
|---|---|
| CN107493117A (en) | 2017-12-19 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN107493117B (en) | The two-dimentional joint acquisition method of direct expansion msk signal under a kind of high dynamic | |
| CN105790788B (en) | A kind of pseudo-code of direct expansion msk signal-Doppler's joint acquisition method | |
| CN106772455B (en) | A kind of GNSS anti-spoofing loop tracks methods based on Inertia information auxiliary with parameter Estimation | |
| CN110071738B (en) | Spread spectrum signal despreading and tracking method based on multi-pseudo code branch receiver | |
| CN105141340B (en) | The digital method of reseptance of DS msk signal | |
| CN101969321B (en) | FFT (Fast Fourier Transform) based large frequency offset secondary catching method of direct sequence spread spectrum system | |
| CN106998586B (en) | The synchronization acquiring method of wireless communication system in a kind of high dynamic environment | |
| CN109088838B (en) | Pseudo code-Doppler fast capturing method of direct sequence spread spectrum DPSK signal under high dynamic condition | |
| CN109412644B (en) | Doppler frequency estimation method for direct sequence spread spectrum MSK signal | |
| CN108880609B (en) | Pseudo code synchronization method based on burst spread spectrum signal | |
| CN108183879A (en) | A kind of pseudo-code subcarrier synchronization realizing method for Terahertz communication | |
| WO2018103186A1 (en) | Method and apparatus for receiving td-altboc signal | |
| CN107342960B (en) | Non-data-aided frequency offset estimation method suitable for amplitude phase shift keying | |
| CN109150235A (en) | Compressed sensing based multicycle direct expansion msk signal two dimension joint acquisition method | |
| CN110300079B (en) | MSK signal coherent demodulation method and system | |
| CN106209160B (en) | A kind of compressed sensing based direct expansion msk signal two dimension joint acquisition method | |
| CN107370705A (en) | FFT optimization method in the capture of high dynamic weakly continuous phase modulated signal | |
| CN108196274A (en) | Be applicable in BOC (n, n) signal without fuzziness catching method and device | |
| CN107872419A (en) | A kind of pseudo-code service bit Timing Synchronization implementation method for Terahertz communication | |
| CN107682294B (en) | FPGA-based phase ambiguity correction method for high-speed 16apsk signal | |
| CN113037671A (en) | Low-complexity efficient SOQPSK symbol timing and phase joint synchronization algorithm | |
| CN102833204A (en) | Frequency offset estimation implementation method | |
| CN103188067B (en) | A kind of chip clock frequency departure estimation error of spread spectrum system and the method for correction | |
| CN111082835A (en) | Pseudo code and Doppler combined capturing method of direct sequence spread spectrum signal under high dynamic condition | |
| CN109104215A (en) | A kind of Frequency Hopping Signal chip rate blind estimating method based on wavelet transformation |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant | ||
| CF01 | Termination of patent right due to non-payment of annual fee |
Granted publication date: 20190809 |