CN106787771A - A kind of controlled resonant converter - Google Patents
A kind of controlled resonant converter Download PDFInfo
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- CN106787771A CN106787771A CN201710113028.XA CN201710113028A CN106787771A CN 106787771 A CN106787771 A CN 106787771A CN 201710113028 A CN201710113028 A CN 201710113028A CN 106787771 A CN106787771 A CN 106787771A
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- drive signal
- resonant converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/01—Resonant DC/DC converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
- H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33573—Full-bridge at primary side of an isolation transformer
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The present invention relates to a kind of controlled resonant converter, including drive signal adjustment module and drive signal generation module；The drive signal adjustment module gathers the magnitude of voltage of the current direct current output of the controlled resonant converter, produces the first control signal and the second control signal according to the DC voltage value for being gathered and is transferred to the drive signal generation module；The drive signal generation module is sent to the parameter of the drive signal on the switching device of the switch element according to first control signal and the regulation of the second control signal, so as to control the dutycycle or the angle of flow and switching frequency of the switch element breaker in middle device so that the voltage value stabilization of the direct current output is in the range of setting；Wherein, the control of the first control signal dutycycle or the angle of flow, the second control signal controlling switch frequency.Implement a kind of controlled resonant converter of the invention, have the advantages that：It easily realizes that protection is controlled, zero passage switch is difficult failure, stresses of parts is small.
Description
Technical field
The present invention relates to field of power supplies, more specifically to a kind of controlled resonant converter.
Background technology
Resonance switch convertor（resonant converter）Main power circuit is main by switching device, fairing and
Resonant network etc. is constituted.Because resonance switch convertor works in no-voltage（ZVS）Switch or/and zero current（ZCS）Switch shape
State, has the advantages that switching frequency high, circuit small volume, power density are high.In the prior art, VFC（variable
frequency control）Strategy and fixed-frequency control（fixed frequency control）Strategy can apply to resonance and open
Close converter.In these control strategies, VFC strategy changes driving source by switching device（Usually voltage source）Frequency
Rate, changes each element impedance value of resonant network, and then reach the purpose of controlling transmission power with this；Fixed-frequency control strategy then passes through
Switching device changes driving source（Usually voltage source）Amplitude, and then reach the purpose of controlling transmission power.However, on the one hand
VFC strategy often results in that resonance switch convertor circulation energy is big, switching frequency becomes in width load, input application scenario wide
The problems such as changing low wide ranges, magnetic element utilization rate and difficult startup/protection control realization；Another aspect fixed-frequency control strategy exists
Such occasion also results in resonance switch convertor ZVT/Zero Current Switch fails, device voltage current stress is big etc.
Problem.Therefore, there is protection control realization difficulty using the resonance switch convertor of prior art, zero passage switch mistake easily occur
Effect, the defect such as stresses of parts is big.
The content of the invention
The technical problem to be solved in the present invention is, for prior art above-mentioned protection control realization it is difficult, easily go out
The big defect of existing zero passage switch failure, stresses of parts, there is provided a kind of easily to realize that protection control, zero passage switch are difficult failure, device
A kind of small controlled resonant converter of part stress.
The technical solution adopted for the present invention to solve the technical problems is：A kind of controlled resonant converter is constructed, including will input
DC voltage be converted to the switch element of square-wave pulse, the square-wave pulse is by resonant network, high frequency transformer and rectification
Turn into a direct current output for the magnitude of voltage of setting after unit, also produce mould including drive signal adjustment module and drive signal
Block；The drive signal adjustment module gathers the magnitude of voltage of the current direct current output of the controlled resonant converter, straight according to what is gathered
Stream magnitude of voltage produces the first control signal and the second control signal and is transferred to the drive signal generation module；It is described to drive letter
Number generation module is sent to the switching device of the switch element according to first control signal and the regulation of the second control signal
On drive signal parameter, so as to control the dutycycle or the angle of flow and switching frequency of the switch element breaker in middle device,
So that the voltage value stabilization of the direct current output is in the range of setting；Wherein, first control signal control dutycycle or
The angle of flow, the second control signal controlling switch frequency.
Further, the dutycycle or the angle of flow after the first control signal regulation adjust mould with the drive signal
Result after the VD and the difference of reference voltage that block is collected amplify through error is directly proportional；The second control letter
Number there is linear relationship between first drive signal.
Further, first control signal meets following linear relationship with second control signal：
v δ+ V k v fs =V f
Wherein, first control signal isv δ, second control signal bev fs,V k、V fIt is by the controlled resonant converter
Constant that design parameter is determined, more than zero.
Further, under the regulation of first control signal and the second control signal, the drive signal regulation
The frequency and dutycycle or the angle of flow of the drive signal of module output are mutually corresponded to, when the dutycycle or the angle of flow of the drive signal
During for a setting value, its frequency is another setting value.
Further, the drive signal adjustment module includes voltage sample module, error amplification module and linear coupling
Matched moulds block；Wherein, the voltage sample module is sampled by DC output end, obtains sampled voltage and export to amplify to the error
Module；The sampled voltage and reference voltage are taken its difference and difference to obtaining and carry out ratio product by the error amplification module
Error voltage is obtained after point；The linear coupling module obtains error voltage, after carrying out computing with the voltage for setting respectively
First control signal is produced with second control signal；First control signal is conveyed with second control signal
To the drive signal generation module.
Further, the drive signal generation module includes waveform generation module, comparison module and drive module；Its
In, the waveform generation module adjusts internal controlled current source according to second control signal, produce that peak value is constant, frequency with
The triangular wave that second control signal is directly proportional；Meanwhile, also the peak value moment in the triangular wave produces one with the triangle
The narrow pulse sequence and is transported to the drive module by crest value with the narrow pulse sequence of frequency；The comparison module compares institute
The first control signal and the triangular wave are stated, and comparative result is delivered into the drive module；On two of the drive module
Rise and detect the narrow pulse sequence rising edge and the comparative result rising edge time respectively along triggers circuit, and respectively described
Rising edge time overturns the output level of the rising edge triggers circuit, the output level or described of the rising edge triggers circuit
The output level of rising edge triggers circuit is formed by being respectively outputted to after logic inverter in the control end of different switching devices
The drive signal of the controlled resonant converter switch element.
Further, the linear coupling module includes the first subtracter, the second subtracter, multiplier and amplitude limit electricity
Road；Error voltage is connected to an input of first subtracter, and another input input of first subtracter sets
Fixed first voltage, the output end of first subtracter is respectively outputted to one input of the comparator by amplitude limiter circuit
With an input of the multiplier；The second voltage of another input connection setting of the multiplier, the multiplier
Output end is connected with an input of second subtracter；The of another input of second subtracter and setting
Three voltages are connected, and the output end of second subtracter is connected to the input of the waveform generation module；The error voltage
With the negative input end that the output end of the multiplier is connected to first subtracter and the second subtracter.
Further, the first voltage, second voltage and tertiary voltage are positive voltage；Wherein, first voltage is big
The small minimum duty cycle or the angle of flow for determining the controlled resonant converter, the tertiary voltage size determines the resonant transformation
The maximum switching frequency of device.
Further, the switch element includes full-bridge or half-bridge structure, and the resonant network includes and the switch
Series resonant network, series resonant network, LCC or LLC resonant networks that unit is adapted.
Further, the rectification unit includes diode rectification, times stream rectification, full-wave rectification or synchronous rectification electricity
Road.
Implement a kind of controlled resonant converter of the invention, have the advantages that：Due to being missed obtained from output sampling
Potential difference, the of with linear relationship, regulation drive signal dutycycle or the angle of flow and frequency is produced using the error voltage
One control signal and the second control signal, by unit or module to producing above-mentioned first control signal and the second control signal
Parameter setting, it would be desirable to regulated quantity be distributed to the dutycycle or the angle of flow and frequency of drive signal up so that the two product
The effect of raw superposition, so as to realize being realized by less regulated quantity the effect of larger modulation range.Therefore, its easy realization
Protection is controlled, zero passage switch is difficult failure, stresses of parts is small.
Brief description of the drawings
Fig. 1 is a kind of structural representation of controlled resonant converter embodiment of the invention；
Fig. 2 is the structural representation of drive signal adjustment module in the embodiment；
Fig. 3 is the structural representation of drive signal generation module in the embodiment；
Fig. 4 is the structural representation of linear coupling module in the embodiment；
Fig. 5 be it is a kind of in the embodiment in the case of controlled resonant converter circuit diagram；
Fig. 6 is the waveform diagram of each key node in Fig. 5.
Specific embodiment
Below in conjunction with accompanying drawing, embodiments of the present invention is further illustrated.
As shown in figure 1, in a kind of controlled resonant converter embodiment of the invention, the controlled resonant converter includes straight by what is be input into
Stream voltage conversion is the switch element of square-wave pulse, and the square-wave pulse is by resonant network, high frequency transformer and rectification unit
Turn into a direct current output for the magnitude of voltage of setting afterwards, also including drive signal adjustment module and drive signal generation module；Institute
The magnitude of voltage that drive signal adjustment module gathers the current direct current output of the controlled resonant converter is stated, according to the DC voltage for being gathered
Value produces the first control signal and the second control signal and is transferred to the drive signal generation module；The drive signal is produced
Module is sent to the drive on the switching device of the switch element according to first control signal and the regulation of the second control signal
The parameter of dynamic signal, so as to control the dutycycle or the angle of flow and switching frequency of the switch element breaker in middle device so that institute
The voltage value stabilization of direct current output is stated in the range of setting；Wherein, the control of the first control signal dutycycle or the angle of flow,
The second control signal controlling switch frequency.In other words, in the present embodiment, the drive signal in the controlled resonant converter is adjusted
Section module obtains current VD by the DC output end of the controlled resonant converter, is carried out according to the current voltage for obtaining
Computing or conversion, obtain the first control signal and the second control signal, and first control signal and the second control signal are transported to
Drive signal generation module, the drive signal generation module according to input above-mentioned first control signal and the second control signal,
Switching drive signal is produced, and is exported to switch element, the switch of controlling switch unit breaker in middle device；Above-mentioned current voltage
When larger, the switching drive signal of output to switching device causes that the dutycycle or the angle of flow of switching device reduce, and makes switch
The switching frequency of device reduces, so that VD reduction；When above-mentioned current voltage is smaller, output to derailing switch
The switching drive signal of part causes that the dutycycle or the angle of flow of switching device increase, and increases the switching frequency of switching device,
So that VD is raised.So so that the output DC voltage of above-mentioned controlled resonant converter maintains the defeated of setting
Go out voltage annex.In the present embodiment, above-mentioned output to the drive signal of switching device be with obtain VD change
Change and change, specifically, the change of the DC voltage of output causes above-mentioned first control signal and the second control signal to become
Change, and the first control signal causes the dutycycle of controlling switch device in drive signal or the Parameters variation of the angle of flow, for example, driving
The pulse width of dynamic signal；And the second control signal causes that the parameter of the switching frequency of controlling switch device in drive signal becomes
Change, for example, the frequency of drive signal.In the present embodiment, above-mentioned dutycycle or the angle of flow are changed simultaneously with frequency, also
It is to export DC voltage come stabilization by changing dutycycle or the angle of flow and switching frequency simultaneously in the present embodiment to be.
It is noted that in the present embodiment, the definition of dutycycle or the angle of flow is and dutycycle of the prior art
Or the definition identical of the angle of flow.The two actually same parameter, refers to switch periods breaker in middle break-over of device time
Length, traditionally when switch element is full-bridge circuit, the commonly referred to angle of flow, and be the situation of half-bridge circuit in switch element
Under, commonly referred to dutycycle.For switching drive signal, the two both corresponds to the pulse width of drive signal.
Further, the dutycycle or the angle of flow after the first control signal regulation adjust mould with the drive signal
Result after the VD and the difference of reference voltage that block is collected amplify through error is directly proportional；The second control letter
Number there is linear relationship between first drive signal.
In the present embodiment, if first control signal isv δ, second control signal bev fs, then described first
Control signal meets following linear relationship with second control signal：v δ+ V k v fs =V f；Wherein,V k、V fIt is normal more than zero
Number, its value is determined by the parameter designing process of the controlled resonant converter.In fact, above-mentioned linear relationship is by the present embodiment
What specific circuit structure was determined, above-mentioned constant is also embodied in specific circuit parameter.In other words, in the present embodiment, by
In the restriction of physical circuit and electrical parameter so that be presented above-mentioned linear between above-mentioned first control signal and the second control signal
Relation.Simultaneously as there is above-mentioned linear relationship, by the selection and setting of circuit parameter, in first control signal and
Under the regulation of the second control signal, the frequency and dutycycle or the angle of flow of the drive signal of the drive signal adjustment module output
It is mutually corresponding, it is possible to achieve one-to-one relation, i.e., when the dutycycle or the angle of flow of the drive signal are a setting value,
Its frequency is another setting value；When drive signal has a dutycycle for setting or the angle of flow, the drive signal is same
When with one setting frequency.So so that for whole controlled resonant converter, can either comprehensive dutycycle or the angle of flow
Regulation, the benefit of switching frequency regulation, it is also possible to the adverse consequences for avoiding two kinds of regulative modes from bringing, i.e., by less regulation
Measure larger adjustment scope.
Fig. 2 shows drive signal adjustment module more specifically structure in the present embodiment.In fig. 2, the drive signal
Adjustment module includes voltage sample module, error amplification module and linear coupling module；Wherein, the voltage sample module is by straight
Stream output end sampling, obtains sampled voltage and exports to the error amplification module；The error amplification module is by the sampling
Voltage and reference voltage take its difference and obtain error voltage after the difference to obtaining carries out proportional integral；The linear coupling mould
Block obtains error voltage, produces first control signal respectively after carrying out computing with the voltage for setting with the described second control
Signal processed；First control signal is transported to the drive signal generation module with second control signal.
Fig. 3 shows the concrete structure of drive signal generation module in the present embodiment.In figure 3, the drive signal is produced
Raw module includes waveform generation module, comparison module and drive module；Wherein, the waveform generation module is according to the described second control
Signal Regulation inside processed controlled current source, the triangular wave that generation peak value is constant, frequency is directly proportional to second control signal；Together
When, also generation one is same with the peak value of the triangular wave frequently with the narrow pulse sequence of phase, and the narrow pulse sequence is transported into institute
State drive module；That is, for above-mentioned triangular wave, when each its peak value occurs, all producing a burst pulse；
So so that the frequency that above-mentioned triangle crest value occurs is identical with the frequency that the burst pulse occurs；Meanwhile, the triangle crest value
Rising edge with should pulse rising edge alignment；Comparison module first control signal and the triangular wave, and
Comparative result is delivered into the drive module；The drive module includes two parallel rising edge triggers circuits and logic inverter,
The input of the two rising edge triggers circuits is connected with first control signal and the second control signal respectively, its output end
Directly or by logic inverter output to the control end of the different switching device in switch element, the switching device is controlled
Switch on and off, form above-mentioned drive signal or switching drive signal；In said structure, two rising edge triggers circuits point
The narrow pulse sequence rising edge and the comparative result rising edge time are not detected, and respectively in rising edge time upset
The output level of the rising edge triggers circuit, described two output levels drive directly or through conduct after logic inverter respectively
Signal is transported to the control end of different switching devices in switch element.Wherein, a rising edge triggers circuit is respectively by one
Directly the drive level and a drive level by not gate of output are transferred on two adjacent bridge arms.
Fig. 4 shows a kind of concrete structure of linear coupling module in the present embodiment, and the linear coupling module includes first
Subtracter, the second subtracter, multiplier and amplitude limiter circuit；Error voltage is connected to first subtracter and multiplier
One input, the first voltage of another input input setting of first subtracter, the output of first subtracter
End is exported to described comparator one end by amplitude limiter circuit；The second voltage of another input connection setting of the multiplier,
The multiplier outputs are connected with an input of second subtracter；Another input of second subtracter
Tertiary voltage with setting is connected, and the output end of second subtracter is connected to the input of the waveform generation module.Its
In, the output end of the error voltage and the multiplier is connected to the negative defeated of first subtracter and the second subtracter
Enter end.In the present embodiment, the first voltage, second voltage and tertiary voltage are previously set, and the foundation of its setting is
The circuit parameter of controlled resonant converter, for example, turn ratio of the primary and secondary of output voltage, output current and high frequency transformer etc.
Deng.Meanwhile, the first voltage, second voltage and tertiary voltage determine first control signal with the described second control letter
Number linear relationship.
By the selection of said structure and parameter, in the present embodiment, in first control signal and the second control letter
Number regulation under, the frequency and dutycycle or the angle of flow of the drive signal of drive signal adjustment module output are mutually corresponded to,
When the dutycycle or the angle of flow of the drive signal are a setting value, its frequency is another setting value.For example, in this reality
Apply in example in the case of one kind, each dutycycle of the drive waveforms after regulation can be caused to have and a kind of switch is uniquely corresponded to
Frequency, the switching frequency of such as 90% dutycycle correspondence 100kHz, 50% switching frequency of dutycycle correspondence 110kHz etc..
In general, in the present embodiment, compared with existing self-sustained phase shift control, the dutycycle of drive waveforms
Or it is linear between the angle of flow and switching frequency, simplify the design of control circuit；And two control dimensions are interrelated,
Enhance the stability of system；Meanwhile, the technical scheme in the present embodiment compared with existing frequency conversion control technique, open by its resonance
Converter is closed when input voltage or power output change, the excursion of switching frequency is narrower, be conducive to improving humorous
Shake the utilization rate of magnetic element in switch converters, and simplify the design process of resonance switch convertor median filter, resonance
Switch converters startup/defencive function is more easy to realize.
Additionally, technical scheme is compared with existing fixed-frequency control technology in the present embodiment, resonance switch convertor is defeated in width
Enter voltage or load application scenario wide, no-voltage or the operation of zero-current soft switch state can be remained.And with existing frequency conversion
When control technology and fixed-frequency control technology are compared, using the resonance switch convertor of technical scheme in the present embodiment in width input electricity
Pressure or load application scenario wide, have smaller circulation energy in running, improve unit efficiency.
Fig. 5 and Fig. 6 show it is a kind of in the present embodiment in the case of controlled resonant converter circuit diagram and each point in the circuit
Oscillogram.In fig. 5 and fig., application circuit of the technical scheme in the present embodiment in LCC controlled resonant converters is given.
For LCC controlled resonant converters, power output（P o）Reduce or input voltage（V in）During rising, the angle of flow need to be reduced（δ）Or increase
Switching frequency（f s）To maintain output voltage constant；Power output（P o）Raise or input voltage（V in）During reduction, need to increase and lead
Current flow angle（δ）Or reduce switching frequency（f s）To maintain output voltage constant.
During specific implementation, Fig. 5 is referred to, Fig. 5 shows the LCC resonant transformations of a kind of quasi- fixed-frequency control in the present embodiment
Device, including power supply 1, switching network 2, resonant network and transformer 3, rectifying part 4, filter network 5, load 6 and control circuit
（The control circuit includes foregoing drive signal generation module and drive signal adjustment module）.It is power supply 1, switching network 2, humorous
Vibrating network and transformer 3, rectifying part 4, filter network 5 and load 6 are sequentially connected.Power supply 1 is dc sourceV in；Switching network
2 is full bridge switching circuit, wherein S1 and S2 composition leading-bridge, S3 and S4 composition lagging legs；Resonant network and transformer 3 are wrapped
Include series resonance inductorL r, series resonant capacitanceC s, parallel resonance electric capacityC p, transformer TrThe turn ratio is n:1；Rectifying part 4 is for again
Stream rectification circuit；Filter network 4 is LC filter circuits；Load 6 is resistive loadR L。
Control circuit includes voltage sample module 8, error amplifier 7, reference voltage 11, linear coupling module 12, waveform
Generation module 21, comparison module 20 and drive module 30；Wherein, waveform generation module 21, comparison module 20 and drive module 30
Constitute above-mentioned drive signal generation module, remainder composition drive signal adjustment module.Wherein linear coupling module 12 is by producing
Raw first voltageV dFirst voltage source 13, the first subtracter 14, the second subtracter 16, multiplier 15, produce second voltageV k's
The second voltage source, generation tertiary voltageV FTertiary voltage source 18 and amplitude limiter circuit 19 constitute.
In the present embodiment, specific work process and the principle of foregoing circuit are：The detection of voltage sample module 8 output voltage is simultaneously
Error signal is produced by error amplifier 7v e；Linear coupling module 12 is receivedv e, switching frequency control signal is produced respectivelyv fs
（Second control signal）And conduction angle control signalv δ（First control signal）；Waveform generating module 21 is receivedv fs, produce respectively
Triangular wavev sawAnd pulse signalv p；Comparison module 20 is receivedv sawWithv δ, produce comparative resultv cmp；Drive module 30 is receivedv cmp
Withv p, switching drive signal is produced to control main power circuit switching device to work.
Fig. 5 is the oscillogram of each key point of the present embodiment foregoing circuit.Its transverse axis is the time（ms）, in fig. 4, press
Order from top to bottom, first longitudinal axis of waveform is full-bridge circuit output voltagev AB（V）And resonance currenti r（A）；Second
The waveform longitudinal axis is triangular carrierv sawAnd conduction angle control signalv δ；3rd waveform and the 4th waveform are respectively switching tubes 1
（S1）With switching tube 4（S4）Gate electrode drive signals.Waveform in Fig. 4 is obtained under the following conditions：Input voltageV in=
300V, output voltageV o=48V, power outputP o=1500W, resonant inductanceL r=105.66 μ H, series resonant capacitance and parallel connection are humorous
Shake electric capacityC s=C p=59.19nF, transformer turns ration=2.7。
Additionally, in the present embodiment, above-mentioned switch element can include full-bridge or half-bridge structure, and the resonant network bag
Include series resonant network, series resonant network, LCC the or LLC resonant networks being adapted with the switch element.The rectification list
Unit includes diode rectification, times stream rectification, full-wave rectification or circuit of synchronous rectification.That is, in either case, it is whole
Stream filter unit can be using times stream rectification of various structures or species；Circuit of synchronous rectification can also be used, for example, using
The full bridge rectifier of diode rectification, the full bridge rectifier using synchronous rectification, the full-wave rectification using diode rectification
Circuit or the full-wave rectifying circuit using synchronous rectification.
In the present embodiment, above-mentioned technical proposal is except the LCC controlled resonant converters that can be used in the present embodiment, can be with
For the two element controlled resonant converter such as series resonance, parallel resonance, or the multi-element resonant converter such as LLC, LCC.
Embodiment described above only expresses several embodiments of the invention, and its description is more specific and detailed, but simultaneously
Therefore the limitation to the scope of the claims of the present invention can not be interpreted as.It should be pointed out that for one of ordinary skill in the art
For, without departing from the inventive concept of the premise, various modifications and improvements can be made, these belong to guarantor of the invention
Shield scope.Therefore, the protection domain of patent of the present invention should be determined by the appended claims.
Claims (10)
1. a kind of controlled resonant converter, including the DC voltage of input is converted to the switch element of square-wave pulse, the square wave arteries and veins
Rush by turning into a direct current output for the magnitude of voltage of setting after resonant network, high frequency transformer and rectification unit, its feature exists
In also including drive signal adjustment module and drive signal generation module；The drive signal adjustment module gathers resonance change
The magnitude of voltage of the current direct current output of parallel operation, the first control signal and the second control letter are produced according to the DC voltage value for being gathered
Number and be transferred to the drive signal generation module；The drive signal generation module is according to first control signal and second
Control signal regulation is sent to the parameter of the drive signal on the switching device of the switch element, so as to control the switch single
The dutycycle or the angle of flow and switching frequency of first breaker in middle device so that model of the voltage value stabilization of the direct current output in setting
In enclosing；Wherein, the control of the first control signal dutycycle or the angle of flow, the second control signal controlling switch frequency.
2. controlled resonant converter according to claim 1, it is characterised in that the dutycycle after the first control signal regulation
Or the difference of the VD that is collected with the drive signal adjustment module of the angle of flow and reference voltage is amplified through error
Result afterwards is directly proportional；There is linear relationship between second control signal and first drive signal.
3. controlled resonant converter according to claim 2, it is characterised in that first control signal and the described second control
Signal meets following linear relationship：
v δ+V k v fs =V f
Wherein, first control signal isv δ, second control signal bev fs,V k、V fIt is setting by the controlled resonant converter
Constant that meter parameter is determined, more than zero.
4. controlled resonant converter according to claim 3, it is characterised in that in first control signal and the second control letter
Number regulation under, the frequency and dutycycle or the angle of flow of the drive signal of drive signal adjustment module output are mutually corresponded to,
When the dutycycle or the angle of flow of the drive signal are a setting value, its frequency is another setting value.
5. controlled resonant converter according to claim 4, it is characterised in that the drive signal adjustment module is adopted including voltage
Egf block, error amplification module and linear coupling module；Wherein, the voltage sample module is sampled by DC output end, is obtained
Sampled voltage is simultaneously exported to the error amplification module；The sampled voltage and reference voltage are taken it by the error amplification module
Difference and the difference to obtaining obtain error voltage after carrying out proportional integral；The linear coupling module obtains error voltage, warp
Cross after carrying out computing with the voltage for setting and produce first control signal respectively with second control signal；First control
Signal processed is transported to the drive signal generation module with second control signal.
6. controlled resonant converter according to claim 5, it is characterised in that the drive signal generation module includes that waveform is produced
Raw module, comparison module and drive module；Wherein, the waveform generation module is received according to second control signal regulation inside
Control current source, the triangular wave that generation peak value is constant, frequency is directly proportional to second control signal；Meanwhile, also in the triangle
The peak value moment of ripple produce one with the triangle crest value with frequency narrow pulse sequence, and described in the narrow pulse sequence is transported to
Drive module；Comparison module first control signal and the triangular wave, and comparative result is delivered into the drive
Dynamic model block；Two rising edge triggers circuits of the drive module detect that the narrow pulse sequence rising edge compares with described respectively
As a result rising edge time, and overturn the output level of the rising edge triggers circuit in the rising edge time respectively, it is described on
Rise along the output level of triggers circuit or the output level of the rising edge triggers circuit by being respectively outputted to after logic inverter
In the control end of different switching devices, the drive signal of the controlled resonant converter switch element is formed.
7. controlled resonant converter according to claim 6, it is characterised in that the linear coupling module includes the first subtraction
Device, the second subtracter, multiplier and amplitude limiter circuit；Error voltage is connected to an input of first subtracter, described
The first voltage of another input input setting of the first subtracter, the output end of first subtracter is by amplitude limiter circuit point
An input of one input of the comparator and the multiplier Shu Chu not arrived；Another input of the multiplier connects
The second voltage of setting is connect, the multiplier outputs are connected with an input of second subtracter；Described second subtracts
Another input of musical instruments used in a Buddhist or Taoist mass is connected with the tertiary voltage of setting, and the output end of second subtracter is connected to the waveform and produces
The input of raw module；The output end of the error voltage and the multiplier is connected to first subtracter and second
The negative input end of subtracter.
8. controlled resonant converter according to claim 7, it is characterised in that the first voltage, second voltage and the 3rd electricity
Pressure is positive voltage；Wherein, first voltage size determines the minimum duty cycle or the angle of flow of the controlled resonant converter, described
Three voltage swings determine the maximum switching frequency of the controlled resonant converter.
9. the controlled resonant converter according to claim 1-8 any one, it is characterised in that the switch element includes full-bridge
Or half-bridge structure, the resonant network include be adapted with the switch element series resonant network, series resonant network,
LCC or LLC resonant networks.
10. controlled resonant converter according to claim 9, it is characterised in that the rectification unit include diode rectification, times
The circuit of synchronous rectification of stream rectification, full-wave rectification or more circuit form.
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| CN201710113028.XA CN106787771A (en) | 2017-02-28 | 2017-02-28 | A kind of controlled resonant converter |
| PCT/CN2018/077436 WO2018157796A1 (en) | 2017-02-28 | 2018-02-27 | Resonant converter |
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| CN201710113028.XA CN106787771A (en) | 2017-02-28 | 2017-02-28 | A kind of controlled resonant converter |
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Cited By (4)
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| WO2018157796A1 (en) * | 2017-02-28 | 2018-09-07 | 深圳市皓文电子有限公司 | Resonant converter |
| WO2019113784A1 (en) * | 2017-12-12 | 2019-06-20 | Astec International Limited | Resonant converters power supplies and control methods for reducing unbalanced currents in resonant converter power supplies |
| CN112003455A (en) * | 2019-05-27 | 2020-11-27 | 台达电子工业股份有限公司 | Power supply and control method thereof |
| CN113394981A (en) * | 2020-06-10 | 2021-09-14 | 成都芯源***有限公司 | Resonant converter with automatic frequency adjustment and control method thereof |
Families Citing this family (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN115494377B (en) * | 2022-06-02 | 2024-07-05 | 中国南方电网有限责任公司超高压输电公司检修试验中心 | Method and device for realizing boost injection type harmonic current source |
| CN117411322A (en) * | 2023-09-26 | 2024-01-16 | 深圳市佳合丰新能源科技有限公司 | Automatic control method for staggered phases of asymmetric resonant half-bridge |
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| CN101064476A (en) * | 2006-04-30 | 2007-10-31 | 艾默生网络能源***有限公司 | Resonant DC/DC converter and its control method |
| CN102025266A (en) * | 2009-06-18 | 2011-04-20 | 力博特公司 | Numeric control method for liquid level control (LLC) resonant conversion circuit |
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| WO2018157796A1 (en) * | 2017-02-28 | 2018-09-07 | 深圳市皓文电子有限公司 | Resonant converter |
| WO2019113784A1 (en) * | 2017-12-12 | 2019-06-20 | Astec International Limited | Resonant converters power supplies and control methods for reducing unbalanced currents in resonant converter power supplies |
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| CN112003455B (en) * | 2019-05-27 | 2022-04-29 | 台达电子工业股份有限公司 | Power supply and control method thereof |
| CN113394981A (en) * | 2020-06-10 | 2021-09-14 | 成都芯源***有限公司 | Resonant converter with automatic frequency adjustment and control method thereof |
| CN113394981B (en) * | 2020-06-10 | 2022-09-06 | 成都芯源***有限公司 | Resonant converter with automatic frequency adjustment and control method thereof |
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| WO2018157796A1 (en) | 2018-09-07 |
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