CN105785295B - A kind of gradient power amplifier based on multistage coupling inductance optimization design - Google Patents
A kind of gradient power amplifier based on multistage coupling inductance optimization design Download PDFInfo
- Publication number
- CN105785295B CN105785295B CN201610246657.5A CN201610246657A CN105785295B CN 105785295 B CN105785295 B CN 105785295B CN 201610246657 A CN201610246657 A CN 201610246657A CN 105785295 B CN105785295 B CN 105785295B
- Authority
- CN
- China
- Prior art keywords
- coupling inductance
- group
- bridge
- circuit
- bridge circuit
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
Classifications
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
- G01R33/00—Arrangements or instruments for measuring magnetic variables
- G01R33/20—Arrangements or instruments for measuring magnetic variables involving magnetic resonance
- G01R33/28—Details of apparatus provided for in groups G01R33/44 - G01R33/64
- G01R33/38—Systems for generation, homogenisation or stabilisation of the main or gradient magnetic field
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
Landscapes
- Physics & Mathematics (AREA)
- Condensed Matter Physics & Semiconductors (AREA)
- General Physics & Mathematics (AREA)
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Amplifiers (AREA)
Abstract
The present invention relates to a kind of gradient power amplifier based on multistage coupling inductance optimization design, including pwm control circuit, the power-varying circuitry being connected with pwm control circuit, the low-pass filter circuit being connected with power-varying circuitry and load.Low-pass filter circuit includes coupling inductance part and low-pass filtering capacitive part, and coupling inductance part is connected between the power-varying circuitry and the low-pass filtering capacitive part, and coupling inductance part includes at least two-stage coupling inductance.Using multistage coupling inductance in the gradient power amplifier based on multistage coupling inductance optimization design, the capability of fast response of gradient power amplifier is utmostly improved, while low output current ripple is furthermore achieved.
Description
Technical field
The present invention relates to a kind of gradient power amplifiers in magnetic resonance imaging system, and in particular to one kind is based on more
The gradient power amplifier of grade coupling inductance optimization design.
Background technique
With the continuous improvement of medical level, magnetic resonance imaging device has been used widely.Gradient power amplification
Device is one of core component of magnetic resonance imaging system, and with the continuous improvement of mr imaging technique, system is to gradient power amplifier
Performance more stringent requirements are proposed.United States Patent (USP) " the pulse-width modulated of Patent No. US005070292
Circuit for driving a load ", wherein a kind of similar topological structure for MRI gradient power amplifier is disclosed, it should
Common filter inductance has been changed to coupling inductance in patent, to advantageously reduce the ripple of output electric current, has improved system
Bandwidth.Application publication number is the Chinese invention patent application of CN104950273A (application No. is 201410120308.X) simultaneously
" a kind of gradient amplifier using coupling inductance output filtering ", wherein equally using coupling inductance output filtering, to meet ladder
Spend the imaging system requirement of the quick output response of electric current and low output ripple electric current.But during this kind of gradient amplifier is only applicable to
In low-voltage power supply environment, it is not suitable in the magnetic resonance imaging system for having higher voltage demand.The magnetic resonance gradient of high voltage supply
System needs fast-changing high current, ultralow current ripples and accurate current control, in order to reach quick electric current
Variation, needs high pressure, high-current semiconductor.The higher device of voltage generally has higher switching loss, and limiting may reach
The maximum switching frequency arrived enables high-voltage inverter to be switched with sufficiently high frequency to tie up under high switching loss
The time interval for holding accurate current waveform is also restrained.Publication No. CN1247319A's (application No. is 99118609.5)
Chinese invention patent application " switching amplifier for generating the continuous free wave shape for MRI coil ", disclosed in
Switching amplifier uses two isolated DC power bus, generates the gradient power amplifier of high-voltage great-current.This is controlled in actual use
Circuit processed is complicated, and at high cost.
Summary of the invention
First technical problem to be solved by this invention is to provide one kind for the above-mentioned prior art can further drop
Low output current ripple, the gradient power amplifier of lifting system quick response.
Second technical problem to be solved by this invention is to provide a kind of both facilitate for the above-mentioned prior art to apply
In high pressure working environment, and facilitate the gradient power amplifier applied in mesolow working environment.
The present invention solves the above problems used technical solution are as follows: a kind of ladder based on multistage coupling inductance optimization design
Power amplifier is spent, including
Pwm control circuit is connected, for handling respectively with the feedback end of gradient control signal output and output electric current
Gradient controls signal and exports the feedback signal of electric current, to export pwm control signal according to control logic；
Power-varying circuitry, input terminal is connected with the pwm control signal output end of the pwm control circuit, according to PWM
It controls signal and generates high-voltage pulse；
Low-pass filter circuit, input terminal are connected with the power-varying circuitry, generate high-voltage signal output for filtering
To load, the conversion of high-voltage pulse to load end voltage difference of the two ends is completed, so that generating expected electric current in load；
It is characterized by:
The low-pass filter circuit includes coupling inductance part and low-pass filtering capacitive part, and the coupling inductance part connects
It connects between the power-varying circuitry and the low-pass filtering capacitive part, the coupling inductance part includes at least two-stage coupling
Close inductance.
Preferably, the power-varying circuitry includes first group of H-bridge circuit, second group of H-bridge circuit, third group H-bridge circuit
With the 4th group of H-bridge circuit, first group of H-bridge circuit, second group of H-bridge circuit, third group H-bridge circuit and the 4th group of H-bridge circuit work
Corresponding PWM timing is respectively 0 degree, 180 degree, 90 degree and 270 degree；
The coupling inductance part includes first order coupling inductance and second level coupling inductance；
First order coupling inductance includes the first coupling inductance, the second coupling inductance, third coupling inductance and the 4th coupling electricity
Sense；
Second level coupling inductance includes the 5th coupling inductance and the 6th coupling inductance；
The first half-bridge output midpoint of first group of H-bridge circuit and the first half-bridge output midpoint difference of second group of H-bridge circuit
It is connected to two input terminals of the first coupling inductance；
The first half-bridge output midpoint of third group H-bridge circuit and the first half-bridge output midpoint difference of the 4th group of H-bridge circuit
It is connected to two input terminals of the second coupling inductance；
The second half-bridge output midpoint of first group of H-bridge circuit and the second half-bridge output midpoint difference of second group of H-bridge circuit
It is connected to two input terminals of third coupling inductance；
The second half-bridge output midpoint of third group H-bridge circuit and the second half-bridge output midpoint difference of the 4th group of H-bridge circuit
It is connected to two input terminals of the 4th coupling inductance；
The output end of first coupling inductance and the output end of the second coupling inductance are respectively connected to the two of the 5th coupling inductance
The output end of a input terminal, the output end of third coupling inductance and the 4th coupling inductance is respectively connected to the two of the 6th coupling inductance
A input terminal；
The output end of 5th coupling inductance and the output end of the 6th inductance are connected to the low-pass filtering capacitive part
On.
The low-pass filtering capacitive part includes one group or multiple groups high-frequency absorption circuit.
Selectively, the high-frequency absorption circuit is that RC absorbing circuit, C absorbing circuit, LRC absorbing circuit or LRCD absorb
Circuit.
In order to facilitate the gradient power amplifier operation in mesolow working environment or high pressure working environment, the H
A switching tube is connected in every switching branches of bridge circuit or is connected in parallel at least two switching tubes or is at least connected
Connect two switching tubes.
Compared with the prior art, the advantages of the present invention are as follows: it should the gradient power based on multistage coupling inductance optimization design
Using multistage coupling inductance in amplifier, the capability of fast response of gradient power amplifier is utmostly improved, while into one
Step realizes low output current ripple.Furthermore it is somebody's turn to do the topology of the gradient power amplifier based on multistage coupling inductance optimization design
Structure can greatly improve performance indicator of the gradient power amplifier in High Voltage Power Supply, better meet 1.5T and
Requirement of the 3.0T MRI system to high gradient switching rate.
Detailed description of the invention
Fig. 1 is the structural block diagram of gradient power amplifier in the embodiment of the present invention.
Fig. 2 is the topology diagram of gradient power amplifier in the embodiment of the present invention.
Fig. 3 is the equivalent circuit diagram of the first coupling inductance in the embodiment of the present invention.
Fig. 4 is that first group of first half-bridge of H-bridge circuit exports the first of midpoint and second group of H-bridge circuit in the embodiment of the present invention
The voltage oscillogram at half-bridge output midpoint.
Specific embodiment
The present invention will be described in further detail below with reference to the embodiments of the drawings.
As depicted in figs. 1 and 2, the gradient power amplifier based on multistage coupling inductance optimization design in the present embodiment,
Including pwm control circuit 1, power-varying circuitry 2 and low-pass filter circuit 3.
Wherein general pwm control circuit 1 can be used in pwm control circuit 1, which controls with gradient respectively
Signal output end is connected with the feedback end of output electric current, for handling gradient control signal and exporting the feedback signal of electric current,
To export pwm control signal according to control logic.
Power-varying circuitry 2 in the present embodiment includes first group of H-bridge circuit 2A, second group of H-bridge circuit 2B, third group H
Bridge circuit 2C and the 4th group of H-bridge circuit 2D, first group of H-bridge circuit 2A, second group of H-bridge circuit 2B, third group H-bridge circuit 2C and
The corresponding PWM timing of four groups of H-bridge circuit 2D work is respectively 0 degree, 180 degree, 90 degree and 270 degree.
It wherein include switching device K11, K12, K13 and K14 in first group of H-bridge circuit 2A, in second group of H-bridge circuit 2B
Include switching device K21, K22, K23 and K24, include in third group H-bridge circuit 2C switching device K31, K32, K33 and
It include switching device K41, K42, K43 and K44 in K34, the 4th group of H-bridge circuit 2D.Switching device point in every group of H-bridge circuit
It is not connected with the pwm control signal output end of pwm control circuit 1, generates high-voltage pulse under the control of pwm control signal.
In order to facilitate the gradient power amplifier operation in high pressure working environment, in every switching branches of H-bridge circuit
Two switching tubes are at least connected in series, i.e., set each switching device to the switching tube of two series connections.In this way, the gradient
Power amplifier can be applied in higher voltage power supply environment, facilitate and meet 1.5T and 3.0T MRI system to height
The requirement of gradient switching rate.
The input terminal of low-pass filter circuit 3 is connected with power-varying circuitry 2, and low-pass filter circuit 3 includes coupling inductance
Part 31 and low-pass filtering capacitive part 32, coupling inductance part 31 are connected to power-varying circuitry 2 and low-pass filtering capacitance part
Divide between 32, which can work and exist according to the sequential logic of the high-voltage pulse from power-varying circuitry 2
Pressure stabilizing state or instantaneous state can satisfy the requirement of the low output ripple of electric current when work is in pressure stabilizing state, and work as work
In instantaneous state, then the requirement of fast-response is able to satisfy.
Low-pass filtering capacitive part 32 couples the inductance formed with coupling inductance part 31 and constitutes low-pass filter circuit 3, energy
It is enough that the high-voltage signal generated after filtering is output to load, the conversion of high-voltage pulse to load end voltage difference of the two ends is completed, so that
Expected electric current is generated in load.
Coupling inductance part 31 in the present embodiment includes two-stage coupling inductance.I.e. coupling inductance part 31 includes the first order
Coupling inductance and second level coupling inductance.First order coupling inductance include the first coupling inductance 311A, the second coupling inductance 312A,
Third coupling inductance 313A and the 4th coupling inductance 314A.Second level coupling inductance includes the 5th coupling inductance 315B and the 6th coupling
Close inductance 316B.
The first half-bridge output midpoint of first group of H-bridge circuit 2A and the first half-bridge of second group of H-bridge circuit 2B export midpoint
Be respectively connected to two input terminals of the first coupling inductance 311A, i.e. the half-bridge that switching device K11 and switching device K14 are formed
Output midpoint is connected with an input terminal of the first coupling inductance 311A, and the half of switching device K21 and switching device K24 composition
The output midpoint of bridge is connected with another input terminal of the first coupling inductance 311A.
The first half-bridge output midpoint of third group H-bridge circuit 2C and the first half-bridge of the 4th group of H-bridge circuit 2D export midpoint
Be respectively connected to two input terminals of the second coupling inductance 312A, i.e. the half-bridge that switching device K31 and switching device K34 are formed
Output midpoint is connected with an input terminal of the second coupling inductance 312A, and the half of switching device K41 and switching device K44 composition
The output midpoint of bridge is connected with another input terminal of the second coupling inductance 312A.
The second half-bridge output midpoint of first group of H-bridge circuit 2A and the second half-bridge of second group of H-bridge circuit 2B export midpoint
Be respectively connected to two input terminals of third coupling inductance 313A, i.e. the half-bridge that switching device K12 and switching device K13 are formed
Output midpoint is connected with an input terminal of third coupling inductance 313A, and the half of switching device K22 and switching device K23 composition
The output midpoint of bridge is connected with another input terminal of third coupling inductance 313A.
The second half-bridge output midpoint of third group H-bridge circuit 2C and the second half-bridge of the 4th group of H-bridge circuit 2D export midpoint
Be respectively connected to two input terminals of the 4th coupling inductance 314A, i.e. the half-bridge that switching device K32 and switching device K33 are formed
Output midpoint is connected with an input terminal of the 4th coupling inductance 314A, and the half of switching device K42 and switching device K43 composition
The output midpoint of bridge is connected with another input terminal of the 4th coupling inductance 314A.
By taking the course of work of the first coupling inductance 311A in first order coupling inductance as an example, illustrate first order coupling inductance
The course of work, the second coupling inductance 312A, third coupling inductance 313A and the 4th coupling inductance 314A and the first coupling inductance
The course of work of 311A is identical, and difference is only that on working sequence.
H bridge conversion section is output to two high-voltage pulses of the first coupling inductance 311A input terminal, when the two high-tension pulses
When the duty ratio of punching is simultaneously greater than 50%, it may appear that switching device K11, K21 be closed at or switching device K13, K23 simultaneously
The case where closure, the coupling inductance of the first coupling inductance 311A is equivalent to low value inductance at this time, this low value inductance and low pass filtered
Wave capacitive part 32 forms one group of low-pass filtering, for meeting the requirement of higher current-rising-rate.When being output to the first coupling
When electromotive force between two high-voltage pulses of inductance 311A input terminal and the first coupling inductance 311A output end is opposite, coupling at this time
It closes inductance and low-pass filtering capacitive part 32 forms another group of low-pass filtering, the stabilization gradient for being used to form low ripple electric current is defeated
Out.
When the duty ratio of the work wave of switching device K11, K21 in H-bridge circuit is respectively 50%, corresponding derailing switch
The signal output waveform of part K13 and K23 respectively correspond with switching device K11 and K21 completely the same respectively.And switching device K11,
The signal output waveform phase difference 180 degree of K21.
Equivalent circuit Fig. 3 of first coupling inductance 311A, if the unilateral inductance Lp foot of the first coupling inductance 311A
Enough big, Lp is much larger than the equivalent leakage inductance Ls of the first coupling inductance 311A, and coupling inductance can be equivalent to ideal transformer and leakage inductance
Concatenated model, current ripples at this time are system optimal value.Wherein LS1 and LS2 be two windings equivalent leakage inductance, LS1 and
LS2 calculates the equivalent leakage inductance Ls for obtaining the first coupling inductance 311A according to circuit theory, and Lp is equivalent magnetizing inductance.
I.e. when the duty ratio of the work wave of switching device K11, K21 in H-bridge circuit is respectively 50%, coupled with first
The first half-bridge of the output of the first half-bridge the midpoint Vx1 and second group of H-bridge circuit 2B of first group of H-bridge circuit 2A of inductance 311A connection
The voltage waveform for exporting midpoint Vx2 is as shown in Figure 4.Due to being ideal transformer, circuit design meets LS1 and LS2 is equal, flows through
The electric current of the two windings is equal, then Vy1=Vy2, can prove Vx1-Vy=Vy-Vx2, Vy=(Vx1+Vx2)/2 here.
It is equivalent at the end Vy of ideal transformer, operating voltage is the half of Vx voltage, and the waveform that working frequency is twice is working.
It can be seen that when the duty ratio of the work wave of switching device K11, K21 in H-bridge circuit is respectively 50%, the voltage at the end Vy
It is approximate DC, the current ripples of the first coupling inductance 311A output at this time are almost negligible.When actual design, Lp is not
It may be infinity, according to the requirement of quick correspondence and low ripple, Lp and Ls appropriate can be chosen, it still being capable of maximum journey
The very low output ripple of the guarantee of degree.
After the duty ratio of switching device K11, K21 work wave in H-bridge circuit is more than 50%, then just will appear switch
The case where device K11, K21 are simultaneously turned on.At this moment ideal transformer is not present, and only LS1 and LS2 is working, for wink
For state response, response speed at this time is most fast.In this case, as long as LS1 and LS2 are sufficiently small, it is able to satisfy quick response
Requirement.
After the duty ratio of switching device K11, K21 work wave in H-bridge circuit is more than 50%, as the above analysis
One coupling inductance 311A is equivalent to low value leakage inductance, and in order to reduce current ripples at this time, introduce second level coupling inductance has very much
It is necessary.
The output end of the output end of the first coupling inductance 311A and the second coupling inductance 312A are separately connected in the present embodiment
To two input terminals of the 5th coupling inductance 315B, the output end of third coupling inductance 313A and the 4th coupling inductance 314A's is defeated
Outlet is respectively connected to two input terminals of the 6th coupling inductance 316B.The output end and the 6th inductance of 5th coupling inductance 315B
Output end be connected in the low-pass filtering capacitive part 32.
Second level coupling inductance is considered further that, due to first group of H-bridge circuit 2A, second group of H-bridge circuit 2B, third group H bridge electricity
The corresponding PWM timing of road 2C and the 4th group of H-bridge circuit 2D work is respectively 0 degree, 180 degree, 90 degree and 270 degree.Here with it is negative
It is analyzed for 5th coupling inductance 315B of load end P connection.When the forward current dynamic of load end output increases, at this time
The P input of reference load is forward direction, the case where duty ratio of H bridge translation circuit be will appear greater than 50%, according to design timing,
Just there is 90 degree of phase difference in the waveform of two input terminals for the 5th coupling inductance 315B connecting with load end P, and at this time
The five positive good berths of coupling inductance 315B are under good coupled mode.Since the coefficient of coup is higher, Approximate Equivalent is ideal coupling
Inductance is closed, then the electric current for flowing through two windings of the 5th coupling inductance 315B is approximately equal.5th coupling inductance 315B at this time
It will work together with low-pass filtering capacitive part 32, and significantly reduce output current ripple at this time.Due to the 5th coupling electricity
Feel the effect of 315B, it is obvious that each at this time group of H bridge flows through all approximate phase of output current ripple after first order coupling inductance
Deng.According to the requirement of system bandwidth, the inductance of optimization design first order coupling inductance and second level coupling inductance, final
The output current ripple that load outputs will be optimized.
When the duty ratio of H bridge conversion section occurs 100%, the 5th coupling inductance 315B will be equivalent to two independent leakages
The form of sense, coupling inductance will be not present.At this point, first order coupling inductance and second level coupling inductance are all equivalent to low value leakage inductance
Form, be able to satisfy the requirement of system maximum quick response in this way.
Low-pass filtering capacitive part 32 in the present embodiment includes one group or multiple groups high-frequency absorption circuit.High-frequency absorption electricity
Road can according to need selection and use RC absorbing circuit, C absorbing circuit, LRC absorbing circuit or LRCD absorbing circuit etc..
Claims (3)
1. a kind of gradient power amplifier based on multistage coupling inductance optimization design, including
Pwm control circuit (1) is connected, for handling respectively with the feedback end of gradient control signal output and output electric current
Gradient controls signal and exports the feedback signal of electric current, to export pwm control signal according to control logic；
Power-varying circuitry (2), input terminal are connected with the pwm control signal output end of the pwm control circuit (1), according to
Pwm control signal generates high-voltage pulse；
Low-pass filter circuit (3), input terminal are connected with the power-varying circuitry (2), defeated for filtering generation high-voltage signal
Load is arrived out, completes the conversion of high-voltage pulse to load end voltage difference of the two ends, so that generating expected electric current in load；
It is characterized by:
The low-pass filter circuit (3) includes coupling inductance part (31) and low-pass filtering capacitive part (32), the coupling electricity
Sense part (31) is connected between the power-varying circuitry (2) and the low-pass filtering capacitive part (32), the coupling electricity
Sense part (31) includes at least two-stage coupling inductance；
The power-varying circuitry (2) includes first group of H-bridge circuit (2A), second group of H-bridge circuit (2B), third group H-bridge circuit
(2C) and the 4th group of H-bridge circuit (2D), first group of H-bridge circuit (2A), second group of H-bridge circuit (2B), third group H-bridge circuit (2C)
Corresponding PWM timing is respectively 0 degree, 180 degree, 90 degree and 270 degree with the 4th group of H-bridge circuit (2D) work；
The coupling inductance part (31) includes first order coupling inductance (31A) and second level coupling inductance (31B)；
First order coupling inductance (31A) includes the first coupling inductance (311A), the second coupling inductance (312A), third coupling inductance
(313A) and the 4th coupling inductance (314A)；
Second level coupling inductance (31B) includes the 5th coupling inductance (315B) and the 6th coupling inductance (316B)；
The first half-bridge output midpoint of first group of H-bridge circuit (2A) and the first half-bridge of second group of H-bridge circuit (2B) export midpoint
It is respectively connected to two input terminals of the first coupling inductance (311A)；
The first half-bridge output midpoint of third group H-bridge circuit (2C) and the first half-bridge of the 4th group of H-bridge circuit (2D) export midpoint
It is respectively connected to two input terminals of the second coupling inductance (312A)；
The second half-bridge output midpoint of first group of H-bridge circuit (2A) and the second half-bridge of second group of H-bridge circuit (2B) export midpoint
It is respectively connected to two input terminals of third coupling inductance (313A)；
The second half-bridge output midpoint of third group H-bridge circuit (2C) and the second half-bridge of the 4th group of H-bridge circuit (2D) export midpoint
It is respectively connected to two input terminals of the 4th coupling inductance (314A)；
The output end of first coupling inductance (311A) and the output end of the second coupling inductance (312A) are respectively connected to the 5th coupling
Two input terminals of inductance (315B), the output end of the output end of third coupling inductance (313A) and the 4th coupling inductance (314A)
It is respectively connected to two input terminals of the 6th coupling inductance (316B)；
The output end of 5th coupling inductance (315B) and the output end of the 6th inductance are connected to the low-pass filtering capacitance part
Divide on (32).
2. gradient power amplifier according to claim 1, it is characterised in that: low-pass filtering capacitive part (32) packet
Include one group or multiple groups high-frequency absorption circuit.
3. gradient power amplifier according to claim 2, it is characterised in that: the high-frequency absorption circuit is that RC absorbs electricity
Road, C absorbing circuit, LRC absorbing circuit or LRCD absorbing circuit.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201610246657.5A CN105785295B (en) | 2016-04-19 | 2016-04-19 | A kind of gradient power amplifier based on multistage coupling inductance optimization design |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201610246657.5A CN105785295B (en) | 2016-04-19 | 2016-04-19 | A kind of gradient power amplifier based on multistage coupling inductance optimization design |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN105785295A CN105785295A (en) | 2016-07-20 |
| CN105785295B true CN105785295B (en) | 2019-05-03 |
Family
ID=56398028
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201610246657.5A Active CN105785295B (en) | 2016-04-19 | 2016-04-19 | A kind of gradient power amplifier based on multistage coupling inductance optimization design |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN105785295B (en) |
Families Citing this family (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN106226714A (en) * | 2016-08-31 | 2016-12-14 | 沈阳东软医疗***有限公司 | A kind of gradient amplifier, control method and imaging device |
| CN106772163B (en) * | 2017-01-25 | 2019-07-16 | 上海东软医疗科技有限公司 | A kind of gradient amplifier and its modulator approach |
| CN110995181B (en) * | 2019-12-31 | 2023-03-24 | 湖南迈太科医疗科技有限公司 | Gradient power amplifier |
Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101405671A (en) * | 2006-03-17 | 2009-04-08 | Nxp股份有限公司 | Supply circuit with ripple compensation |
| CN103280957A (en) * | 2013-05-21 | 2013-09-04 | 广西电网公司电力科学研究院 | Circuit for reducing ripple wave and inhibiting noise and for adjustable precise direct-current high-voltage source and control method |
| CN103312154A (en) * | 2012-03-12 | 2013-09-18 | 南京航空航天大学 | Series type multi input coupled inductor buck and boost converter |
| CN103312153A (en) * | 2012-03-12 | 2013-09-18 | 南京航空航天大学 | Parallel multi input coupled inductor buck and boost converter |
| CN103475248A (en) * | 2013-08-30 | 2013-12-25 | 华为技术有限公司 | Power conversion circuit and power conversion system |
| CN104142483A (en) * | 2013-05-07 | 2014-11-12 | 辽宁开普医疗***有限公司 | High-voltage high-current small-ripple-wave gradient amplifier |
| CN104950273A (en) * | 2014-03-28 | 2015-09-30 | 辽宁开普医疗***有限公司 | Gradient amplifier applying coupled inductors to output filter |
Family Cites Families (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP3202023B1 (en) * | 2014-09-29 | 2022-02-23 | Koninklijke Philips N.V. | Multi-level inverter and method for providing multi-level output voltage by utilizing the multi-level inverter |
-
2016
- 2016-04-19 CN CN201610246657.5A patent/CN105785295B/en active Active
Patent Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101405671A (en) * | 2006-03-17 | 2009-04-08 | Nxp股份有限公司 | Supply circuit with ripple compensation |
| CN103312154A (en) * | 2012-03-12 | 2013-09-18 | 南京航空航天大学 | Series type multi input coupled inductor buck and boost converter |
| CN103312153A (en) * | 2012-03-12 | 2013-09-18 | 南京航空航天大学 | Parallel multi input coupled inductor buck and boost converter |
| CN104142483A (en) * | 2013-05-07 | 2014-11-12 | 辽宁开普医疗***有限公司 | High-voltage high-current small-ripple-wave gradient amplifier |
| CN103280957A (en) * | 2013-05-21 | 2013-09-04 | 广西电网公司电力科学研究院 | Circuit for reducing ripple wave and inhibiting noise and for adjustable precise direct-current high-voltage source and control method |
| CN103475248A (en) * | 2013-08-30 | 2013-12-25 | 华为技术有限公司 | Power conversion circuit and power conversion system |
| CN104950273A (en) * | 2014-03-28 | 2015-09-30 | 辽宁开普医疗***有限公司 | Gradient amplifier applying coupled inductors to output filter |
Also Published As
| Publication number | Publication date |
|---|---|
| CN105785295A (en) | 2016-07-20 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| US9787217B2 (en) | Power conversion circuit and power conversion system | |
| CN110945771B (en) | DC/DC converter | |
| CN109167524A (en) | A kind of three-phase alternating current-direct current buck translation circuit and its control method | |
| CN106469994B (en) | Electric power converter and MRI system including this converter | |
| CN204886704U (en) | High -power switching power supply circuit and have high -voltage inverter of this circuit | |
| CN105450068B (en) | A kind of three-level current transformer IGBT burst pulse suppressing method | |
| CN105785295B (en) | A kind of gradient power amplifier based on multistage coupling inductance optimization design | |
| CN111525804B (en) | DC/DC conversion system | |
| CN106374772B (en) | The series compensation circuit and magnetic resonance imaging device of gradient amplifier | |
| US20190280615A1 (en) | Modulation method and apparatus based on three-phase neutral point clamped inverter | |
| CN102882410A (en) | Single-phase seven-level inverter | |
| CN104950273A (en) | Gradient amplifier applying coupled inductors to output filter | |
| CN206349917U (en) | A kind of resonance circuit | |
| CN103647448A (en) | Integrated step-down-flyback type high power factor constant current circuit and device | |
| CN113078820B (en) | Nine-switch tube five-level active neutral point clamped dual-active bridge isolation DC-DC converter | |
| CN104796027B (en) | Voltage balance circuit and three-phase inverter | |
| CN103762875A (en) | Non-symmetric Z-source half-bridge converter with dual output function | |
| CN208508784U (en) | Half-bridge drive circuit, chip and air conditioner | |
| CN106787886B (en) | Seven level inverse conversion topological structures and seven electrical level inverters | |
| CN112054679B (en) | Positive and negative voltage conversion direct-current power supply and control method thereof | |
| CN103701328A (en) | Isolated bi-directional DC (direct current)-DC converter | |
| JP6461439B1 (en) | DC / DC converter | |
| Kouchaki et al. | Filter design for active neutral point clamped voltage source converter using high frequency GaN-FETs | |
| CN210518110U (en) | Multi-level correction magnet power supply based on Buck circuit cascade connection | |
| CN209419505U (en) | Modified full bridge driving circuit |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |