CN105591530B - Control method is rectified based on the three-phase PWM of model prediction and triangle wave - Google Patents
Control method is rectified based on the three-phase PWM of model prediction and triangle wave Download PDFInfo
- Publication number
- CN105591530B CN105591530B CN201510737259.9A CN201510737259A CN105591530B CN 105591530 B CN105591530 B CN 105591530B CN 201510737259 A CN201510737259 A CN 201510737259A CN 105591530 B CN105591530 B CN 105591530B
- Authority
- CN
- China
- Prior art keywords
- phase
- voltage
- current
- control
- value
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/12—Arrangements for reducing harmonics from ac input or output
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Rectifiers (AREA)
Abstract
The invention discloses the three-phase PWMs based on model prediction and triangle wave to rectify control method, belongs to electric electronic current change technology, field of intelligent control.The control method of the invention is mainly made of outer voltage, Model Predictive Control, triangle wave control；Wherein outer voltage is PI link, Model Predictive Control is current inner loop control, control method is simple, using triangle wave control with the advantage of Model Predictive Control respectively realized when switching frequency is lower input power factor for 1 fixed-frequency control, exchange side input current low harmony wave.
Description
Technical field
The present invention relates to three-phase voltage type PWM commutation techniques, more particularly to three based on model prediction and triangle wave
Phase PWM rectifies control method.
Background technique
With the development of economy, the demand of high-power DC power supply rises year by year, and traditional does not control and phase control large power
Mains input current harmonic wave is big, and power factor is low larger to electric network influencing, and current-responsive is unable to meet production life slowly and needs
It asks；And Three-phase PWM Voltage Rectifier can eliminate Harmonics of Input from the root, and have unity power factor, so by
To paying close attention to for current field of power electronics.
Control strategy common at present has: hysteresis comparison control, Model Predictive Control, predictive current control, Feedforward Decoupling
Control, but these controls still have shortcoming at present: simple hysteresis comparison control input current ripple is still larger；And it is preceding
Feedback decoupling control, predictive current control need to increase SVPWM or SPWM link, and algorithm is complicated；Model Predictive Control is divided into continuously
Model Predictive Control and finite aggregate Model Predictive Control, although finite aggregate Model Predictive Control dynamic response contrast is fast, not
It is able to achieve fixed-frequency control, causes the filtering of exchange side difficult, and continuous Model Predictive Control usually requires modulator.
Summary of the invention
For the deficiency of existing control strategy, it is an object of that present invention to provide three based on model prediction and triangle wave
Phase PWM rectifies control method.Using triangle wave control and the advantage of model prediction respectively, new type of control method, letter are designed
While changing algorithm, ac-side current harmonic wave is reduced, while realizing fixed-frequency control.
The purpose of the present invention can be achieved through the following technical solutions.
Control method is rectified based on the three-phase PWM of model prediction and triangle wave, key step is as follows:
(S1) zero crossing of power grid A phase voltage (ea) is obtained using phase lock circuitry, DSP is according to power grid A phase voltage (ea)
Zero crossing calculates grid cycle in real time, and changes the control period with this, while calculating according to the zero crossing of power grid A phase voltage (ea)
The voltage value (ea, eb, ec) of power grid three-phase input, and fill and be changed to digital signal；
(S2) using current Hall sensor difference sampling three-phase reactor input current value (ia, ib, ic), using point
The output DC voltage value (Vdc) at the both ends platen press sampling three-phase voltage type PWM rectifier DC bus capacitor (C), and be converted to number
Word signal；
(S3) after completing step (S1) and (S2), by instruction DC voltage value (Vdc_ref) and output DC voltage value
(Vdc) input of the difference as outer voltage, outer voltage are controlled using PI, and the output of PI control obtains the amplitude of reference current
(I*), reference current amplitude (I*) is multiplied to obtain reference current i* α and i* β with electric network voltage phase information；
(S4) that the mathematical model of Three-phase PWM Voltage Rectifier is transformed to two-phase α β from three-phase abc rest frame is quiet
Only coordinate system, and the reference current, three-phase alternating current side electric current, the three-phase alternating current side voltage that are controlled according to outer voltage carry out mould
Type PREDICTIVE CONTROL；
(S5) rectifier bridge exchange side two-phase voltage (V α, V are obtained according to Model Predictive Control in two-phase α β rest frame
β), it and transforms to three-phase abc rest frame and obtains three-phase voltage (Va, Vb, Vc), three-phase voltage that transformation obtains is removed respectively
It is then adjusted by PI with direct voltage reference value (Vdc_ref) and clipping, output is compared with triangular wave, finally export 6
Road driving signal；Wherein the amplitude of triangular wave is consistent with PI clipping.
Further, in the step (S1), the zero crossing time of power grid A phase voltage (ea) is obtained using phase lock circuitry,
It calculates the period of power grid in real time with DSP, while calculating the value of power grid input three-phase voltage.
Further, in the step (S2), the middle input using current Hall sensor difference sampling three-phase reactor
Current value (ia, ib, ic), using the output at the both ends electric resistance partial pressure method sampling three-phase voltage type PWM rectifier DC bus capacitor (C)
DC voltage value (Vdc).
Further, in the step (S3), by instruction DC voltage value (Vdc_ref) and output DC voltage value
(Vdc) difference carries out PI control, and PI control output obtains the amplitude (I*) of reference current, reference current amplitude (I*) and cos
(wt) it is multiplied and obtains reference current i* α, reference current amplitude (I*) is multiplied to obtain reference current i* β with sin (wt).
Further, in the step (S4) and (S5), the data according to (S1), (S2), (S3) step are quiet in two-phase α β
Model Predictive Control is only carried out under coordinate system, Model Predictive Control of the present invention refers to the model prediction control of continuous state
System controls the output of model prediction and triangle wave in step (S5), to obtain three-phase driving signal.
Compared with prior art, the beneficial effects of the present invention are:
1, algorithm is simple, is not necessarily to SVPWM or SPWM modulation unit；
2, Three-phase PWM Voltage Rectifier exchange side input current ripple is low, and system can realize that unity power factor is run；
3, Three-phase PWM Voltage Rectifier DC side output voltage is controllable, and ripple is small；
4, fixed-frequency control may be implemented.
Detailed description of the invention
Fig. 1 is of the invention based on the three-phase PWM of model prediction and triangle wave rectification control method block diagram；
Fig. 2 is the effect picture using Three-phase PWM Voltage Rectifier matlab emulation DC side output voltage of the invention；
Fig. 3 is using Three-phase PWM Voltage Rectifier matlab emulation A phase AC input voltage of the invention and electric current
Effect picture.
Specific embodiment
Explanation that present invention will now be described in further detail with reference to the embodiments and the accompanying drawings, but embodiments of the present invention
It is without being limited thereto.If being that those skilled in the art can join it is noted that having the process or parameter of not special detailed description below
It is realized according to the prior art.
As shown in Figure 1, of the invention based on the rectification control method signal of the three-phase PWM of model prediction and triangle wave
Figure, key step are as follows:
(S1) zero crossing of power grid A phase voltage (ea) is obtained using phase lock circuitry, DSP is according to power grid A phase voltage (ea)
Zero crossing calculates grid cycle in real time, and changes the control period with this, while calculating according to the zero crossing of power grid A phase voltage (ea)
The voltage value (ea, eb, ec) of power grid three-phase input, and fill and be changed to digital signal；
(S2) using the input current value (ia, ib, ic) of current Hall sensor difference sampling three-phase reactor, using electricity
The DC voltage value (Vdc) at the both ends partial pressure method sampling three-phase voltage type PWM rectifier DC bus capacitor (C) is hindered, and is converted to number
Word signal；
(S3) after completing step (S1) and (S2), by instruction DC voltage value (Vdc_ref) and output DC voltage value
(Vdc) difference carries out PI control, and PI control output obtains the amplitude (I*) of reference current, reference current amplitude (I*) and cos
(wt) it is multiplied and obtains reference current i* α, reference current amplitude (I*) is multiplied to obtain reference current i* β with sin (wt)；
(S4) that the mathematical model of Three-phase PWM Voltage Rectifier is transformed to two-phase α β from three-phase abc rest frame is quiet
Only coordinate system, and the reference current, three-phase alternating current side electric current, the three-phase alternating current side voltage that are controlled according to outer voltage carry out mould
Type PREDICTIVE CONTROL, specific implementation are as described below:
A) assume that AC reactance is L, route and reactance equivalent resistance are R, and ABC triphase parameter is equal, and two-phase is static
Coordinate system (α coordinate system) lower switch function is defined as S α and S β, if the period is Ts in systematic sampling.It is fixed according to Kirchoff s voltage
Rule obtains ac-side current relationship such as formula (1):
Wherein iαAnd iβTwo-phase α β rest frame is transformed to for the input current value (ia, ib, ic) of three-phase reactor
Value；eαAnd eβThe value of two-phase α β rest frame is transformed to for the voltage value (ea, eb, ec) of power grid three-phase input；Vdc is three-phase
The DC voltage value at the both ends voltage type PWM rectifier DC bus capacitor (C)；Other parameters are as previously described.
Formula (1) discretization is obtained into the current expression (2) of k+1 sampling instant:
Wherein iα(k) and iβIt (k) is the input current measurement of three-phase reactor under k sample moment two-phase α β rest frame
Value；iα(k+1) and iβIt (k+1) is the predicted current value of three-phase reactor under k+1 sampling instant two-phase α β rest frame.
B) it is objective function such as (3) so that k+1 moment predicted current good track reference electric current i* α and i* β:
J=(iα(k+1)-iα *)2+(iβ(k+1)-iβ *)2 (3)
C) when objective function J minimum, current tracking effect is best, acquires partial differentialWithAnd it is enabled to be equal to
Zero:
Wherein Vα=Sα*Vdc, Vβ=Sβ*Vdc, VαAnd VβSide voltage is exchanged for rectifier bridge under two-phase α β rest frame.
It obtains rectifier bridge to exchange side voltage V α and V β being (5) by formula (4):
(S5) rectifier bridge exchange side voltage V α and V β is obtained according to Model Predictive Control, and is transformed into the static seat of three-phase abc
Va, Vb, Vc are obtained under mark system, then Va, Vb, Vc are passed through divided by direct voltage reference value Vdc_ref respectively to PI adjust and limit
Width, output are compared with triangular wave (amplitude is consistent with PI clipping), finally export 6 tunnel driving signals.
In step (S2), output DC voltage (Vdc) sampling uses electric resistance partial pressure, and utilizes HCPL-7840
Isolation makes the voltage range of sampled voltage adaptation DSP sample port using amplifier conditioning.
Preferably, the dsp processor that 2000 series of Texas Instruments can be selected carries out algorithm calculating.
In step (S3), DC voltage value (Vdc_ref) will be instructed and export the difference progress PI of DC voltage value (Vdc)
Control, PI control output obtain the amplitude (I*) of reference current, and reference current amplitude (I*) is multiplied to obtain with reference to electricity with cos (wt)
I* α is flowed, reference current amplitude (I*) is multiplied to obtain reference current i* β with sin (wt)；
In step (S5), it is that the output of model prediction is subjected to triangle wave control, is not necessarily to modulator, switching frequency
It is identical as triangular wave frequency, fixed frequency can be realized come regulating switch frequency by adjusting triangle wave frequency rate, to obtain three-phase drive
Dynamic signal.Wherein when triangle wave controls, the driving signal of the upper bridge arm of corresponding half-bridge is when input value is greater than triangular wave
1, the driving signal of lower bridge arm is 0；When input value is less than triangular wave, the upper bridge arm of corresponding half-bridge is 0, and the driving of lower bridge arm is believed
Number be 1.
As shown in Figure 2 to 3, the direct current output electricity emulated using Three-phase PWM Voltage Rectifier matlab of the invention
Press (Vdc) response fast, ripple is small, alternating current net side voltage A phase voltage (ea) and A phase alternating current (ia) same-phase, input power
Factor is high, is approximately 1.
Those skilled in the art can do this specific embodiment under the premise of without prejudice to the principle and substance of the present invention
It various modifications or supplement or is substituted in a similar manner out, but these changes each fall within protection scope of the present invention.Cause
This technology of the present invention range is not limited to the above embodiment.
Claims (1)
1. rectifying control method based on the three-phase PWM of model prediction and triangle wave, it is characterised in that include the following steps:
(S1) zero crossing of power grid A phase voltage (ea) is obtained using phase lock circuitry, DSP is according to the zero passage of power grid A phase voltage (ea)
Point calculates grid cycle in real time, and changes the control period with this, while calculating power grid according to the zero crossing of power grid A phase voltage (ea)
The voltage value (ea, eb, ec) of three-phase input, and be converted to digital signal；
(S2) using the input current value (ia, ib, ic) of current Hall sensor difference sampling three-phase reactor, using resistance point
The DC voltage value (Vdc) at the both ends platen press sampling three-phase voltage type PWM rectifier DC bus capacitor (C), and be converted to digital letter
Number；
(S3) after completing step (S1) and (S2), DC voltage value (Vdc_ref) will be instructed and exported DC voltage value (Vdc)
Difference carries out PI control, and PI control output obtains the amplitude (I*) of reference current, reference current amplitude (I*) and electric network voltage phase
Cos (wt) multiplication of information obtains reference current i* α, sin (wt) phase of reference current amplitude (I*) and electric network voltage phase information
It is multiplied to arrive reference current i* β；
(S4) mathematical model of Three-phase PWM Voltage Rectifier is transformed to the static seat of two-phase α β from three-phase abc rest frame
Mark system, and it is pre- according to reference current, three-phase alternating current side electric current, the three-phase alternating current side voltage progress model that outer voltage controls
Observing and controlling system, specific as follows:
A) assume that AC reactance is L, route and reactance equivalent resistance are R, and ABC triphase parameter is equal, two-phase static coordinate
It is that lower switch function is defined as S α and S β, if the period is Ts in systematic sampling；Exchange side is obtained according to Kirchhoff's second law
Current relationship such as formula (1):
Wherein iαAnd iβThe value of two-phase α β rest frame is transformed to for the input current value (ia, ib, ic) of three-phase reactor；eα
And eβThe value of two-phase α β rest frame is transformed to for the voltage value (ea, eb, ec) of power grid three-phase input；Vdc is three-phase voltage
The DC voltage value at the both ends type PWM rectifier DC bus capacitor (C)；
Formula (1) discretization is obtained into the current expression (2) of k+1 sampling instant:
Wherein iα(k) and iβIt (k) is the input current measured value of three-phase reactor under k sample moment two-phase α β rest frame；iα
(k+1) and iβIt (k+1) is the predicted current value of three-phase reactor under k+1 sampling instant two-phase α β rest frame；
It B is) so that the good track reference electric current i of k+1 moment predicted current* αAnd i* β, objective function such as (3):
J=(iα(k+1)-i* α)2+(iβ(k+1)-i* β)2 (3)
C) when objective function J minimum, current tracking effect is best, acquires partial differentialWithAnd it is enabled to be equal to zero:
Wherein Vα=Sα*Vdc, Vβ=Sβ*Vdc, VαAnd VβSide voltage is exchanged for rectifier bridge under two-phase α β rest frame；
It obtains rectifier bridge to exchange side voltage V α and V β being (5) by formula (4):
(S5) rectifier bridge exchange side voltage V α and V β is obtained according to Model Predictive Control, and is transformed into three-phase abc rest frame
Under obtain Va, Vb, Vc, by Va, Vb, Vc respectively divided by instruction DC voltage value Vdc_ref then pass through PI adjust and clipping, it is defeated
It is compared out with triangular wave, finally exports 6 tunnel driving signals, wherein triangle wave amplitude is consistent with PI clipping；
In step (S2), output DC voltage (Vdc) sampling uses electric resistance partial pressure, and is isolated using HCPL-7840,
Make the voltage range of sampled voltage adaptation DSP sample port using amplifier conditioning；
In step (S3), DC voltage value (Vdc_ref) will be instructed and export the difference progress PI control of DC voltage value (Vdc)
System, PI control output obtain the amplitude (I*) of reference current, and reference current amplitude (I*) is multiplied to obtain reference current with cos (wt)
i* α, reference current amplitude (I*) is multiplied to obtain reference current i with sin (wt)* β；
In step (S5), it is that the output of model prediction is subjected to triangle wave control, is not necessarily to modulator, switching frequency and three
Angle wave frequency rate is identical, fixed frequency can be realized by adjusting triangle wave frequency rate come regulating switch frequency, to obtain three-phase drive letter
Number；Wherein when triangle wave controls, the driving signal that input value is greater than the upper bridge arm of corresponding half-bridge when triangular wave is 1, under
The driving signal of bridge arm is 0；When input value is less than triangular wave, the driving signal of the upper bridge arm of corresponding half-bridge is 0, lower bridge arm
Driving signal is 1.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201510737259.9A CN105591530B (en) | 2015-11-01 | 2015-11-01 | Control method is rectified based on the three-phase PWM of model prediction and triangle wave |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201510737259.9A CN105591530B (en) | 2015-11-01 | 2015-11-01 | Control method is rectified based on the three-phase PWM of model prediction and triangle wave |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN105591530A CN105591530A (en) | 2016-05-18 |
| CN105591530B true CN105591530B (en) | 2019-05-14 |
Family
ID=55930853
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201510737259.9A Active CN105591530B (en) | 2015-11-01 | 2015-11-01 | Control method is rectified based on the three-phase PWM of model prediction and triangle wave |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN105591530B (en) |
Families Citing this family (9)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN106385196A (en) * | 2016-09-27 | 2017-02-08 | 华中科技大学 | Current ripple real-time prediction model-based three-level voltage source variable switching frequency control method |
| CN107204711B (en) * | 2017-07-04 | 2019-09-17 | 北京千驷驭电气有限公司 | Current prediction method and device based on extension z-transform |
| CN107528447A (en) * | 2017-07-26 | 2017-12-29 | 华南理工大学 | A kind of switch type forecast Control Algorithm |
| CN107370403A (en) * | 2017-08-31 | 2017-11-21 | 华南理工大学 | Power electronic system finite aggregate model predictive control method based on discrete-time Lyapunov function |
| CN107395035A (en) * | 2017-08-31 | 2017-11-24 | 华南理工大学 | A kind of modulator approach of the Single-phase PWM Rectifier based on discrete-time Lyapunov function |
| CN107370402B (en) * | 2017-08-31 | 2020-02-18 | 华南理工大学 | Switching control method based on discrete Lyapunov function |
| CN107453627B (en) * | 2017-08-31 | 2020-07-28 | 华南理工大学 | Fixed frequency control method for prediction control of finite set model |
| CN111211701B (en) * | 2020-02-13 | 2021-08-13 | 厦门大学 | Few-sensor model prediction control method of three-phase voltage source type rectifier |
| CN117134586B (en) * | 2023-10-26 | 2024-02-09 | 茂睿芯（深圳）科技有限公司 | Multi-mode working power factor correction control system |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103731084A (en) * | 2014-01-10 | 2014-04-16 | 西北工业大学 | Permanent magnet synchronous motor low inverter power consumption direct torque control method and device |
| CN104868761A (en) * | 2015-05-25 | 2015-08-26 | 华南理工大学 | Novel triangular wave comparison control method for three-phase PWM rectifier |
-
2015
- 2015-11-01 CN CN201510737259.9A patent/CN105591530B/en active Active
Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103731084A (en) * | 2014-01-10 | 2014-04-16 | 西北工业大学 | Permanent magnet synchronous motor low inverter power consumption direct torque control method and device |
| CN104868761A (en) * | 2015-05-25 | 2015-08-26 | 华南理工大学 | Novel triangular wave comparison control method for three-phase PWM rectifier |
Non-Patent Citations (1)
| Title |
|---|
| 三相电压源型PWM整流器控制方法的发展综述;程启明，等;《电力***保护与控制》;20120201;第40卷(第3期);第146-148页 |
Also Published As
| Publication number | Publication date |
|---|---|
| CN105591530A (en) | 2016-05-18 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN105591530B (en) | Control method is rectified based on the three-phase PWM of model prediction and triangle wave | |
| CN100521485C (en) | LCL filtering based voltage type active rectifier steady control system and method | |
| CN109217698B (en) | A kind of double-closed-loop control method based on traditional VSR closed-loop current control | |
| CN102983588B (en) | A kind of photovoltaic grid-connected inverting system based on cutting-in control algorithm | |
| CN107317490A (en) | A kind of dead beat prediction direct Power Control method based on three-phase Vienna rectifiers | |
| CN104734164B (en) | Control method for low-voltage static var generator based on voltage space vector | |
| CN106786647A (en) | A kind of three-phase four-wire system parallel connection non-linear composite control method of APF two close cycles | |
| CN105391285A (en) | Three-phase PWM rectifier control method based on deadbeat and triangular wave comparison | |
| CN110112940A (en) | A kind of PWM rectifier adaptive sliding mode QPIR control method under the β coordinate system based on α | |
| CN103326611A (en) | Controlling method for predicting direct power of three-phase voltage source type PWM converter | |
| CN105450057A (en) | Direct power prediction control method based on three-phase six-switch rectifier load current observation | |
| CN107196491B (en) | A kind of double buck gird-connected inverter half period current distortion inhibition system and method | |
| CN110311404A (en) | A kind of current predictive control method of single-phase grid-connected photovoltaic DC-to-AC converter | |
| CN104868761A (en) | Novel triangular wave comparison control method for three-phase PWM rectifier | |
| CN103887797A (en) | Control method for limiting offset current of active power filter | |
| CN108321812A (en) | A kind of prediction direct Power Control method based on fuzzy PI hybrid control | |
| CN104821601A (en) | Three-phase photovoltaic grid-connected inverter control device | |
| CN107769259B (en) | A kind of inverter current forecast Control Algorithm based on discrete averaging model | |
| CN107370403A (en) | Power electronic system finite aggregate model predictive control method based on discrete-time Lyapunov function | |
| CN105762789B (en) | A kind of 3-phase power converter model predictive control method of Converter Without Voltage Sensor | |
| CN103401405A (en) | Method for realizing selective harmonic elimination modulation by adopting fixed control cycle | |
| CN103023057A (en) | Voltage-type PWM (pulse-width modulation) rectifier output power control method under power grid unsymmetrical fault | |
| CN107294139B (en) | A kind of current source grid-connection converter control method | |
| CN109301823A (en) | A kind of electrical energy power quality disturbance compensation method based on Finite State Model predictive control strategy | |
| CN102969716A (en) | Method for controlling active power filter of marine electrical network |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |