CN105099210A - Electric quantity isolation sensor - Google Patents
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- CN105099210A CN105099210A CN201510595501.3A CN201510595501A CN105099210A CN 105099210 A CN105099210 A CN 105099210A CN 201510595501 A CN201510595501 A CN 201510595501A CN 105099210 A CN105099210 A CN 105099210A
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Abstract
The invention discloses an electric quantity isolation sensor which comprises a pulse width modulation (PWM) closed-loop modulation circuit, a transformer and a PWM demodulation circuit, wherein the PWM closed-loop modulation circuit is used for generating a PWM modulation signal by using closed-loop control according to a direct current input signal; the transformer is used for coupling pulse information in the PWM modulation signal to the PWM demodulation circuit; and the PWM demodulation circuit is used for demodulating the pulse information to obtain and output a direct current output signal. The electric quantity isolation sensor provided by the invention adopts a closed-loop PWM modulation mode, linear pulse width modulation of the direct current input signal to the PWM modulation signal is achieved, the high isolation of the electric quantity isolation sensor is achieved, and the accuracy and the reliability of the electric quantity isolation sensor are improved.
Description
Technical field
The present invention relates to electricity capacity separation sensor technical field, particularly relate to a kind of electricity capacity separation sensor.
Background technology
Along with the development of new energy technology, for optimizing energy supply efficiency, some high-power systems have employed higher operating voltage.The such as locomotive traction system of high ferro and city rail, China at present with direct current 750V, 1500V for main flow, abroad the highest traction voltage is up to 3600V; In addition, high-power frequency conversion or inverter controller, space flight high direct voltage distribution system, scientific research high-intensity magnetic field high-tension coil etc., all may be operated in high drive pattern.For the monitoring of this type systematic, on the one hand, according to safety requirements, operating voltage is high, and for ensureing the safety of the person and equipment, isolation voltage also must correspondingly improve, and as resistance toly in the isolation of metro traction system requirements is pressed in more than 10kVAC; On the other hand, relative to low pressure low-power system, bipolarity, high common mode voltage signal in this type systematic, may be there is, need to isolate withstand voltage higher, monitoring product that reliability is higher.
Electromagnetic isolation formula pulse width modulation (PulseWidthModulation, PWM) technology, transmission be pulse width signal, transmission accuracy affects by leakage inductance hardly, high isolation monitoring occasion should be applicable to very much, but, for a long time, realize high-precision PWM demodulation techniques difficulty very large, product temperature poor performance, reliability is low, especially under the prerequisite having cost control, to such an extent as to seldom sees the high accuracy industrial products being successfully applied to volume production both at home and abroad.For a long time, domestic railway systems mainly by Introduced From Abroad manufacturer transducer, in recent years, also have though domestic and see that indivedual producer is proposed high direct voltage height isolated product, and accuracy of measurement, only to 0.5 grade, also has certain gap with external product.
Therefore, the electricity capacity separation sensor of a kind of high accuracy and high reliability how is provided to be the problem that those skilled in the art need to solve at present.
Summary of the invention
The object of this invention is to provide a kind of electricity capacity separation sensor, electricity capacity separation sensor provided by the invention adopts the PWM mode of closed loop, realize the linear pulse-width modulation of direct-flow input signal to PWM modulation signal, achieve the height isolation of electricity capacity separation sensor, improve precision and the reliability of electricity capacity separation sensor.
For solving the problems of the technologies described above, the invention provides a kind of electricity capacity separation sensor, comprising:
PWM closed loop modulation circuit, for generating PWM modulation signal according to direct-flow input signal, employing closed-loop control;
Transformer, for being coupled to PWM demodulator circuit by the pulse width information in described PWM modulation signal;
Described PWM demodulator circuit, for carrying out demodulation to described pulse width information, obtaining and exporting direct-flow output signal.
Preferably, described PWM closed loop modulation circuit comprises square-wave oscillator circuit, the first filter circuit, the second inverter, the second filter circuit, integral operation amplifier, R3, R5, C5 and reference voltage setter, wherein:
Described square-wave oscillator circuit is connected with the input of described first filter circuit, the output of described first filter circuit is connected with the input of described second inverter, the output of described second inverter is respectively with the input of described second filter circuit and be connected with the input of described transformer by described C5, described direct-flow input signal delivers to the reverse input end of described integral operation amplifier after being superposed with the output end signal of described second filter circuit by described R5, the in-phase input end of described integral operation amplifier is connected with described reference voltage setter, the output of described integral operation amplifier is connected with the output of described first filter circuit through described R3.
Preferably, described square-wave oscillator circuit comprises R1, C1 and the first inverter, wherein:
The first end of described R1 is connected with the first end of described C1, described R1 is connected with the input of described first inverter with the common port of described C1, the second end ground connection of described C1, second end of described R1 is connected the output as described square-wave oscillator circuit with the output of described first direction device.
Preferably, described first filter circuit comprises R2 and C2, wherein:
The first end of described R2 is connected with the output of described square-wave oscillator circuit, second end of described R2 is connected with the first end of described C2, the second end ground connection of described C2, the first end of described R2 is as the input of described first filter circuit, and the common port of described R2 and described C2 is as the output of described first filter circuit.
Preferably, described second filter circuit comprises R4 and C4, wherein:
The first end of described R4 is connected with the output of described second inverter, second end of described R4 is connected with the first end of described C4, the second end ground connection of described C4, the first end of described R4 is as the input of described second filter, and the common port of described R4 and described C4 is as the output of described second filter circuit.
Preferably, described integral operation amplifier comprises operational amplifier and C3, wherein:
The first end of described C3 is connected with the reverse input end of described operational amplifier, and second end of described C3 is connected the output as described integral operation amplifier with the output of described operational amplifier.
Preferably, described PWM demodulator circuit comprises PWM ripple demodulating equipment, and described PWM ripple demodulating equipment comprises R6, R7, R8, R9, the first triode Q1, the second triode Q2 and d type flip flop, wherein:
The first end of described R6 is connected with the output head anode of described transformer, described R6 is connected with the emitter of described first triode Q1 and the base stage of described second triode Q2 respectively with the common port of the output head anode of described transformer, second end of described R6 is connected with the first end of described R7 and ground connection, second end of described R7 is connected with the negative pole of output end of described transformer, and the common port of the negative pole of output end of described R7 and described transformer is connected with the base stage of described first triode Q1 and the emitter of described second triode Q2 respectively; The first end of described R8 is connected with the collector electrode of described first triode Q1, the set end SD of described d type flip flop respectively, second end of described R8 is connected with the first end of described R9 and connects power supply, second end of described R9 is connected with the reset terminal CD of described second triode Q2 collector electrode, described d type flip flop respectively, the data terminal D of described d type flip flop and the equal ground connection of clock end CLK.
Preferably, described PWM demodulator circuit also comprises low pass filter and DC signal output module, wherein:
The input of described low pass filter is connected with the output P0 of described d type flip flop, and the output of described low pass filter is connected with the input of described DC signal output module, and the output of described DC signal output module exports described direct-flow output signal.
Preferably, described transformer is that PCB is without magnetic core coupling transformer.
A kind of electricity capacity separation sensor provided by the invention, comprises PWM closed loop modulation circuit, transformer and PWM demodulator circuit, and PWM closed loop modulation circuit generates PWM modulation signal according to direct-flow input signal, employing closed-loop control; Pulse width information in PWM modulation signal is coupled to PWM demodulator circuit by transformer; PWM demodulator circuit is used for carrying out demodulation to pulse width information, obtains and exports direct-flow output signal.Visible, electricity capacity separation sensor provided by the invention adopts the PWM mode of closed loop, realize the linear pulse-width modulation of direct-flow input signal to PWM modulation signal, achieve the height isolation of electricity capacity separation sensor, improve precision and the reliability of electricity capacity separation sensor.
Accompanying drawing explanation
In order to be illustrated more clearly in the technical scheme in the embodiment of the present invention, be briefly described to the accompanying drawing used required in prior art and embodiment below, apparently, accompanying drawing in the following describes is only some embodiments of the present invention, for those of ordinary skill in the art, under the prerequisite not paying creative work, other accompanying drawing can also be obtained according to these accompanying drawings.
Fig. 1 is the structural representation of a kind of electricity capacity separation sensor provided by the invention;
Fig. 2 is the circuit diagram of another kind of electricity capacity separation sensor provided by the invention.
Embodiment
Core of the present invention is to provide a kind of electricity capacity separation sensor, electricity capacity separation sensor provided by the invention adopts the PWM mode of closed loop, realize the linear pulse-width modulation of direct-flow input signal to PWM modulation signal, achieve the height isolation of electricity capacity separation sensor, improve precision and the reliability of electricity capacity separation sensor.
For making the object of the embodiment of the present invention, technical scheme and advantage clearly, below in conjunction with the accompanying drawing in the embodiment of the present invention, technical scheme in the embodiment of the present invention is clearly and completely described, obviously, described embodiment is the present invention's part embodiment, instead of whole embodiments.Based on the embodiment in the present invention, those of ordinary skill in the art, not making the every other embodiment obtained under creative work prerequisite, belong to the scope of protection of the invention.
Embodiment one
Please refer to Fig. 1, Fig. 1 is the structural representation of a kind of electricity capacity separation sensor provided by the invention;
This electricity capacity separation sensor, comprising:
PWM closed loop modulation circuit 11, for generating PWM modulation signal according to direct-flow input signal, employing closed-loop control;
Transformer 12, for being coupled to PWM demodulator circuit 13 by the pulse width information in PWM modulation signal;
PWM demodulator circuit 13, for carrying out demodulation to pulse width information, obtaining and exporting direct-flow output signal.
A kind of electricity capacity separation sensor provided by the invention, comprises PWM closed loop modulation circuit, transformer and PWM demodulator circuit, and PWM closed loop modulation circuit generates PWM modulation signal according to direct-flow input signal, employing closed-loop control; Pulse width information in PWM modulation signal is coupled to PWM demodulator circuit by transformer; PWM demodulator circuit is used for carrying out demodulation to pulse width information, obtains and exports direct-flow output signal.Visible, electricity capacity separation sensor provided by the invention adopts the PWM mode of closed loop, realize the linear pulse-width modulation of direct-flow input signal to PWM modulation signal, achieve the height isolation of electricity capacity separation sensor, improve precision and the reliability of electricity capacity separation sensor.
Embodiment two
Please refer to Fig. 2, wherein, Fig. 2 is the circuit diagram of another kind of electricity capacity separation sensor provided by the invention.
This electricity capacity separation sensor comprises:
PWM closed loop modulation circuit 21, transformer and PWM demodulator circuit 23;
As preferably, this PWM closed loop modulation circuit 21 comprises square-wave oscillator circuit, the first filter circuit, the second inverter U1B, the second filter circuit, integral operation amplifier, R3, R5, C5 and reference voltage setter, wherein:
Square-wave oscillator circuit is connected with the input of the first filter circuit, the output of the first filter circuit is connected with the input of the second inverter U1B, the output of the second inverter U1B is respectively with the input of the second filter circuit and be connected with the input of transformer by C5, direct-flow input signal delivers to the reverse input end of integral operation amplifier after being superposed with the output end signal of the second filter circuit by R5, the in-phase input end of integral operation amplifier is connected with reference voltage setter, the output of integral operation amplifier is connected with the output of the first filter circuit through R3.
As preferably, transformer is that PCB is without magnetic core coupling transformer 22.
Be understandable that, PCB is without magnetic core coupling transformer 22 by core loss and saturatedly to affect, and high frequency performance is good, low in energy consumption, and easily realizes high-voltage isolating.
In addition, as preferably, square-wave oscillator circuit comprises R1, C1 and the first inverter U1A, wherein:
The first end of R1 is connected with the first end of C1, and the common port of R1 and C1 is connected with the input of the first inverter U1A, the second end ground connection of C1, and second end of R1 is connected the output as square-wave oscillator circuit with the output of first direction device.
Be understandable that; here the first inverter U1A and above-mentioned the second inverter U1B mentioned can be all high speed Si Mite inverter; but also can be the inverter of other types; the present invention does not do special restriction at this, can realize the dissimilar inverter of the object of the invention all within protection scope of the present invention.
As preferably, the first filter circuit comprises R2 and C2, wherein:
The first end of R2 is connected with the output of square-wave oscillator circuit, and second end of R2 is connected with the first end of C2, the second end ground connection of C2, and the first end of R2 is as the input of the first filter circuit, and the common port of R2 and C2 is as the output of the first filter circuit.
As preferably, the second filter circuit comprises R4 and C4, wherein:
The first end of R4 is connected with the output of the second inverter U1B, and second end of R4 is connected with the first end of C4, the second end ground connection of C4, and the first end of R4 is as the input of the second filter, and the common port of R4 and C4 is as the output of the second filter circuit.
Be understandable that; the particular circuit configurations of above-mentioned first filter circuit and the second filter circuit is a kind of preferred form provided by the invention; the present invention does not do special restriction for the particular circuit configurations of the first filter circuit and the second filter circuit, can realize the filter circuit of the object of the invention all within protection scope of the present invention.
As preferably, integral operation amplifier comprises operational amplifier and C3, wherein:
The first end of C3 is connected with the reverse input end of operational amplifier, and second end of C3 is connected the output as integral operation amplifier with the output of operational amplifier.
Be understandable that, first inverter U1A and R1, C1 forms square-wave oscillator circuit (this part is digital circuit), produce the fundamental frequency square-wave signal of certain frequency, fundamental frequency square-wave signal is after the first filter circuit (being also R2 and C2) filtering, obtain approximate triangular signal, as the positive threshold voltage VT+ of triangular signal voltage higher than the second inverter U1B, second inverter U1B output low level, as the negative threshold voltage VT-of triangular signal voltage lower than the second inverter U1B, inverter exports high level, therefore, different according to the amplitude of triangular signal, what the second inverter U1B exported is the square-wave signal that duty ratio is relevant to its positive and negative threshold voltage, also be PWM modulation signal.
PWM modulation signal superposes with the direct-flow input signal VIN through R5 after the second filter circuit (being also R4 and C4) filtering, obtain error signal E, error signal E compares integration by integral operation amplifier with reference to the reference voltage VREF given to constant voltage device again, the voltage signal that integral operation amplifier exports is added on the triangular signal of the first filter circuit output by R3, the amplitude translation of triangular signal changes, and then achieve the duty ratio of adjustment PWM modulation signal, achieve the linear pulse-width modulation (this part be analog circuit) of direct-flow input signal to PWM modulation signal.
Further, under the effect of closed-loop control, the output of integral operation amplifier carries out upper and lower translation to triangular signal in real time through resistance R3, change the position of the intersection point of the positive and negative threshold voltage of triangular signal and the second inverter U1B, and then achieving the adjustment of the duty ratio to PWM modulation signal, the inverting input average voltage that PWM closed loop modulation circuit 21 is finally stabilized in integral operation amplifier is equal with reference voltage VREF.If control the half that reference voltage VREF is the power supply VCC of integral operation amplifier, then when not adding direct-flow input signal VIN, the duty ratio of PWM modulation signal is the output of 50%, PWM closed loop modulation circuit 21 is 0, can increase zero adjustment circuit if desired.When there being direct-flow input signal VIN to input, the anti-phase input terminal voltage of integral operation amplifier changes, under the effect of feedback loop, the duty ratio of the PWM modulation signal that adjustment second inverter U1B exports by PWM closed loop modulation circuit 21, finally still make the reverse input end average voltage of integral operation amplifier equal with reference voltage VREF, realize the linear modulation of direct-flow input signal to PWM modulation signal duty ratio.
Be understandable that, when exporting PWM modulation signal, except providing the second inverter U1B in the present embodiment, additionally provide the PWM modulation signal drive circuit (this part is analog circuit) that U1C, U1D, U1E and U1F compose in parallel, for strengthening the driving force of the PWM modulation signal of output, the pulse width information of PWM modulation signal, through electric capacity C5 AC coupled rear drive transformer, is coupled to PWM demodulator circuit 23 by PWM modulation signal.
Therefore, be understood that, on the one hand, the duty ratio of PWM modulation signal is only relevant with the power supply VCC of direct-flow input signal VIN, reference voltage VREF and integral operation amplifier, because direct-flow input signal VIN is detected input signals, therefore, the accuracy of measurement of direct-flow input signal VIN is determined by power supply VCC, the reference voltage VREF of integral operation amplifier and the output rising time of the second inverter U1B (can be such as Si Mite inverter) and trailing edge time symmetry.And be easy to buying due to the reference voltage setter of high accuracy, low drifting; And, within the scope of certain frequency, output rising edge and the trailing edge time symmetry of the second inverter U1B almost can be ignored, therefore, this PWM closed loop modulation circuit 21 is easy to realize high measurement accuracy, do not rely on the linearity at the edge of triangular signal, strong to the fault tolerance of component parameter.That is, in PWM closed loop modulation circuit 21 close loop negative feedback effect under, as long as the power supply VCC of integral operation amplifier and reference voltage VREF is enough accurate, even if having the frequency of oscillation because the Parameters variation of other components and parts in PWM closed loop modulation circuit 21 causes, triangular signal transformation, filtering and integration time constant etc. among a small circle in situation about changing occur, these change caused by error also can be implemented closed loop, can not affect the accuracy of measurement, stability is fine.
On the other hand, the pulse width information of the just PWM modulation signal of transformer transmission, it is one group of switching signal, the ringing noise that transformer leakage inductance brings can not affect the transmission of pulse width information, on certainty of measurement almost without impact, visible, transformer is easy to realize high-isolating, and the ratio conversion introduced because of electromagnetic interference etc. in transformer work also can not affect the accuracy of the duty ratio of PWM modulation signal, reliability is high.
As preferably, PWM demodulator circuit 23 comprises PWM ripple demodulating equipment 231, and this PWM ripple demodulating equipment 231 comprises R6, R7, R8, R9, the first triode Q1, the second triode Q2 and d type flip flop U3A, wherein:
The first end of R6 is connected with the output head anode of transformer, R6 is connected with the emitter of the first triode Q1 and the base stage of the second triode Q2 respectively with the common port of the output head anode of transformer, second end of R6 is connected with the first end of R7 and ground connection, second end of R7 is connected with the negative pole of output end of transformer, and the common port of the negative pole of output end of R7 and transformer is connected with the base stage of the first triode Q1 and the emitter of the second triode Q2 respectively; The first end of R8 is connected with the collector electrode of the first triode Q1, the set end SD of d type flip flop U3A respectively, second end of R8 is connected with the first end of R9 and meets power vd D, second end of R9 is connected with the reset terminal CD of the second triode Q2 collector electrode, d type flip flop U3A respectively, the data terminal D of d type flip flop U3A and the equal ground connection of clock end CLK.
Be understandable that, namely due to transformer transmission is one group of pulse width information (also switching information), sign be the duty cycle information of PWM modulation signal, the target of demodulation is PWM modulation signal pulse width information being reduced to clamping.The power supply termination power vd D of d type flip flop U3A, in addition, due to data terminal D and the equal ground connection of clock end CLK of d type flip flop U3A, the upset of output level is only controlled by set end SD and reset terminal CD.When the PWM-(being also pulse width information-) that the PWM+ that the output head anode of transformer exports (being also pulse width information+) exports relative to the negative pole of output end of transformer exports positive pulse, first triode Q1 ends, second triode Q2 conducting, the set end SD of d type flip flop U3A is high level, reset terminal CD is low level, the inverse output terminal of d type flip flop U3A, also namely PO exports high level; When the PWM-that the PWM+ exported when the output head anode of transformer (also i.e. pulse width information+) exports relative to the negative pole of output end of transformer (also i.e. pulse width information-) output negative pulse, first triode Q1 conducting, second triode Q2 ends, the set end SD of d type flip flop U3A is low level, reset terminal CD is high level, the inverse output terminal of d type flip flop U3A, is also PO output low level, completes the demodulation of the pulse width information to PWM modulation signal.
Visible, the precision of PWM ripple demodulating equipment 231 is only by the control of the power vd D of demodulator circuit, and the bell signal of transformer affects the conducting edge of pulse width information hardly, and electromagnetic interference performance is good; In addition, the effective range due to the set end SD of digital logic device d type flip flop U3A, reset terminal CD level signal is wide; When in the work of PWM ripple demodulating equipment 231, each resistance, triode electric current etc. change among a small circle because of temperature change, impact hardly the precision of demodulation, circuit reliability is high.
As preferably, PWM demodulator circuit 23 also comprises low pass filter 232 and DC signal output module 233, wherein:
The input of low pass filter 232 is connected with the output P0 of d type flip flop U3A, and the output of low pass filter 232 is connected with the input of DC signal output module 233, and the output of DC signal output module 233 exports direct-flow output signal.
The PWM modulation signal obtained after pulse width information demodulation is delivered to low pass filter 232 by PWM ripple demodulating equipment 231, PWM modulation signal after low pass filter 232 pairs of demodulation carries out filtering, and the PWM modulation signal after is after filtering converted to the direct-flow output signal linear with direct-flow input signal and exports by DC signal output module 233.
In addition, DC signal output module 233 is here direct current output module and/or direct voltage output module.
A kind of electricity capacity separation sensor that the present embodiment provides, on the basis of embodiment one, Transformer Selection PCB, without magnetic core coupling transformer, furthermore achieved that the height isolation of electricity capacity separation sensor, improves precision and the reliability of electricity capacity separation sensor.
In this specification, each embodiment adopts the mode of going forward one by one to describe, and what each embodiment stressed is the difference with other embodiments, between each embodiment identical similar portion mutually see.
Also it should be noted that, in this manual, the such as relational terms of first and second grades and so on is only used for an entity or operation to separate with another entity or operating space, and not necessarily requires or imply the relation that there is any this reality between these entities or operation or sequentially.And, term " comprises ", " comprising " or its any other variant are intended to contain comprising of nonexcludability, thus make to comprise the process of a series of key element, method, article or equipment and not only comprise those key elements, but also comprise other key elements clearly do not listed, or also comprise by the intrinsic key element of this process, method, article or equipment.When not more restrictions, the key element limited by statement " comprising ... ", and be not precluded within process, method, article or the equipment comprising described key element and also there is other identical element.
To the above-mentioned explanation of the disclosed embodiments, professional and technical personnel in the field are realized or uses the present invention.To be apparent for those skilled in the art to the multiple amendment of these embodiments, General Principle as defined herein can without departing from the spirit or scope of the present invention, realize in other embodiments.Therefore, the present invention can not be restricted to these embodiments shown in this article, but will meet the widest scope consistent with principle disclosed herein and features of novelty.
Claims (9)
1. an electricity capacity separation sensor, is characterized in that, comprising:
PWM closed loop modulation circuit, for generating PWM modulation signal according to direct-flow input signal, employing closed-loop control;
Transformer, for being coupled to PWM demodulator circuit by the pulse width information in described PWM modulation signal;
Described PWM demodulator circuit, for carrying out demodulation to described pulse width information, obtaining and exporting direct-flow output signal.
2. electricity capacity separation sensor as claimed in claim 1, it is characterized in that, described PWM closed loop modulation circuit comprises square-wave oscillator circuit, the first filter circuit, the second inverter, the second filter circuit, integral operation amplifier, R3, R5, C5 and reference voltage setter, wherein:
Described square-wave oscillator circuit is connected with the input of described first filter circuit, the output of described first filter circuit is connected with the input of described second inverter, the output of described second inverter is respectively with the input of described second filter circuit and be connected with the input of described transformer by described C5, described direct-flow input signal delivers to the reverse input end of described integral operation amplifier after being superposed with the output end signal of described second filter circuit by described R5, the in-phase input end of described integral operation amplifier is connected with described reference voltage setter, the output of described integral operation amplifier is connected with the output of described first filter circuit through described R3.
3. electricity capacity separation sensor as claimed in claim 2, it is characterized in that, described square-wave oscillator circuit comprises R1, C1 and the first inverter, wherein:
The first end of described R1 is connected with the first end of described C1, described R1 is connected with the input of described first inverter with the common port of described C1, the second end ground connection of described C1, second end of described R1 is connected the output as described square-wave oscillator circuit with the output of described first direction device.
4. electricity capacity separation sensor as claimed in claim 2, it is characterized in that, described first filter circuit comprises R2 and C2, wherein:
The first end of described R2 is connected with the output of described square-wave oscillator circuit, second end of described R2 is connected with the first end of described C2, the second end ground connection of described C2, the first end of described R2 is as the input of described first filter circuit, and the common port of described R2 and described C2 is as the output of described first filter circuit.
5. electricity capacity separation sensor as claimed in claim 2, it is characterized in that, described second filter circuit comprises R4 and C4, wherein:
The first end of described R4 is connected with the output of described second inverter, second end of described R4 is connected with the first end of described C4, the second end ground connection of described C4, the first end of described R4 is as the input of described second filter, and the common port of described R4 and described C4 is as the output of described second filter circuit.
6. electricity capacity separation sensor as claimed in claim 2, it is characterized in that, described integral operation amplifier comprises operational amplifier and C3, wherein:
The first end of described C3 is connected with the reverse input end of described operational amplifier, and second end of described C3 is connected the output as described integral operation amplifier with the output of described operational amplifier.
7. electricity capacity separation sensor as claimed in claim 1, it is characterized in that, described PWM demodulator circuit comprises PWM ripple demodulating equipment, and described PWM ripple demodulating equipment comprises R6, R7, R8, R9, the first triode Q1, the second triode Q2 and d type flip flop, wherein:
The first end of described R6 is connected with the output head anode of described transformer, described R6 is connected with the emitter of described first triode Q1 and the base stage of described second triode Q2 respectively with the common port of the output head anode of described transformer, second end of described R6 is connected with the first end of described R7 and ground connection, second end of described R7 is connected with the negative pole of output end of described transformer, and the common port of the negative pole of output end of described R7 and described transformer is connected with the base stage of described first triode Q1 and the emitter of described second triode Q2 respectively; The first end of described R8 is connected with the collector electrode of described first triode Q1, the set end SD of described d type flip flop respectively, second end of described R8 is connected with the first end of described R9 and connects power supply, second end of described R9 is connected with the reset terminal CD of described second triode Q2 collector electrode, described d type flip flop respectively, the data terminal D of described d type flip flop and the equal ground connection of clock end CLK.
8. electricity capacity separation sensor as claimed in claim 1, it is characterized in that, described PWM demodulator circuit also comprises low pass filter and DC signal output module, wherein:
The input of described low pass filter is connected with the output P0 of described d type flip flop, and the output of described low pass filter is connected with the input of described DC signal output module, and the output of described DC signal output module exports described direct-flow output signal.
9. the electricity capacity separation sensor as described in any one of claim 1-8, is characterized in that, described transformer is that PCB is without magnetic core coupling transformer.
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| WO2017143926A1 (en) * | 2016-02-25 | 2017-08-31 | Huawei Technologies Co., Ltd. | Signal processing arrangement for a transmitter |
| CN110190837A (en) * | 2019-06-24 | 2019-08-30 | 镇江英创电力电子有限公司 | A kind of isolated amplifier device |
| CN112260542A (en) * | 2020-09-07 | 2021-01-22 | 上海军陶电源设备有限公司 | Circuit for realizing on/off signal isolation transmission function and control method |
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| CN205178886U (en) * | 2015-09-17 | 2016-04-20 | 绵阳市维博电子有限责任公司 | Sensor is kept apart to electric quantity |
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| CN103684422A (en) * | 2013-12-12 | 2014-03-26 | 安伏（苏州）电子有限公司 | High-voltage direct current signal isolating and sampling device of non-optical coupling element |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| WO2017143926A1 (en) * | 2016-02-25 | 2017-08-31 | Huawei Technologies Co., Ltd. | Signal processing arrangement for a transmitter |
| CN108702351A (en) * | 2016-02-25 | 2018-10-23 | 华为技术有限公司 | Signal processing framework for transmitter |
| US10516424B2 (en) | 2016-02-25 | 2019-12-24 | Huawei Technologies Co., Ltd. | Signal processing arrangement for a transmitter |
| CN108702351B (en) * | 2016-02-25 | 2021-03-02 | 华为技术有限公司 | Signal processing architecture for transmitters |
| CN110190837A (en) * | 2019-06-24 | 2019-08-30 | 镇江英创电力电子有限公司 | A kind of isolated amplifier device |
| CN110190837B (en) * | 2019-06-24 | 2024-03-15 | 镇江英创电力电子有限公司 | Isolation amplifier device |
| CN112260542A (en) * | 2020-09-07 | 2021-01-22 | 上海军陶电源设备有限公司 | Circuit for realizing on/off signal isolation transmission function and control method |
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| CN105099210B (en) | 2018-02-06 |
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