CN104717164A - Signal correction method and signal correction device - Google Patents

Signal correction method and signal correction device Download PDF

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Publication number
CN104717164A
CN104717164A CN201310675974.5A CN201310675974A CN104717164A CN 104717164 A CN104717164 A CN 104717164A CN 201310675974 A CN201310675974 A CN 201310675974A CN 104717164 A CN104717164 A CN 104717164A
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signal path
filter
correction coefficient
signal
frequency mixer
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CN104717164B (en
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张元硕
郑景嘉
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Realtek Semiconductor Corp
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Realtek Semiconductor Corp
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Abstract

A signal correction method applied to correct mismatch between an in-phase signal path and an orthographic signal path of a transmitter comprises the following steps: additionally setting at least one mixer correction coefficient at a transmitting end of the transmitter; looping back at least one mixer test signal from the transmitting end to conduct spectrum analysis to obtain at least one mixer spectrum analysis result; adjusting the at least one mixer correction coefficient of the transmitting end according to the at least one mixer spectrum analysis result; and additionally using an in-phase signal path finite impulse response filter and an orthogonal signal path finite impulse response filter to correct mismatch between a low-pass filter of the in-phase signal path at the transmitting end and a low-pass filter of the orthographic signal path at the transmitting end. A similar mismatch correction operation can also be applied to a receiver.

Description

Signal bearing calibration and means for correcting
Technical field
Embodiment disclosed by the present invention is the bearing calibration and the interlock circuit that are relevant to communication system, the espespecially a kind of unmatched bearing calibration of orthogonal with one (Q) signal path of a homophase (I) signal path and relevant apparatus being applied to a conveyer.
Background technology
In general, more complicated modulation technique can include more message data usually, namely, transmission rate can be improved by the modulation treatment of complexity, as 64 quadrature amplitude modulation (64-Quadrature Amplitude Modulation, 64-QAM), or even 256-QAM.Therefore, more and more universal for the amplitude-modulated demand of high-order orthogonal.If expect, high-order orthogonal Modulation and Amplitude Modulation can have good biography to produce effects really, error vector magnitude value (the Error Vector Magnitude of communication system must be improved accordingly, EVM), and to affect one of most important factor of error vector magnitude value be homophase with orthogonal between the degree of uneven (In-phase Quadrature-phase imbalance, IQimbalance).The unbalanced main cause of IQ is caused to be radio frequency (Radio Frequency, RF) circuit not mating at IQ two-way, even deviation slightly also can impact global communication system, form incomplete quadrature modulation/rectification program, and then cause the rising of the receiving terminal error rate (Bit Error Rate, BER).This deviation can be divided into again amplitude (amplitude) deviation and phase place (phase) deviation, once these deviations exist, frequency spectrum just can produce the Image interference of symmetrical frequency.Please refer to Fig. 1, the schematic diagram that receive a mirror image signal that signal and this reception signal produce of Fig. 1 received by a receiving terminal.Difference between the amplitude of this reception signal and the amplitude of this mirror image signal is commonly referred to as mirror image and repels than (Image Rejection Ratio, IRR), and for example, when the serious imbalance of IQ, IRR is just little, otherwise then large.
In order to improve the impact that this deviation causes, on side circuit often before formal transmitting-receiving signal, first carrying out the action correcting (calibration), being called that IQ corrects.And cause the in-phase path in circuit and quadrature path each other unmatched main source have two, one is local oscillator (local oscillator, LO) carrier wave when carrier wave being pushed to separately frequency mixer (mixer) on in-phase path and quadrature path is produced, be difficult to present perfect 90 degree of phase differences, or two that are pushed to in-phase path and quadrature path frequency mixer separately carry that wave amplitude is not of uniform size to be caused, namely above-mentioned phase deviation and amplitude excursion.Its two for due to have unavoidably in circuit manufacture procedure faulty situation occur, therefore the two groups of assemblies Incomplete matching each other on in-phase path and quadrature path can be made, such as, low pass filter (low-pass filter in in-phase path and quadrature path, LPF), analog-digital converter (analog-to-digital converter, ADC), digital analog converter (digital-to-analog converter, or the assembly such as gain amplifier (gain amplifier) does not mate DAC), thus can cause and produce difference by the signal of in-phase path and quadrature path, when signal is by the in-phase path that do not match each other each other and quadrature path, just often Image interference signal (as shown in Figure 1) is produced, cause the reduction of signal quality.Therefore, in communication system, how to perform IQ and correct, become a considerable subject under discussion in field for this reason.
Summary of the invention
According to embodiments of the invention, disclose a kind of unmatched bearing calibration of orthogonal with one (Q) signal path of a homophase (I) signal path and the interlock circuit that are applied to a conveyer, to solve the problem.
According to the present invention one first embodiment, disclose a kind of signal bearing calibration, for correcting one first signal path of a conveyer and not mating between one second signal path, wherein this one of first signal path and this second signal path are a homophase (I) signal path, another of this first signal path and this second signal path is one orthogonal (Q) signal path, and this bearing calibration includes: at least one frequency mixer correction coefficient of a transmission end extra setup of this conveyer; At least one frequency mixer test signal is produced one first from this transmission end through this at least one frequency mixer correction coefficient and transmits signal, and this first transmission signal of loopback (loopback) carries out spectrum analysis to obtain at least one frequency mixer result of spectrum analysis; This at least one frequency mixer correction coefficient is adjusted according to this at least one frequency mixer result of spectrum analysis, to obtain this final at least one frequency mixer correction coefficient, with not mating between a frequency mixer of the frequency mixer and this second signal path that correct this first signal path; And additionally utilize one first signal path finite impulse response filter (finite impulseresponse filter, FIR filter) one first signal path finite impulse response (FIR) process is carried out to this first signal path, and additionally utilize one second signal path finite impulse response filter to carry out one second signal path finite impulse response (FIR) process to this second signal path, with not mating between a filter of the filter and this second signal path that correct this first signal path.
According to the present invention one second embodiment, disclose a kind of signal bearing calibration, for a receiver a homophase (I) signal path orthogonal with one (Q) signal path between do not mate, include: at least one frequency mixer correction coefficient of a receiving terminal extra setup of this receiver, being exported from a transmission end of this receiver by least one frequency mixer test signal is one first transmission signal, this of returning in loopback (loopback) first transmits signal after this at least one frequency mixer correction coefficient, carries out spectrum analysis to obtain at least one frequency mixer result of spectrum analysis to it, this at least one frequency mixer correction coefficient of this receiving terminal is adjusted according to this at least one frequency mixer result of spectrum analysis, to obtain this final at least one frequency mixer correction coefficient, with not mating between a frequency mixer of this second signal path of the frequency mixer and this receiving terminal that correct this first signal path of this receiving terminal of this receiver, and additionally utilize one first signal path finite impulse response filter (finite impulseresponse filter, FIR filter) one first signal path finite impulse response (FIR) process is carried out to this first signal path of this receiving terminal, and additionally utilize one second signal path finite impulse response filter this second signal path to this receiving terminal to carry out one second signal path finite impulse response (FIR) process, with not mating between a filter of this second signal path of the filter and this receiving terminal that correct this first signal path of this receiving terminal of this receiver.
According to the present invention 1 the 3rd embodiment, disclose a kind of signal means for correcting, for correcting one first signal path of a conveyer and not mating between one second signal path, wherein this one of first signal path and this second signal path are a homophase (I) signal path, another of this first signal path and this second signal path is one orthogonal (Q) signal path, this means for correcting includes a frequency mixer correction coefficient unit, one frequency mixer test signal generation unit, one spectral analysis unit, one frequency mixer correction coefficient adjustment unit and a finite impulse response filter unit.Wherein this frequency mixer correction coefficient unit is the transmission end being coupled to this conveyer, and is set with at least one frequency mixer correction coefficient.This frequency mixer test signal generation unit transmits signal for being used for that at least one frequency mixer test signal is produced one first from this transmission end through this at least one frequency mixer correction coefficient.This spectral analysis unit first transmits signal to carry out spectrum analysis to obtain at least one frequency mixer result of spectrum analysis for this being used for returning to loopback (loopback).This frequency mixer correction coefficient adjustment unit is for being used for according to this at least one frequency mixer result of spectrum analysis to adjust this at least one frequency mixer correction coefficient, to obtain this final at least one frequency mixer correction coefficient, with not mating between a frequency mixer of the frequency mixer and this second signal path that correct this first signal path.This finite impulse response filter unit is this transmission end being coupled to this conveyer, and be used for additionally utilizing one first signal path finite impulse response filter (finite impulse response filter, FIR filter) one first signal path finite impulse response (FIR) process is carried out to this first signal path, and additionally utilize one second signal path finite impulse response filter to carry out one second signal path finite impulse response (FIR) process to this second signal path, with not mating between a filter of the filter and this second signal path that correct this first signal path.
According to the present invention 1 the 4th embodiment, disclose a kind of signal means for correcting, for correcting one first signal path of a receiver and not mating between one second signal path, wherein this one of first signal path and this second signal path are a homophase (I) signal path, another of this first signal path and this second signal path is one orthogonal (Q) signal path, this means for correcting includes a frequency mixer correction coefficient unit, one frequency mixer test signal generation unit, one spectral analysis unit, one frequency mixer correction coefficient adjustment unit and a finite impulse response filter unit.Wherein this frequency mixer correction coefficient unit is the receiving terminal being coupled to this receiver, and is set with at least one frequency mixer correction coefficient.This frequency mixer test signal generation unit is transmit signal at least one frequency mixer test signal is produced one first from a transmission end of this receiver.This spectral analysis unit, for this first transmission signal of returning in loopback (loopback) is after this at least one frequency mixer correction coefficient, carries out spectrum analysis to obtain at least one frequency mixer result of spectrum analysis to it.This frequency mixer correction coefficient adjustment unit be for according to this at least one frequency mixer result of spectrum analysis to adjust this at least one frequency mixer correction coefficient of this receiving terminal, to obtain this final at least one frequency mixer correction coefficient, with not mating between a frequency mixer of this second signal path of the frequency mixer and this receiving terminal that correct this first signal path of this receiving terminal of this receiver.This finite impulse response filter unit is this receiving terminal being coupled to this receiver, and be used for additionally utilizing one first signal path finite impulse response filter (finite impulse response filter, FIR filter) one first signal path finite impulse response (FIR) process is carried out to this first signal path of this receiving terminal, and additionally utilize one second signal path finite impulse response filter this second signal path to this receiving terminal to carry out one second signal path finite impulse response (FIR) process, with not mating between a filter of this second signal path of the filter and this receiving terminal that correct this first signal path of this receiving terminal of this receiver.
One of them advantage of the present invention be can above method and device compensate a conveyer a homophase (I) signal path orthogonal with one (Q) signal path between do not mate, especially can compensate this homophase signal path of this conveyer and not mating between this orthogonal signal path frequency mixer separately; And compensate this homophase signal path of this conveyer and not mating between this orthogonal signal path low pass filter separately.Not mating by after adequate compensation/correction between homophase signal path with orthogonal signal path, electronic installation just can obtain preferably communication usefulness.
Accompanying drawing explanation
The schematic diagram that receive a mirror image signal that signal and this reception signal produce of Fig. 1 received by a receiving terminal.
Fig. 2 is the schematic diagram that OFDM modulation passes a conveyer of receipts machine.
Fig. 3 is the schematic diagram that OFDM modulation passes a receiver of receipts machine.
Fig. 4 is for correcting the schematic diagram of an embodiment of the unmatched a kind of means for correcting between one first signal path of a conveyer and one second signal path according to the present invention.
Fig. 5 is the schematic diagram of another setting of the means for correcting of Fig. 4.
Fig. 6 is the schematic diagram of the embodiment according to the first homophase signal path frequency response computing unit of the present invention.
Fig. 7 is the schematic diagram of another embodiment according to the first homophase signal path frequency response computing unit of the present invention.
Fig. 8 is for correcting the schematic diagram of another embodiment of the unmatched a kind of means for correcting between one first signal path of a conveyer and one second signal path according to the present invention.
Fig. 9 is the schematic diagram of another setting of the means for correcting of Fig. 8.
Figure 10 is the schematic diagram of the embodiment according to the second homophase signal path frequency response computing unit of the present invention.
Figure 11 is the schematic diagram of another embodiment according to the second homophase signal path frequency response computing unit of the present invention.
Figure 12 is for correcting the flow chart of an embodiment of the unmatched a kind of bearing calibration between one first signal path of a conveyer and one second signal path according to the present invention.
Figure 13 is for correcting the flow chart of another embodiment of the unmatched a kind of bearing calibration between one first signal path of a conveyer and one second signal path according to the present invention.
Figure 14 is for correcting the schematic diagram of an embodiment of the unmatched a kind of means for correcting between one first signal path of a receiver and one second signal path according to the present invention.
Figure 15 is for correcting the schematic diagram of another embodiment of the unmatched a kind of means for correcting between one first signal path of a receiver and one second signal path according to the present invention.
Figure 16 is for correcting the flow chart of an embodiment of the unmatched a kind of bearing calibration between one first signal path of a receiver and one second signal path according to the present invention.
Figure 17 is for correcting the flow chart of another embodiment of the unmatched a kind of bearing calibration between one first signal path of a receiver and one second signal path according to the present invention.
Wherein, description of reference numerals is as follows:
200,400,800 conveyers
440,1432 transmission ends
202,302 homophase signal path
204,304 orthogonal signal paths
206,306 correction coefficient unit
300,1400,1500 receivers
432,1440 receiving terminals
402,1402 frequency mixer test signal generation unit
404,1404 low pass filter test signal generation unit
406,1406 frequency mixer correction coefficient unit
408,805,1408,1505 switch units
410,1410 low pass filter correction coefficient unit
412,812,1412,1512 tap coefficient calculation unit
414,1414 finite impulse response filter unit
416 first digital analog converters
418 second digital analog converters
420,1,420 first low pass filters
422,1,422 second low pass filters
424,1,424 first frequency mixers
426,1,426 second frequency mixers
428,1428 oscillators
430 power amplifiers
434 spectral analysis unit
436,1436 frequency mixer correction coefficient adjustment units
438,1438 low pass filter correction coefficient adjustment units
4122,14122 orthogonal signal path frequencies RESPONSE CALCULATION unit
4124,14,124 first homophase signal path frequency response computing units
4126,14126 coefficient calculation unit
4142,14,142 first finite impulse response filters
4144,14,144 second finite impulse response filters
8124,15,124 second homophase signal path frequency response computing units
1202 ~ 1222,1310 ~ 1318 steps
1602 ~ 1622,1710 ~ 1718 steps
1430 low noise amplifiers
1416 first analog-digital converters
1418 second analog-digital converters
Embodiment
Some vocabulary is employed to censure specific assembly in the middle of specification and claims.Person with usual knowledge in their respective areas should understand, and same assembly may be called with different nouns by manufacturer.This specification and claims book is not used as with the difference of title the mode distinguishing assembly, but is used as the criterion of differentiation with assembly difference functionally." comprising " mentioned in the middle of specification and claim is in the whole text an open term, therefore should be construed to " comprise but be not limited to ".In addition, " couple " word in this case comprise directly any and be indirectly electrically connected means.Therefore, if describe a first device in literary composition to be coupled to one second device, then represent this first device and directly can be electrically connected in this second device, or be indirectly electrically connected to this second device by other devices or connection means.
About means for correcting of the present invention, first by mathematical expression, its basic theories is described below, first, please refer to Fig. 2, Fig. 2 is the schematic diagram that OFDM modulation passes a conveyer of receipts machine.In general, whether a homophase (I) signal path 202 orthogonal with one (Q) signal path 204 tested in conveyer 200 has unmatched situation, the signal (single-tone signal) with single-frequency can be inputed to conveyer 200 and by it, then observe the signal of output whether occur mirror image (image) signal.When the mirror image signal produced is stronger, represent that homophase (I) signal path 202 is higher with the unmatched degree between orthogonal (Q) signal path 204.A correction coefficient unit 206 is included in conveyer 200, interior containing two correction coefficient, one first coefficient X and one second coefficient Y respectively, as shown in Figure 2, first coefficient X does not mate with the amplitude of signal between orthogonal (Q) signal path 204 for being used for correcting homophase (I) signal path 202, and the second coefficient Y does not mate with the phase place of signal between orthogonal (Q) signal path 204 for being used for correcting homophase (I) signal path 202.By the first coefficient X in change correction coefficient unit 206 and the second coefficient Y, the effect eliminating mirror image signal can be reached.In theory, want fully to eliminate mirror image signal, the equation that demand fulfillment is following:
X = 1 R cos ( Φ ) - - - ( 1 )
Y=-tan(Φ) (2)
Φ herein represents that frequency is f ssingle-frequency test signal do not mate produced phase difference through the path of homophase (I) signal path 202 and orthogonal (Q) signal path 204, R is then for frequency is f ssingle-frequency test signal do not mate produced amplitude difference ratio through the path of homophase (I) signal path 202 and orthogonal (Q) signal path 204.
In addition, please refer to Fig. 3, Fig. 3 is the schematic diagram that OFDM modulation passes a receiver of receipts machine.In general, a homophase (I) signal path 302 orthogonal with one (Q) signal path 304 in test receiver 300 is wanted whether to have unmatched situation, the signal (single-tone signal) with single-frequency can be inputed to receiver 300 and by it, whether the signal then analyzing receiving terminal occurs mirror image (image) signal.Including a correction coefficient unit 306 in receiver 300, inside contain two correction coefficient, is one first coefficient X and one second coefficient Y respectively.Same, when and time Y=-tan (Φ), mirror image signal can fully be eliminated.Φ herein represents that frequency is f ssingle-frequency test signal do not mate produced phase difference through the path of homophase (I) signal path 302 and orthogonal (Q) signal path 304, R is then for frequency is f ssingle-frequency test signal do not mate produced amplitude difference ratio through the path of homophase (I) signal path 202 and orthogonal (Q) signal path 304.
Next device of the present invention and related description will be described in detail, first please refer to Fig. 4, Fig. 4 is for correcting the schematic diagram of an embodiment of the unmatched a kind of means for correcting between one first signal path of a conveyer and one second signal path according to the present invention, wherein one of this first signal path and this second signal path is a homophase (I) signal path, and another of this first signal path and this second signal path is one orthogonal (Q) signal path.Conveyer 400 includes (such as part or all) at least partially of an electronic installation, and this electronic installation comprises at least one transfer circuit and at least one receiving circuit, and the example of this electronic installation can be including (but not limited to): multifunctional mobile telephone, intelligent mobile phone, personal digital assistant (Personal DigitalAssistant), personal computer (Personal Computer) such as (Laptop) computer on knee and desktop (Desktop) computer.Such as: conveyer 400 can represent the processing module in this electronic installation, a such as processor.Again such as: conveyer 400 can represent the entirety of this electronic installation.But this purposes only in order to illustrate, not limitation of the present invention, in fact, anyly can reach design that is same or similar functions, and other changes of invention spirit according to the invention, all belong to category of the present invention.According to a change case of the present embodiment, conveyer 400 can represent the system comprising this electronic installation, and this electronic installation is the subsystem of this system.Especially, this electronic installation can be and comprises OFDM modulation (Orthogonal FrequencyDivision Multiplexing, OFDM) electronic installation of circuit, wherein conveyer 400 can correct for above-mentioned OFDM modulation circuit; But the present invention is not as limit.
As shown in Figure 4, conveyer 400 includes: a frequency mixer test signal generation unit 402, one low pass filter test signal generation unit 404, one frequency mixer correction coefficient unit 406, one switch unit 408, one low pass filter correction coefficient unit 410, one tap coefficient calculation unit 412, one finite impulse response filter unit 414, one first digital analog converter 416, one second digital analog converter 418, one first low pass filter 420, one second low pass filter 422, one first frequency mixer 424, one second frequency mixer 426, one oscillator 428, one power amplifier 430, one receiving terminal 432, one spectral analysis unit 434, one frequency mixer correction coefficient adjustment unit 436 and a low pass filter correction coefficient adjustment unit 438.According to the present embodiment, conveyer 400 is each after restarting (after such as powering on or after system replacement), and before general data transfer mode formally starts, in order to a transmission end 440(that will improve conveyer 400 at least includes the first digital analog converter 416, second digital analog converter 418, first low pass filter 420, second low pass filter 422, first frequency mixer 424, second frequency mixer 426, oscillator 428) a homophase (I) signal path (namely pass through the first digital analog converter 416 in this transmission end, the path of the first low pass filter 420 and the first frequency mixer 424) orthogonal with one (Q) signal path (namely passes through the second digital analog converter 418 in this transmission end, the path of the second low pass filter 422 and the second frequency mixer 426) between not the mating of circuit characteristic, conveyer 400 can be introduced into a correction parameter computation schema, in other words, under this correction parameter computation schema, the first step can calculate for the correction parameter be optimized of the difference between this homophase signal path in the transmission end 440 of conveyer 400 and this orthogonal signal path, next carry out similar correction parameter to receiving terminal 432 again to calculate, transmission end 440 just can be allowed afterwards to enter general data transfer mode, and the correction parameter obtained under being simultaneously used in this correction parameter computation schema starts to carry out formal data and passes receipts.But, these are only the purposes of explanation, not limitation of the present invention, in fact, anyly can reach same or the design of similar functions or operation sequence, and other changes of invention spirit according to the invention, all belong to category of the present invention.For example, the first low pass filter 420, second low pass filter 422 in conveyer 400 can also be the filter of other functions.
Specifically, first correction emphasis of the present embodiment is be to add frequency mixer correction coefficient unit 406 in addition for the transmission end 440 of conveyer 400, frequency mixer correction coefficient unit 406 directly or indirectly can be coupled to the transmission end 440 of conveyer 400, and be set with one first frequency mixer correction coefficient X and one second frequency mixer correction coefficient Y, wherein the first frequency mixer correction coefficient X is positioned on this homophase signal path of transmission end 440, that is, the signal of this homophase signal path through transmission end 440 can be multiplied with the first frequency mixer correction coefficient X, and then corrected this homophase signal path caused due to the not matching component characteristic between the first signal path of transmission end 440 and the second signal path and do not mate with the amplitude between this quadrature phase signal path.And the second frequency mixer correction coefficient Y is for being coupled between this homophase signal path and this quadrature phase path, that is, the signal of this homophase signal path through transmission end 440 can be multiplied with the second frequency mixer correction coefficient Y, signal afterwards again with through this orthogonal signal path of transmission end 440 is added, and then is corrected this homophase signal path that the not matching component characteristic between the first signal path of transmission end 440 and the second signal path causes and do not mate with the phase place in this orthogonal signal path.But above details of operation and circuit design only supply the purposes of the explanation of the present embodiment, not limitation of the present invention, in fact also can use and exceed plural correction coefficient, so its corresponding complexity and precision also likely can change to some extent.Or contrary mode can be used arrange the first frequency mixer correction coefficient X and the second frequency mixer correction coefficient Y (that is, first frequency mixer correction coefficient X is for being positioned at this orthogonal signal path, second frequency mixer correction coefficient Y is coupled between this homophase signal path and this quadrature phase path, and signal is added and then betides this homophase signal path)).It should be noted, in this embodiment, the initial value of the first frequency mixer correction coefficient X can be set to 1, the initial value of the second frequency mixer correction coefficient Y can be set to 0, in other words, under desirable state, the value of the first frequency mixer correction coefficient X should be 1, and the value of the second frequency mixer correction coefficient Y should be 0.About deciding means and the details of the optimum value of the first frequency mixer correction coefficient X and the second frequency mixer correction coefficient Y, will illustrate in follow-up paragraph.
In addition, second correction emphasis of the present embodiment is for being that the transmission end 440 for conveyer 400 adds finite impulse response filter unit 414 in addition, finite impulse response filter unit 414 directly or indirectly can be coupled to the transmission end 440 of conveyer 400, and be used for utilizing one first finite impulse response filter (finite impulse response filter, FIRfilter) 4142 to carry out a homophase signal path finite impulse response (FIR) process to this homophase (I) signal path of transmission end 440 extraly; And utilize one second finite impulse response filter 4144 this orthogonal signal path to transmission end 440 to carry out an orthogonal signal path finite impulse response (FIR) process extraly.Through suitably design the first finite impulse response filter 4142 and the second finite impulse response filter 4144 respective multiple tap coefficients (tap coefficient), just the not matching and correlation between second low pass filter 422 in this orthogonal signal path of the first low pass filter 420 of this homophase signal path of the transmission end 440 of conveyer 400 and the first digital analog converter 416 and transmission end 440 and the second digital analog converter 418 can be returned.It should be noted, in this embodiment, multiple tap coefficients of the first finite impulse response filter 4142 and the second finite impulse response filter 4144 can be set to initial condition, can not be changed to make the signal content through the first finite impulse response filter 4142 and the second finite impulse response filter 4144.In other words, under desirable state, as long as those tap coefficients of the first finite impulse response filter 4142 and the second finite impulse response filter 4144 maintain initial value.About deciding means and the details of the optimum value of those tap coefficients of the first finite impulse response filter 4142 and the second finite impulse response filter 4144, will illustrate in follow-up paragraph.
First according to the present embodiment, error between lower of this correction parameter computation schema non-match error for process is the first frequency mixer 424 and the second frequency mixer 426, and the first low pass filter 420 and the first digital analog converter 416 and the error between the second low pass filter 422 and the second digital analog converter 418.Preceding paragraph is for operating in steady job frequency, that is a local oscillator frequencies f of oscillator 428 osc, can say comparatively simple; Consequent, different gains can be given for broader frequency band, can say comparatively loaded down with trivial details, therefore the present embodiment preferentially can calculate the numerical value of the first frequency mixer correction coefficient X and the second frequency mixer correction coefficient Y in frequency mixer correction coefficient unit 406, then processes for finite impulse response filter unit 414 on this basis again.Therefore, when calculating frequency mixer correction coefficient unit 406, except can first reset except frequency mixer correction coefficient unit 406, also those tap coefficients of the first finite impulse response filter 4142 in finite impulse response filter unit 414 and the second finite impulse response filter 4144 can be reset, in order to avoid change the signal through finite impulse response filter unit 414.In addition, because low pass filter correction coefficient unit 410 is only those tap coefficients for the first finite impulse response filter 4142 in aided solving finite impulse response filter unit 414 and the second finite impulse response filter 4144 in the present embodiment, in other words, only just need temporarily to use low pass filter correction coefficient unit 410 when calculating the tap coefficient in finite impulse response filter unit 414, therefore, no matter in the content calculating frequency mixer correction coefficient unit 406, or conveyer 400 is when general operation, capital as shown in Figure 4, switch 408 is set as bypass (bypass) low pass filter correction coefficient unit 410.But, the present invention is not limited with above-mentioned some related setting details, for example, when calculating the first frequency mixer correction coefficient X and the second frequency mixer correction coefficient Y of frequency mixer correction coefficient unit 406, also can first without direct finite impulse response filter unit 414, such as bypass finite impulse response filter unit 414, makes finite impulse response filter unit 414 can not have influence on the first frequency mixer correction coefficient X of frequency mixer correction coefficient unit 406 and the calculating of the second frequency mixer correction coefficient Y.Above-mentioned change like this, also all belongs to scope of the present invention.
Next, frequency mixer test signal generation unit 402 can produce one first frequency mixer and correct test signal TS1 and one second frequency mixer correction test signal TS2, it is single-frequency test signal that first frequency mixer corrects test signal TS1, and its frequency is the local oscillator frequencies f based on transmission end 440 oscadd a characteristic frequency f in addition again 0one first frequency mixer obtained corrects test frequency, and (frequency is f osc+ f 0); Similarly, it is also single-frequency test signal that the second frequency mixer corrects test signal TS2, and its frequency is this local oscillator frequencies f based on transmission end 440 oscdeduct characteristic frequency f in addition again 0one second frequency mixer obtained corrects test frequency, and (frequency is f osc-f 0).First, first frequency mixer corrects test signal TS1 can through frequency mixer correction coefficient unit 406, and walk around low pass filter correction coefficient unit 410 by switch unit 408, finite impulse response filter unit 414 afterwards again under initial condition, next through whole transmission end 440, then loopback (loopback) is to receiving terminal 432, by spectral analysis unit 434, spectrum analysis is carried out to it more afterwards, obtain a frequency mixer result of spectrum analysis, and this frequency mixer result of spectrum analysis at least comprises the information that the first frequency mixer corrects a mirror image (image) the signal size of test signal TS1.So frequency mixer correction coefficient adjustment unit 436 can adjust the first frequency mixer correction coefficient X, and can make the first frequency mixer correct test signal TS1 this mirror image signal present the first frequency mixer correction coefficient X of relative minimum as one first result X a; And adjustment the second frequency mixer correction coefficient Y, and this mirror image signal that the first frequency mixer can be made to correct test signal TS1 presents the second frequency mixer correction coefficient Y of relative minimum as one second result Y a.About the detailed operation of above adjustment the first frequency mixer correction coefficient X and the second frequency mixer correction coefficient Y, for example, certain pace can be used for base unit is to change its value, so in fact originally can appropriately adjust according to the one-tenth of the precision needed for application and synthesise various.
Hold, then the second frequency mixer correction test signal TS2 similarly can through frequency mixer correction coefficient unit 406, and walk around low pass filter correction coefficient unit 410 by switch unit 408, finite impulse response filter unit 414 afterwards again under initial condition and transmission end 440, then receiving terminal 432 is transmitted back to, by spectral analysis unit 434, spectrum analysis is carried out to obtain a frequency mixer result of spectrum analysis to it more afterwards, and this frequency mixer result of spectrum analysis at least comprises the information that the second frequency mixer corrects a mirror image (image) the signal size of test signal TS2.Finally, frequency mixer correction coefficient adjustment unit 436 can adjust the first frequency mixer correction coefficient X, and can make the second frequency mixer correct test signal TS2 this mirror image signal present the first frequency mixer correction coefficient X of relative minimum as one the 3rd result X b; And adjustment the second frequency mixer correction coefficient Y, and this mirror image signal that the second frequency mixer can be made to correct test signal TS2 presents the second frequency mixer correction coefficient Y of relative minimum as one the 4th result Y b.Finally, to the first result X aand the 3rd result X baverage and be used as the first final frequency mixer correction coefficient X, and to the second result Y aand the 4th result Y baverage and be used as the second final frequency mixer correction coefficient Y.This first frequency mixer correction coefficient X obtained and the second frequency mixer correction coefficient Y be for will for first frequency mixer correct test frequency (frequency will be f osc+ f 0) correction result and the second frequency mixer correct test frequency (frequency be f osc-f 0) correction result to be averaged obtained approximate correction result, can close to optimally correcting not mating between the frequency mixer 424 of this homophase signal path of transmission end 440 of conveyer 400 and the frequency mixer 426 in this orthogonal signal path of transmission end 440.
Next, then the error between lower process first low pass filter 420 and the second low pass filter 422 of this correction parameter computation schema is carried out according to the present embodiment.As previously mentioned, first finite impulse response filter 4142 of this homophase signal path being coupled to transmission end 440 is utilized in finite impulse response filter unit 414 to carry out this homophase signal path finite impulse response (FIR) process to this homophase signal path, and utilize the second finite impulse response filter 4144 being coupled to this orthogonal signal path of transmission end 440 in finite impulse response filter unit 414 to carry out this orthogonal signal path finite impulse response (FIR) process to this orthogonal signal path, to correct not mating between the first low pass filter 420 and the second low pass filter 422.In addition, it should be noted, because main object is be to compensate not mating between this homophase signal path and this orthogonal signal path, historical facts or anecdotes business can only use the first finite impulse response filter 4142 to compensate, and the second finite impulse response filter 4144 is fixed, a delay circuit string (delay chain) such as can be utilized to be used as the second finite impulse response filter 4144, wherein this delay circuit string only can carry out a signal delay process for this orthogonal signal path of transmission end 440, make to be equal to time of delay through the first finite impulse response filter 4142 through the time of delay of the second finite impulse response filter 4144, to avoid the mistake in sequential.
And about the adjustment of those tap coefficients of the first finite impulse response filter 4142 and the second finite impulse response filter 4144 process will details are as follows.First please refer to Fig. 5, Fig. 5 is the schematic diagram of another setting of this means for correcting of Fig. 4, switch unit 408 wherein in Fig. 4 is switched to connects another path, as shown in Figure 5, these multiple low pass filters being set as being used for specially calculating different frequency correct multiple results of the low pass filter correction coefficient unit 410 corresponding to test frequency, then according to counter those tap coefficients releasing the first finite impulse response filter 4142 and the second finite impulse response filter 4144 of those results.Therefore, under the setting of Fig. 5, switch unit 408 is switched to through low pass filter correction coefficient unit 410.Low pass filter correction coefficient unit 410 includes one first low pass filter correction coefficient W and one second low pass filter correction coefficient Z.Wherein the first low pass filter correction coefficient W is coupled to this homophase signal path being positioned at transmission end 440, and be used for correct conveyer 400 transmission end 440 this homophase signal path on the first low pass filter 420 and transmission end 440 this orthogonal signal path on the second low pass filter 422 between this caused homophase signal path that do not mate do not mate with the amplitude between this orthogonal signal path, and the second low pass filter correction coefficient Z be coupled to receiving terminal 440 between this homophase signal path and this quadrature phase path, and be used for correct conveyer 400 transmission end 440 this homophase signal path on the first low pass filter 420 and transmission end 440 this orthogonal signal path on the second low pass filter 422 between this caused homophase signal path that do not mate do not mate with the phase place between this orthogonal signal path.But above details of operation and circuit design only supply the purposes of the explanation of the present embodiment, not limitation of the present invention, in fact also can use and exceed plural correction coefficient, so its corresponding complexity and precision also likely can change to some extent.Or contrary mode can be used arrange the first low pass filter correction coefficient W and the second low pass filter correction coefficient Z (that is the first low pass filter correction coefficient W is positioned at orthogonal signal path, and the second low pass filter correction coefficient Z is coupled between this homophase signal path and quadrature phase path).
Hold, low pass filter test signal generation unit 404 can transmit N number of low pass filter test signal TSL 1~ TSL nwherein N can be the Arbitrary Digit being greater than zero, and through frequency mixer correction coefficient unit 406, low pass filter correction coefficient unit 410, finite impulse response filter unit 414 afterwards again under initial condition, transmission end 440, then receiving terminal 432 is recycled to, carry out spectrum analysis respectively to obtain multiple low pass filter result of spectrum analysis by spectral analysis unit 434 to it more afterwards, those low pass filter result of spectrum analysis at least comprise low pass filter and correct test signal TSL 1~ TSL ndistinguish the information of corresponding multiple mirror image signal sizes.It should be noted, low pass filter test signal TSL 1~ TSL nbe respectively the signal with single-frequency, thus there is low pass filter and correct test frequency f tsl1~ f tslN, and owing to only needing to consider the situation of transmitter and receiver 400 under general operation, therefore low pass filter corrects test frequency f tsl1~ f tslNcan be positioned at conveyer 400 under general modfel for process frequency band range within.Low pass filter test signal TSL 1~ TSL nnumber and low pass filter correct test frequency f tsl1~ f tslNselection directly can have influence on the accuracy of the calibration capability of the first finite impulse response filter 4142 in final finite impulse response filter unit 414 and the second finite impulse response filter 4144, therefore visual demand and comprehensive various cost consideration design the tap number of the first finite impulse response filter 4142 and the second finite impulse response filter 4144 and distribute these low pass filters and correct test frequency f tsl1~ f tslN.
For each low pass filter test signal TSL 1~ TSL n, low pass filter correction coefficient adjustment unit 438 can adjust the first low pass filter correction coefficient W, and low pass filter can be made to test signal TSL 1~ TSL neach this mirror image signal self-corresponding present the first low pass filter correction coefficient W of relative minimum as first low pass filter result W1 ~ WN; And adjustment the second low pass filter correction coefficient Z, and low pass filter can be made to test signal TSL 1~ TSL neach this mirror image signal self-corresponding present the second low pass filter correction coefficient Z of relative minimum as the second low pass filter result Z 1~ Z n.And after all above-mentioned steps has been carried out to each low pass filter test signal, just can obtain multiple first low pass filter result and multiple second low pass filter result.Next step, tap coefficient calculation unit 412 just can utilize the first low pass filter result W 1~ W nand the second low pass filter result Z 1~ Z ncalculate those tap coefficients of the first finite impulse response filter 4142 and the second finite impulse response filter 4144 respectively, process will be described below.
An orthogonal signal path frequencies RESPONSE CALCULATION unit 4122 in tap coefficient calculation unit 412 first can carry out Fu Liye conversion (Fourier transform) for second finite impulse response filter 4144 in this orthogonal signal path, and practice can correct test frequency f at low pass filter respectively for the second finite impulse response filter 4144 tsl1~ f tslNcarry out fast fourier conversion (fast Fourier transform, FFT) of N point, obtain the second finite impulse response filter 4144 corresponding low pass filter correction test frequency f to ask respectively tsl1~ f tslNmultiple frequency response B1 ~ BN.Following equation (3) can be derived according to equation (1), (2), namely utilize one first homophase signal path frequency response computing unit 4124 in tap coefficient calculation unit 412 haply, and according to multiple orthogonal signal path frequencies response B 1~ B n, and corresponding low pass filter corrects test frequency f tsl1~ f tslNthe first low pass filter result W 1~ W nand the second low pass filter result Z 1~ Z nobtain homophase signal path frequency response A 1~ A n.
A i = B i × 1 R i × exp ( - jΦ ) = B i × W i × cos ( - arctan ( Z i ) ) × exp ( j arctan ( Z i ) ) , Wherein i=1 ~ N (3)
Fig. 6 is the schematic diagram of the embodiment according to the first homophase signal path frequency response computing unit of the present invention.It should be noted, the first homophase signal path frequency response computing unit in Fig. 6 is for carrying out computing according to equation (3).And in fact, equation (3) can further use approximate method again and is following equation (4) by abbreviation:
A i = B i × W i × cos ( - arctan ( Z i ) ) × exp ( j arctan ( Z i ) ) ~ = B i × W i × cos ( Z i ) × ( cos ( Z i ) + j sin ( Z i ) ) ~ = B i × W i × ( 1 - Z i 2 2 ) ( ( 1 - Z i 2 2 ) + j Z i ) , , Wherein i=1 ~ N (4)
Fig. 7 is the schematic diagram of another embodiment according to the first homophase signal path frequency response computing unit of the present invention.It should be noted, the first homophase signal path frequency response computing unit in Fig. 7 is for carrying out computing according to equation (4).
Obtaining homophase signal path frequency response A 1~ A nafterwards, the coefficient calculation unit 4126 in tap coefficient calculation unit 412 just can for foundation homophase signal path frequency response A 1~ A ncarry out Fu Li leaf inverse transform (inverse Fourier transform), and real part is got to the result of Fu Li leaf inverse transform, to obtain those tap coefficients of the first finite impulse response filter 4142.In practice, can for homophase signal path frequency response A 1~ A ncarry out fast fourier inverse transform (inverse fast Fourier transform, iFFT), and real part is got to the result of fast fourier inverse transform, to obtain those tap coefficients of the first finite impulse response filter 4142.
According to above deduction, the content of the finite impulse response filter unit 414 finally obtained can be the first finite impulse response filter 4142, and those tap coefficients have wherein calculated as above; And second finite impulse response filter 4144, it is have the delay circuit string with the first finite impulse response filter 4142 same delay time as above-mentioned.Arrive this, obtain the correction parameter that is necessary of transmission end 440 in the present embodiment, as long as afterwards switch unit 408 is switched back the setting shown in Fig. 4, then conveyer 400 just can perform general data and pass receipts, unlike, due to the correction through frequency mixer correction coefficient unit 406 and finite impulse response filter unit 414, now the performance of transmission end 440 is by the performance before being better than not correcting.
Please refer to Fig. 8, Fig. 8 is for correcting the schematic diagram of another embodiment of the unmatched a kind of means for correcting between one first signal path of a conveyer and one second signal path according to the present invention, wherein one of this first signal path and this second signal path is a homophase (I) signal path, and another of this first signal path and this second signal path is one orthogonal (Q) signal path.Can directly in order to replace orthogonal signal path frequencies RESPONSE CALCULATION unit 4122 in the tap coefficient calculation unit 412 in conveyer 400 and the first homophase signal path frequency response computing unit 4124 unlike, the second homophase signal path frequency response computing unit 8124 in the tap coefficient calculation unit 812 in the conveyer 800 in Fig. 8 with conveyer 400.In addition, all exchange unit 805 are set before frequency mixer correction coefficient unit 406.It should be noted, Fig. 8 is the setting for obtaining the first frequency mixer correction coefficient X and the second frequency mixer correction coefficient Y, wherein the setting of switch unit 805 and switch unit 408 as shown in the figure, in other words, the test signal that produces of frequency mixer test signal generation unit 402 now can through frequency mixer correction coefficient unit 406, but can not through low pass filter correction coefficient unit 410.Fig. 9 is the schematic diagram of another setting of the means for correcting of Fig. 8, switch unit 805 wherein in Fig. 8 and switch unit 408 are switched to respectively connects another path, that is, the test signal that produces of frequency mixer test signal generation unit 402 now can not through frequency mixer correction coefficient unit 406, but can through low pass filter correction coefficient unit 410.The operation of related setting and switching refer to the description about Fig. 4 and Fig. 5 above, just seldom repeat at this.For tap coefficient calculation unit 812, compared to the change of the tap coefficient calculation unit 412 in previous embodiment, according to equation (5), tap coefficient calculation unit 812 can correct test frequency f by the corresponding low pass filter of direct basis tsl1~ f tslNthe first low pass filter result W 1~ W nand the second low pass filter result Z 1~ Z nand first frequency mixer correction coefficient X and the second frequency mixer correction coefficient Y obtain homophase signal path frequency response A 1~ A n.
A i = W i 1 + Z i ( 1 + jY ) ( 1 - j Z i ) X - 1 = cos 2 ( arctan ( Z i ) ) W i ( 1 + jY ) ( 1 - j Z i ) X - 1 , Wherein i=1 ~ N (5)
Figure 10 is the schematic diagram of the embodiment according to the second homophase signal path frequency response computing unit of the present invention.It should be noted, the second homophase signal path frequency response computing unit in Figure 10 is for carrying out computing according to equation (5).And in fact, the cos in equation (5) 2(arctan (Z i)) can further use Taylor expansion (Taylor series) to expand into (1-Z again i 2+ Z i 4+ ...), in order to reduce the complexity of computing, only can get first three items to be used as approximation at this, therefore equation (5) can be following equation (6) by abbreviation:
A i = cos 2 ( arctan ( Z i ) ) W i ( 1 + jY ) ( 1 - j Z i ) X - 1 ≈ ( 1 - Z i 2 2 + 3 8 W i 4 ) 2 W i ( 1 + jY ) ( 1 - j Y i ) X - 1 ≈ ( 1 - Z i 2 + Z i 4 ) ( 1 + jY ) ( 1 - j Z i ) = W i X - 1 ( 1 - Z i 2 + Z i 4 ) ( 1 + Y Z i + j ( Y - Z i ) ) , Wherein i=1 ~ N (6)
Figure 11 is the schematic diagram of another embodiment according to the second homophase signal path frequency response computing unit of the present invention.It should be noted, the second homophase signal path frequency response computing unit in Figure 11 is for carrying out computing according to equation (6).
Figure 12 is for correcting the flow chart of an embodiment of the unmatched a kind of bearing calibration between one first signal path of a conveyer and one second signal path according to the present invention, wherein one of this first signal path and this second signal path is a homophase (I) signal path, and another of this first signal path and this second signal path is one orthogonal (Q) signal path.If identical result can be reached substantially, might not need to carry out according to the sequence of steps in the flow process shown in Figure 12, and the step shown in Figure 12 not necessarily will be carried out continuously, that is other steps also can be inserted wherein.In addition, some step in Figure 12 can according to different embodiment or design requirement abridged.The bearing calibration of Figure 12 can be applicable to the conveyer 400 shown in Fig. 4 and Fig. 5.Detailed step is as follows:
Step 1202: at least one frequency mixer correction coefficient of a transmission end extra setup of this conveyer;
Step 1204: at least one frequency mixer test signal is produced one first from this transmission end through this at least one frequency mixer correction coefficient and transmits signal, and this first transmission signal of loopback (loopback) carries out spectrum analysis to obtain at least one frequency mixer result of spectrum analysis;
Step 1206: adjust this at least one frequency mixer correction coefficient according to this at least one frequency mixer result of spectrum analysis, to obtain this final at least one frequency mixer correction coefficient, with not mating between a frequency mixer of the frequency mixer and this second signal path that correct this first signal path;
Step 1208: set at least one filter correction coefficient in this transmission end of this conveyer;
Step 1210: at least one filters to test signal is produced one second from this transmission end through this at least one frequency mixer correction coefficient and this at least one filter correction coefficient and transmits signal, and this second transmission signal of loopback (loopback) carries out spectrum analysis, obtains at least one filter spectrum analysis result;
Step 1212: this at least one filter correction coefficient adjusting this transmission end according to this at least one filter spectrum analysis result;
Step 1214: utilize a delay circuit string (delay chain) to be used as this second signal path finite impulse response filter, and this delay circuit string is for carry out a signal delay process for this second signal path, the time of delay of this first signal path finite impulse response (FIR) process for corresponding to this first signal path finite impulse response filter and carrying out time of delay of wherein this signal delay process;
Step 1216: obtain at least one second signal path frequency response of this second signal path finite impulse response filter respectively on this at least one filter correction test frequency;
Step 1218: according to this at least one second signal path frequency response, to should this at least one first filter correction coefficient results of at least one filter correction test frequency and this at least one second filter correction coefficient results, obtain at least one first signal path frequency response;
Step 1220: this at least one tap coefficient obtaining this first signal path finite impulse response filter according to this at least one first signal path frequency response; And
Step 1222: without this at least one filter correction coefficient, through this first signal path finite impulse response filter, this first signal path finite impulse response (FIR) process is carried out, with not mating between this filter of this filter and this second signal path of correcting this first signal path to this first signal path.
Have the knack of this field person after reading the detailed description herein a little earlier for the conveyer 400 shown in Fig. 4 and Fig. 5, clearly should be able to understand the step 1202 ~ step 1222 of the bearing calibration of Figure 12, therefore be for purpose of brevity, be not just further described for details wherein at this.
Figure 13 is for correcting the flow chart of another embodiment of the unmatched a kind of bearing calibration between one first signal path of a conveyer and one second signal path according to the present invention.If identical result can be reached substantially, might not need to carry out according to the sequence of steps in the flow process shown in Figure 13, and the step shown in Figure 13 not necessarily will be carried out continuously, that is other steps also can be inserted wherein.In addition, some step in Figure 13 can according to different embodiment or design requirement abridged.The bearing calibration of Figure 13 can be applicable to the conveyer 800 shown in Fig. 8 and Fig. 9.Detailed step is as follows:
Step 1202: at least one frequency mixer correction coefficient of a transmission end extra setup of this conveyer;
Step 1204: at least one frequency mixer test signal is produced one first from this transmission end through this at least one frequency mixer correction coefficient and transmits signal, and this first transmission signal of loopback (loopback) carries out spectrum analysis to obtain at least one frequency mixer result of spectrum analysis;
Step 1206: adjust this at least one frequency mixer correction coefficient according to this at least one frequency mixer result of spectrum analysis, to obtain this final at least one frequency mixer correction coefficient, with not mating between a frequency mixer of the frequency mixer and this second signal path that correct this first signal path;
Step 1208: set at least one filter correction coefficient in this transmission end of this conveyer;
Step 1310: at least one filters to test signal is produced one second transmission signal from this transmission end without this at least one frequency mixer correction coefficient and through this at least one filter correction coefficient, and this second transmission signal of loopback (loopback) carries out spectrum analysis, obtains at least one filter spectrum analysis result;
Step 1212: this at least one filter correction coefficient adjusting this transmission end according to this at least one filter spectrum analysis result;
Step 1214: utilize a delay circuit string (delay chain) to be used as this second signal path finite impulse response filter, and this delay circuit string is for carry out a signal delay process for this second signal path, the time of delay of this first signal path finite impulse response (FIR) process for corresponding to this first signal path finite impulse response filter and carrying out time of delay of wherein this signal delay process;
Step 1316: obtain the frequency response of at least one homophase signal path according to this first filter results and this second filter results and frequency mixer correction coefficient;
Step 1318: this at least one tap coefficient obtaining this first signal path finite impulse response filter according to this at least one first signal path frequency response; And
Step 1222: without this at least one filter correction coefficient, through this first signal path finite impulse response filter, this first signal path finite impulse response (FIR) process is carried out, with not mating between this filter of this filter and this second signal path of correcting this first signal path to this first signal path.
Have the knack of this field person after reading the detailed description herein a little earlier for the conveyer 800 shown in Fig. 8 and Fig. 9, clearly should be able to understand the step 1202 ~ step 1214 of the bearing calibration of Figure 13, step 1320 ~ step 1322 and step 1222, therefore be for purpose of brevity, be not just further described for details wherein at this.
Next, please refer to Figure 14, Figure 14 is for correcting the schematic diagram of an embodiment of the unmatched a kind of means for correcting between one first signal path of a receiver and one second signal path according to the present invention, wherein this one of first signal path and this second signal path are a homophase (I) signal path, and another of this first signal path and this second signal path is one orthogonal (Q) signal path.Receiver 1400 includes (such as part or all) at least partially of an electronic installation, and this electronic installation comprises at least one transfer circuit and at least one receiving circuit, and the example of this electronic installation can be including (but not limited to): multifunctional mobile telephone, intelligent mobile phone, personal digital assistant (Personal Digital Assistant), personal computer (Personal Computer) such as (Laptop) computer on knee and desktop (Desktop) computer.Such as: receiver 1400 can represent the processing module in this electronic installation, a such as processor.Again such as: receiver 1400 can represent the entirety of this electronic installation.But this purposes only in order to illustrate, not limitation of the present invention, in fact, anyly can reach design that is same or similar functions, and other changes of invention spirit according to the invention, all belong to category of the present invention.According to a change case of the present embodiment, receiver 1400 can represent the system comprising this electronic installation, and this electronic installation is the subsystem of this system.Especially, this electronic installation can be and comprises OFDM modulation (Orthogonal Frequency Division Multiplexing, OFDM) electronic installation of circuit, wherein receiver 1400 can correct for above-mentioned OFDM modulation circuit; But the present invention is not as limit.
As shown in figure 14, receiver 1400 includes: a frequency mixer test signal generation unit 1402, one low pass filter test signal generation unit 1404, one frequency mixer correction coefficient unit 1406, one switch unit 1408, 1505, one low pass filter correction coefficient unit 1410, one tap coefficient calculation unit 1412, one finite impulse response filter unit 1414, one first analog-digital converter 1416, one second analog-digital converter 1418, one first low pass filter 1420, one second low pass filter 1422, one first frequency mixer 1424, one second frequency mixer 1426, one oscillator 1428, one low noise amplifier 1430, one transmission end 1432, one spectral analysis unit 1434, one frequency mixer correction coefficient adjustment unit 1436 and a low pass filter correction coefficient adjustment unit 1438.According to the present embodiment, receiver 1400 is each after restarting (after such as powering on or after system replacement), and before general data receive mode formally starts, in order to a receiving terminal 1440(that will improve receiver 1400 at least includes the first analog-digital converter 1416, second analog-digital converter 1418, first low pass filter 1420, second low pass filter 1422, first frequency mixer 1424, second frequency mixer 1426, oscillator 1428) a homophase (I) signal path (the first frequency mixer 1424 namely in receiving terminal 1440, the path of the first low pass filter 1420 and the first analog-digital converter 1416) orthogonal with one (Q) signal path (the second frequency mixer 1426 namely in receiving terminal 1440, the path of the second low pass filter 1422 and the second analog-digital converter 1418) between not the mating of circuit characteristic, receiver 1400 can be introduced into a correction parameter computation schema, in other words, under this correction parameter computation schema, can calculate for the correction parameter be optimized of the difference between this homophase signal path in the receiving terminal 1440 of receiver 1400 and this orthogonal signal path, receiving terminal 1440 just can be allowed afterwards to enter general data receive mode, and the correction parameter obtained under being simultaneously used in this correction parameter computation schema starts to carry out formal data receiver.But this purposes only in order to illustrate, not limitation of the present invention, in fact, anyly can reach same or the design of similar functions or operation sequence, and other changes of invention spirit according to the invention, all belong to category of the present invention.
For the first frequency mixer 1424 of the receiving terminal 1440 of the receiver 1400 of Figure 14, second frequency mixer 1426 and the first low pass filter 1420, the correction principle of the second low pass filter 1422 is approximately identical to the first frequency mixer 424 of the transmission end 440 of the conveyer 400 of Fig. 4, second frequency mixer 426 and the first low pass filter 420, the correction principle of the second low pass filter 422, and have the knack of this field person after reading the detailed description herein a little earlier for the conveyer 400 shown in Fig. 4 and Fig. 5, clearly should be able to understand the details of operation of the receiver 1400 of Figure 14, therefore be for purpose of brevity, just be not further described for details wherein at this.
Figure 15 is for correcting the schematic diagram of another embodiment of the unmatched a kind of means for correcting between one first signal path of a receiver and one second signal path according to the present invention, wherein one of this first signal path and this second signal path is a homophase (I) signal path, and another of this first signal path and this second signal path is one orthogonal (Q) signal path.Can directly in order to replace orthogonal signal path frequencies RESPONSE CALCULATION unit 14122 in the tap coefficient calculation unit 1412 in receiver 1400 and the first homophase signal path frequency response computing unit 14124 unlike, the second homophase signal path frequency response computing unit 15124 in the tap coefficient calculation unit 1512 in the receiver 1500 in Figure 15 with receiver 1400.Abbreviation principle for the tap coefficient calculation unit 1512 of the receiving terminal 1440 of the receiver 1500 of Figure 15 is approximately identical to the correction principle of the tap coefficient calculation unit 812 of the conveyer 800 of Fig. 8, and have the knack of this field person after reading the detailed description herein a little earlier for Fig. 8 and 10th ~ 11 figure, clearly should be able to understand the details of operation of the second homophase signal path frequency response computing unit 15124 of Figure 15, therefore be for purpose of brevity, be not just further described for details wherein at this.
Figure 16 is for correcting the flow chart of an embodiment of the unmatched a kind of bearing calibration between one first signal path of a receiver and one second signal path according to the present invention, wherein one of this first signal path and this second signal path is a homophase (I) signal path, and another of this first signal path and this second signal path is one orthogonal (Q) signal path.If identical result can be reached substantially, might not need to carry out according to the sequence of steps in the flow process shown in Figure 16, and the step shown in Figure 16 not necessarily will be carried out continuously, that is other steps also can be inserted wherein.In addition, some step in Figure 16 can according to different embodiment or design requirement abridged.The bearing calibration of Figure 16 can be applicable to the receiver 1400 shown in Figure 14.Detailed step is as follows:
Step 1602: at least one frequency mixer correction coefficient of a receiving terminal extra setup of this receiver;
Step 1604: being exported from a transmission end of this receiver by least one frequency mixer test signal is one first transmission signal, and this of returning in loopback (loopback) first transmits signal after this at least one frequency mixer correction coefficient, carries out spectrum analysis to obtain at least one frequency mixer result of spectrum analysis to it;
Step 1606: this at least one frequency mixer correction coefficient adjusting this receiving terminal according to this at least one frequency mixer result of spectrum analysis, to obtain this final at least one frequency mixer correction coefficient, with not mating between a frequency mixer in this orthogonal signal path of the frequency mixer and this receiving terminal that correct this homophase signal path of this receiving terminal of this conveyer;
Step 1608: except this frequency mixer correction coefficient original, set at least one filter correction coefficient in this receiving terminal in addition;
Step 1610: being exported from this transmission end of this receiver by least one filters to test signal is one second transmission signal, and this of returning in loopback (loopback) second transmits signal after this at least one frequency mixer correction coefficient and this at least one filter correction coefficient of this receiving terminal, carries out spectrum analysis to obtain at least one filter spectrum analysis result to it;
Step 1612: this at least one filter correction coefficient adjusting this receiving terminal according to this at least one filter spectrum analysis result;
Step 1614: utilize a delay circuit string (delay chain) to be used as this second signal path finite impulse response filter, and this delay circuit string is for carry out a signal delay process for this second signal path, the time of delay of this first signal path finite impulse response (FIR) process for corresponding to this first signal path finite impulse response filter and carrying out time of delay of wherein this signal delay process;
Step 1616: obtain at least one second signal path frequency response of this second signal path finite impulse response filter respectively on this at least one filter correction test frequency;
Step 1618: according to this at least one second signal path frequency response and to this at least one first filter correction coefficient results of at least one filter correction test frequency and this at least one second filter correction coefficient results obtaining at least one first signal path frequency response;
Step 1620: this at least one tap coefficient obtaining this first signal path finite impulse response filter according to this at least one first signal path frequency response; And
Step 1622: without this at least one filter correction coefficient, through this first signal path finite impulse response filter, this first signal path finite impulse response (FIR) process is carried out, with not mating between this filter of this filter and this second signal path of correcting this first signal path to this first signal path.
Have the knack of this field person after reading the detailed description (detailed description of such as Fig. 4 and Fig. 5) herein a little earlier for the receiver 1400 shown in Figure 14, clearly should be able to understand the step 1602 ~ step 1622 of the bearing calibration of Figure 16, therefore be for purpose of brevity, be not just further described for details wherein at this.
Figure 17 is for correcting the flow chart of another embodiment of the unmatched a kind of bearing calibration between one first signal path of a receiver and one second signal path according to the present invention, wherein one of this first signal path and this second signal path is a homophase (I) signal path, and another of this first signal path and this second signal path is one orthogonal (Q) signal path.If identical result can be reached substantially, might not need to carry out according to the sequence of steps in the flow process shown in Figure 17, and the step shown in Figure 17 not necessarily will be carried out continuously, that is other steps also can be inserted wherein.In addition, some step in Figure 17 can according to different embodiment or design requirement abridged.The bearing calibration of Figure 17 can be applicable to the receiver 1500 shown in Figure 15.Detailed step is as follows:
Step 1602: at least one frequency mixer correction coefficient of a receiving terminal extra setup of this receiver;
Step 1604: being exported from a transmission end of this receiver by least one frequency mixer test signal is one first transmission signal, and this of returning in loopback (loopback) first transmits signal after this at least one frequency mixer correction coefficient, carries out spectrum analysis to obtain at least one frequency mixer result of spectrum analysis to it;
Step 1606: this at least one frequency mixer correction coefficient adjusting this receiving terminal according to this at least one frequency mixer result of spectrum analysis, to obtain this final at least one frequency mixer correction coefficient, with not mating between a frequency mixer in this orthogonal signal path of the frequency mixer and this receiving terminal that correct this homophase signal path of this receiving terminal of this conveyer;
Step 1608: except this frequency mixer correction coefficient original, set at least one filter correction coefficient in this receiving terminal in addition;
Step 1710: being exported from this transmission end of this receiver by least one filters to test signal is one second transmission signal, and this second transmission signal making loopback (loopback) return is without this at least one frequency mixer correction coefficient of this receiving terminal and after this at least one filter correction coefficient, carries out spectrum analysis to obtain at least one filter spectrum analysis result to it;
Step 1612: this at least one filter correction coefficient adjusting this receiving terminal according to this at least one filter spectrum analysis result;
Step 1614: utilize a delay circuit string (delay chain) to be used as this second signal path finite impulse response filter, and this delay circuit string is for carry out a signal delay process for this second signal path, the time of delay of this first signal path finite impulse response (FIR) process for corresponding to this first signal path finite impulse response filter and carrying out time of delay of wherein this signal delay process;
Step 1716: obtain at least one first signal path frequency response according to this first filter results and this second filter results and this frequency mixer correction coefficient;
Step 1718: this at least one tap coefficient obtaining this first signal path finite impulse response filter according to this at least one first signal path frequency response; And
Step 1622: without this at least one filter correction coefficient, through this first signal path finite impulse response filter, this first signal path finite impulse response (FIR) process is carried out, with not mating between this filter of this filter and this second signal path of correcting this first signal path to this first signal path.
Have the knack of this field person after reading the detailed description (such as the detailed description of Fig. 8 and 10th ~ 11 figure) herein a little earlier for the receiver 1500 shown in Figure 15, clearly should be able to understand the step 1602 ~ step 1614 of the bearing calibration of Figure 17, step 1720 ~ step 1722 and step 1622, therefore be for purpose of brevity, be not just further described for details wherein at this.
The main spirit of the present invention be can above method and device compensate a conveyer a homophase (I) signal path orthogonal with one (Q) signal path between do not mate, especially can compensate this homophase signal path of this conveyer and not mating between this orthogonal signal path frequency mixer separately; And compensate this homophase signal path of this conveyer and not mating between this orthogonal signal path low pass filter separately.Not mating by after adequate compensation/correction between homophase signal path with orthogonal signal path, electronic installation just can obtain preferably communication usefulness.

Claims (76)

1. a signal bearing calibration, for correcting one first signal path of a conveyer and not mating between one second signal path, wherein this one of first signal path and this second signal path are a homophase signal path, another of this first signal path and this second signal path is an orthogonal signal path, it is characterized in that, this bearing calibration includes:
In at least one frequency mixer correction coefficient of a transmission end extra setup of this conveyer;
Produce one first according at least one frequency mixer test signal and this at least one frequency mixer correction coefficient and transmit signal, and this first transmission signal of loopback carries out spectrum analysis to obtain at least one frequency mixer result of spectrum analysis;
This at least one frequency mixer correction coefficient is adjusted according to this at least one frequency mixer result of spectrum analysis, to obtain an end value of this at least one frequency mixer correction coefficient, with not mating between one second frequency mixer of one first frequency mixer and this second signal path that correct this first signal path; And
One first signal path finite impulse response filter is additionally utilized to carry out one first signal path finite impulse response (FIR) process to this first signal path, and additionally utilize one second signal path finite impulse response filter to carry out one second signal path finite impulse response (FIR) process to this second signal path, with not mating between one second filter of one first filter and this second signal path that correct this first signal path.
2. method as claimed in claim 1, wherein this conveyer is an OFDM modulation conveyer.
3. method as claimed in claim 1, wherein this at least one frequency mixer correction coefficient at least includes one first frequency mixer correction coefficient and one second frequency mixer correction coefficient, and wherein this first frequency mixer correction coefficient is do not mate for the amplitude corrected between this first signal path with this second signal path; And this second frequency mixer correction coefficient is do not mate with the phase place of this second signal path for correcting this first signal path.
4. method as claimed in claim 3, wherein this at least one frequency mixer test signal includes one first frequency mixer correction test signal and one second frequency mixer correction test signal, and this first frequency mixer correction test signal has one first frequency mixer correction test frequency, this second frequency mixer corrects test signal and has one second frequency mixer correction test frequency; And this first frequency mixer corrects test frequency is that to add that a characteristic frequency and this second frequency mixer correct test frequency be that this local oscillator frequencies of this transmission end deducts this characteristic frequency for a local oscillator frequencies of this transmission end.
5. method as claimed in claim 4, wherein adjusts this at least one frequency mixer correction coefficient according to this at least one frequency mixer result of spectrum analysis, includes with the step obtaining this final at least one frequency mixer correction coefficient:
Adjust this first frequency mixer correction coefficient, and a mirror image signal that this first frequency mixer can be made to correct test signal presents this first frequency mixer correction coefficient of relative minimum as one first result;
Adjust this second frequency mixer correction coefficient, and this mirror image signal that this first frequency mixer can be made to correct test signal presents this second frequency mixer correction coefficient of relative minimum as one second result;
Adjust this first frequency mixer correction coefficient, and a mirror image signal that this second frequency mixer can be made to correct test signal presents this first frequency mixer correction coefficient of relative minimum as one the 3rd result;
Adjust this second frequency mixer correction coefficient, and this mirror image signal that this second frequency mixer can be made to correct test signal presents this second frequency mixer correction coefficient of relative minimum as one the 4th result; And
Produce this final the first frequency mixer correction coefficient according to this first result and the 3rd result, and produce this final the second frequency mixer correction coefficient according to this second result and the 4th result.
6. method as claimed in claim 1, the step wherein additionally utilizing this first signal path finite impulse response filter this first signal path to this transmission end to carry out this first signal path finite impulse response (FIR) process includes:
At least one filter correction coefficient is set in this transmission end of this conveyer;
Produce one second according at least one filters to test signal and this at least one filter correction coefficient and transmit signal, and this second transmission signal of loopback carries out spectrum analysis, obtains at least one filter spectrum analysis result;
This at least one filter correction coefficient of this transmission end is adjusted according to this at least one filter spectrum analysis result;
At least one tap coefficient of this first signal path finite impulse response filter of this transmission end is obtained according to this at least one filter correction coefficient after adjustment; And
Without this at least one filter correction coefficient, this the first signal path finite impulse response (FIR) process is carried out to this first signal path, with not mating between this second filter of this first filter and this second signal path of correcting this first signal path through this first signal path finite impulse response filter.
7. method as claimed in claim 6, the step wherein additionally utilizing this second signal path finite impulse response filter this second signal path to this transmission end to carry out this second signal path finite impulse response (FIR) process separately includes:
Utilize a delay circuit string to be used as this second signal path finite impulse response filter, and this delay circuit string is for carry out a signal delay process for this second signal path, the time of delay of this first signal path finite impulse response (FIR) process for corresponding to this first signal path finite impulse response filter and carrying out time of delay of wherein this signal delay process.
8. method as claimed in claim 6, wherein produces this second step transmitting signal according to this at least one filters to test signal and this at least one filter correction coefficient and includes:
This at least one filters to test signal is produced this second transmission signal from this transmission end through this at least one frequency mixer correction coefficient and this at least one filter correction coefficient.
9. method as claimed in claim 8, wherein this at least one filter correction coefficient at least includes one first filter correction coefficient and one second filter correction coefficient; This first filter correction coefficient is do not mate for the amplitude corrected between this first signal path with this second signal path; And this second filter correction coefficient is do not mate for the phase place corrected between this first signal path with this second signal path.
10. method as claimed in claim 9, wherein this at least one filters to test signal has at least one filter correction test frequency, and this at least one filter correction test frequency is by within the frequency band range that is positioned at this conveyer institute wish and processes.
11. as the method for claim 10, and the step wherein adjusting this at least one filter correction coefficient of this transmission end according to this at least one filter spectrum analysis result includes:
Adjust this first filter correction coefficient, and a mirror image signal of this at least one filters to test signal can be made to present this first filter correction coefficient of relative minimum as at least one first filter correction coefficient results; And
Adjust this second filter correction coefficient, and this mirror image signal of this at least one filters to test signal can be made to present this second filter correction coefficient of relative minimum as at least one second filter correction coefficient results.
12. as the method for claim 11, and the step wherein obtaining this at least one tap coefficient of this first signal path finite impulse response filter according to this at least one filter correction coefficient after adjustment includes:
Obtain at least one second signal path frequency response of this second signal path finite impulse response filter respectively on this at least one filter correction test frequency;
According to this at least one second signal path frequency response, to should this at least one first filter correction coefficient results of at least one filter correction test frequency and this at least one second filter correction coefficient results, obtain at least one first signal path frequency response; And
This at least one tap coefficient of this first signal path finite impulse response filter is obtained according to this at least one first signal path frequency response.
13. as the method for claim 12, wherein in the step of this at least one second signal path frequency response of this second signal path finite impulse response filter respectively on this at least one filter correction test frequency obtaining this transmission end, for at least one tap coefficient for this second signal path finite impulse response filter carries out Fu Liye conversion, to obtain this at least one second signal path frequency response respectively on this at least one filter correction test frequency of this second signal path finite impulse response filter; And obtain in the step of this at least one tap coefficient of this first signal path finite impulse response filter in the first signal path frequency response at least one according to this, for carrying out Fu Li leaf inverse transform for this at least one first signal path frequency response, and real part is got to the result of Fu Li leaf inverse transform, to obtain this at least one tap coefficient of this first signal path finite impulse response filter of this transmission end.
14. methods as claimed in claim 6, wherein produce this second step of transmitting signal from this transmission end through this at least one filter correction coefficient by this at least one filters to test signal and include:
This at least one filters to test signal is produced this second transmission signal from this transmission end without this at least one frequency mixer correction coefficient and through this at least one filter correction coefficient.
15. as the method for claim 14, and wherein this at least one filter correction coefficient at least includes one first filter correction coefficient and one second filter correction coefficient; This first filter correction coefficient is do not mate for the amplitude corrected between this first signal path with this second signal path; And this second filter correction coefficient is do not mate for the phase place corrected between this first signal path with this second signal path.
16. as the method for claim 15, and wherein this at least one filters to test signal has at least one filter correction test frequency, and this at least one filter correction test frequency by be positioned at this conveyer wish process frequency band range within.
17. as the method for claim 16, and the step wherein adjusting this at least one filter correction coefficient of this transmission end according to this at least one filter spectrum analysis result includes:
Adjust this first filter correction coefficient, and a mirror image signal of this at least one filters to test signal can be made to present this first filter correction coefficient of relative minimum as at least one first filter results; And
Adjust this second filter correction coefficient, and this mirror image signal of this at least one filters to test signal can be made to present this second filter correction coefficient of relative minimum as at least one second filter results.
18. as the method for claim 17, and the step wherein obtaining this at least one tap coefficient of this first signal path finite impulse response filter according to this at least one filter correction coefficient after adjustment also includes:
At least one first signal path frequency response is obtained according to this first filter results and this second filter results; And
This at least one tap coefficient of this first signal path finite impulse response filter is obtained according to this at least one first signal path frequency response.
19. as the method for claim 18, wherein obtain in the step of this at least one tap coefficient of this first signal path finite impulse response filter in the first signal path frequency response at least one according to this, for carrying out Fu Li leaf inverse transform for this at least one first signal path frequency response, and real part is got to the result of Fu Li leaf inverse transform, to obtain this at least one tap coefficient of this first signal path finite impulse response filter of this transmission end.
20. 1 kinds of signal bearing calibrations, for correcting a homophase signal path of a receiver and not mating between an orthogonal signal path, is characterized in that, include:
In at least one frequency mixer correction coefficient of a receiving terminal extra setup of this receiver;
Being exported from a transmission end of this receiver by least one frequency mixer test signal is one first transmission signal, and this of returning in loopback first transmits signal after this at least one frequency mixer correction coefficient, carries out spectrum analysis to obtain at least one frequency mixer result of spectrum analysis to it;
This at least one frequency mixer correction coefficient of this receiving terminal is adjusted according to this at least one frequency mixer result of spectrum analysis, to obtain this final at least one frequency mixer correction coefficient, with not mating between one second frequency mixer of this second signal path of one first frequency mixer and this receiving terminal that correct this first signal path of this receiving terminal of this receiver; And
One first signal path finite impulse response filter this first signal path to this receiving terminal is additionally utilized to carry out one first signal path finite impulse response (FIR) process, and additionally utilize one second signal path finite impulse response filter this second signal path to this receiving terminal to carry out one second signal path finite impulse response (FIR) process, with not mating between one second filter of this second signal path of one first filter and this receiving terminal that correct this first signal path of this receiving terminal of this receiver.
21. as the bearing calibration of claim 20, and wherein this receiver is an OFDM modulation receiver.
22. as the bearing calibration of claim 20, wherein this at least one frequency mixer correction coefficient at least includes one first frequency mixer correction coefficient and one second frequency mixer correction coefficient, and wherein this first frequency mixer correction coefficient is do not mate for the amplitude corrected between this first signal path with this second signal path; And this second frequency mixer correction coefficient is do not mate with the phase place of this second signal path for correcting this first signal path.
23. as the bearing calibration of claim 22, wherein this at least one frequency mixer test signal includes one first frequency mixer correction test signal and one second frequency mixer correction test signal, and this first frequency mixer correction test signal has one first frequency mixer correction test frequency, this second frequency mixer corrects test signal and has one second frequency mixer correction test frequency; And this first frequency mixer corrects test frequency is that to add that a characteristic frequency and this second frequency mixer correct test frequency be that this local oscillator frequencies of this receiving terminal deducts this characteristic frequency for a local oscillator frequencies of this receiving terminal.
24., as the bearing calibration of claim 23, wherein adjust this at least one frequency mixer correction coefficient according to this at least one frequency mixer result of spectrum analysis, include with the step obtaining this final at least one frequency mixer correction coefficient:
Adjust this first frequency mixer correction coefficient, and a mirror image signal that this first frequency mixer can be made to correct test signal presents this first frequency mixer correction coefficient of relative minimum as one first result;
Adjust this second frequency mixer correction coefficient, and this mirror image signal that this first frequency mixer can be made to correct test signal presents this second frequency mixer correction coefficient of relative minimum as one second result;
Adjust this first frequency mixer correction coefficient, and a mirror image signal that this second frequency mixer can be made to correct test signal presents this first frequency mixer correction coefficient of relative minimum as one the 3rd result;
Adjust this second frequency mixer correction coefficient, and this mirror image signal that this second frequency mixer can be made to correct test signal presents this second frequency mixer correction coefficient of relative minimum as one the 4th result; And
Produce this final the first frequency mixer correction coefficient according to this first result and the 3rd result, and produce this final the second frequency mixer correction coefficient according to this second result and the 4th result.
25. as the bearing calibration of claim 20, and the step wherein additionally utilizing this first signal path finite impulse response filter this first signal path to this receiving terminal to carry out this first signal path finite impulse response (FIR) process includes:
Except this frequency mixer correction coefficient original, set at least one filter correction coefficient in this receiving terminal in addition;
Being exported from this transmission end of this receiver by least one filters to test signal is one second transmission signal, and this second transmission signal making loopback return is after this at least one filter correction coefficient of this receiving terminal, carries out spectrum analysis to obtain at least one filter spectrum analysis result to it;
This at least one filter correction coefficient of this receiving terminal is adjusted according to this at least one filter spectrum analysis result;
At least one tap coefficient of this first signal path finite impulse response filter of this receiving terminal is obtained according to this at least one filter correction coefficient after adjustment; And
Without this at least one filter correction coefficient, through this first signal path finite impulse response filter, this first signal path finite impulse response (FIR) process is carried out, with not mating between this filter of this filter and this second signal path of correcting this first signal path to this first signal path.
26. as the bearing calibration of claim 25, and the step wherein additionally utilizing this second signal path finite impulse response filter this second signal path to this receiving terminal to carry out this second signal path finite impulse response (FIR) process includes:
Utilize a delay circuit string to be used as this second signal path finite impulse response filter, and this delay circuit string is for carry out a signal delay process for this second signal path, the time of delay of this first signal path finite impulse response (FIR) process for corresponding to this first signal path finite impulse response filter and carrying out time of delay of wherein this signal delay process.
27. as the bearing calibration of claim 25, and this wherein making loopback return second transmits signal and at least include through the step of this at least one filter correction coefficient of this receiving terminal:
This second transmission signal that loopback is returned passes through this at least one frequency mixer correction coefficient and this at least one filter correction coefficient of this receiving terminal.
28. as the bearing calibration of claim 27, wherein this at least one filter correction coefficient at least includes one first filter correction coefficient and one second filter correction coefficient, wherein this first filter correction coefficient is do not mate for the amplitude corrected between this first signal path with this second signal path, and this second filter correction coefficient is do not mate for the phase place corrected between this first signal path with this second signal path.
29. as the bearing calibration of claim 28, and wherein this at least one filters to test signal has at least one filter correction test frequency, and this at least one filter correction test frequency by be positioned at this receiver wish process frequency band range within.
30. as the bearing calibration of claim 29, and the step wherein adjusting this at least one filter correction coefficient of this receiving terminal according to this at least one filter spectrum analysis result includes:
Adjust this first filter correction coefficient, and a mirror image signal of this at least one filters to test signal can be made to present this first filter correction coefficient of relative minimum as at least one first filter correction coefficient results; And
Adjust this second filter correction coefficient, and this mirror image signal of this at least one filters to test signal can be made to present this second filter correction coefficient of relative minimum as at least one second filter correction coefficient results.
31. as the bearing calibration of claim 30, and the step wherein obtaining this at least one tap coefficient of this first signal path finite impulse response filter according to this at least one filter correction coefficient after adjustment includes:
Obtain at least one second signal path frequency response of this second signal path finite impulse response filter respectively on this at least one filter correction test frequency;
According to this at least one second signal path frequency response and to this at least one first filter results of at least one filter correction test frequency and this at least one second filter results obtaining at least one first signal path frequency response; And
This at least one tap coefficient of this first signal path finite impulse response filter is obtained according to this at least one first signal path frequency response.
32. as the bearing calibration of claim 31, wherein in the step of this at least one second signal path frequency response of this second signal path finite impulse response filter respectively on this at least one filter correction test frequency obtaining this receiving terminal, for at least one tap coefficient for this second signal path finite impulse response filter carries out Fu Liye conversion, to obtain this at least one second signal path frequency response respectively on this at least one filter correction test frequency of this second signal path finite impulse response filter; And obtain in the step of this at least one tap coefficient of this first signal path finite impulse response filter in the first signal path frequency response at least one according to this, for carrying out Fu Li leaf inverse transform for this at least one first signal path frequency response, and real part is got to the result of Fu Li leaf inverse transform, to obtain this at least one tap coefficient of this first signal path finite impulse response filter of this receiving terminal.
33. as the bearing calibration of claim 25, and this wherein making loopback return second transmits signal and at least include through the step of this at least one filter correction coefficient of this receiving terminal:
This second transmission signal that loopback is returned is without this at least one frequency mixer correction coefficient of this receiving terminal and through this at least one filter correction coefficient.
34. as the bearing calibration of claim 33, wherein this at least one filter correction coefficient at least includes one first filter correction coefficient and one second filter correction coefficient, wherein this first filter correction coefficient is do not mate for the amplitude corrected between this first signal path with this second signal path, and this second filter correction coefficient is do not mate for the phase place corrected between this first signal path with this second signal path.
35. as the bearing calibration of claim 34, and wherein this at least one filters to test signal has at least one filter correction test frequency, and this at least one filter correction test frequency by be positioned at this receiver wish process frequency band range within.
36. as the bearing calibration of claim 35, and the step wherein adjusting this at least one filter correction coefficient of this receiving terminal according to this at least one filter spectrum analysis result includes:
Adjust this first filter correction coefficient, and a mirror image signal of this at least one filters to test signal can be made to present this first filter correction coefficient of relative minimum as at least one first filter results; And
Adjust this second filter correction coefficient, and this mirror image signal of this at least one filters to test signal can be made to present this second filter correction coefficient of relative minimum as at least one second filter results.
37. as the bearing calibration of claim 36, and the step wherein obtaining this at least one tap coefficient of this first signal path finite impulse response filter according to this at least one filter correction coefficient after adjustment separately includes:
At least one first signal path frequency response is obtained according to this first filter results, this second filter results and this frequency mixer correction coefficient; And
This at least one tap coefficient of this first signal path finite impulse response filter is obtained according to this at least one first signal path frequency response.
38. as the bearing calibration of claim 37, wherein obtain in the step of this at least one tap coefficient of this first signal path finite impulse response filter in the first signal path frequency response at least one according to this, for carrying out Fu Li leaf inverse transform for this at least one first signal path frequency response, and real part is got to the result of Fu Li leaf inverse transform, to obtain this at least one tap coefficient of this first signal path finite impulse response filter of this receiving terminal.
39. 1 kinds of signal means for correctings, for correcting one first signal path of a conveyer and not mating between one second signal path, wherein this one of first signal path and this second signal path are a homophase signal path, another of this first signal path and this second signal path is an orthogonal signal path, and this means for correcting includes:
One frequency mixer correction coefficient unit, is coupled to a transmission end of this conveyer, is set with at least one frequency mixer correction coefficient;
One frequency mixer test signal generation unit, is used for that at least one frequency mixer test signal is produced one first from this transmission end through this at least one frequency mixer correction coefficient and transmits signal;
One spectral analysis unit, this being used for returning to loopback first transmits signal to carry out spectrum analysis to obtain at least one frequency mixer result of spectrum analysis;
One frequency mixer correction coefficient adjustment unit, be used for according to this at least one frequency mixer result of spectrum analysis to adjust this at least one frequency mixer correction coefficient, to obtain this final at least one frequency mixer correction coefficient, with not mating between one second frequency mixer of one first frequency mixer and this second signal path that correct this first signal path; And
One finite impulse response filter unit, be coupled to this transmission end of this conveyer, be used for additionally utilizing one first signal path finite impulse response filter to carry out one first signal path finite impulse response (FIR) process to this first signal path, and additionally utilize one second signal path finite impulse response filter to carry out one second signal path finite impulse response (FIR) process to this second signal path, with not mating between one second filter of one first filter and this second signal path that correct this first signal path.
40. as the means for correcting of claim 39, and wherein this conveyer is an OFDM modulation conveyer.
41. as the means for correcting of claim 39, wherein this at least one frequency mixer correction coefficient at least includes one first frequency mixer correction coefficient and one second frequency mixer correction coefficient, and wherein this first frequency mixer correction coefficient is do not mate for the amplitude corrected between this first signal path with this second signal path; And this second frequency mixer correction coefficient is do not mate with the phase place of this second signal path for correcting this first signal path.
42. as the means for correcting of claim 41, wherein this at least one frequency mixer test signal includes one first frequency mixer correction test signal and one second frequency mixer correction test signal, and this first frequency mixer correction test signal has one first frequency mixer correction test frequency, this second frequency mixer corrects test signal and has one second frequency mixer correction test frequency; And this first frequency mixer corrects test frequency is that to add that a characteristic frequency and this second frequency mixer correct test frequency be that this local oscillator frequencies of this transmission end deducts this characteristic frequency for a local oscillator frequencies of this transmission end.
43. as the means for correcting of claim 42, wherein this frequency mixer correction coefficient adjustment unit is this first frequency mixer correction coefficient of adjustment, and a mirror image signal that this first frequency mixer can be made to correct test signal presents this first frequency mixer correction coefficient of relative minimum as one first result; Adjust this second frequency mixer correction coefficient, and this mirror image signal that this first frequency mixer can be made to correct test signal presents this second frequency mixer correction coefficient of relative minimum as one second result; Adjust this first frequency mixer correction coefficient, and a mirror image signal that this second frequency mixer can be made to correct test signal presents this first frequency mixer correction coefficient of relative minimum as one the 3rd result; Adjust this second frequency mixer correction coefficient, and this mirror image signal that this second frequency mixer can be made to correct test signal presents this second frequency mixer correction coefficient of relative minimum as one the 4th result; And produce this final the first frequency mixer correction coefficient according to this first result and the 3rd result, and produce this final the second frequency mixer correction coefficient according to this second result and the 4th result.
44. as the means for correcting of claim 39, wherein this spectral analysis unit is separately after second transmits this at least one filter correction coefficient through this transmission end of signal and loopback is returned, spectrum analysis is carried out to obtain at least one filter spectrum analysis result to it, and this means for correcting separately includes:
One filter correction coefficient elements, includes at least one filter correction coefficient;
One filters to test signal generation unit, being used at least one filters to test signal to export from this transmission end of this receiver is one second transmission signal;
One filter correction coefficient adjustment unit, is used for according to this at least one filter spectrum analysis result to adjust this at least one filter correction coefficient of this transmission end;
One tap coefficient calculation unit, is used for this at least one filter correction coefficient after according to adjustment to obtain at least one tap coefficient of this first signal path finite impulse response filter of this transmission end; And
One switch unit, be used for without this at least one filter correction coefficient, through this first signal path finite impulse response filter, this first signal path finite impulse response (FIR) process is carried out, with not mating between this filter of this filter and this second signal path of correcting this first signal path to this first signal path.
45. as the means for correcting of claim 44, wherein for utilizing a delay circuit string to be used as this second signal path finite impulse response filter, and this delay circuit string is for carry out a signal delay process for this second signal path, the time of delay of this first signal path finite impulse response (FIR) process for corresponding to this first signal path finite impulse response filter and carrying out time of delay of wherein this signal delay process.
46. as the means for correcting of claim 44, wherein this spectral analysis unit is separately after second transmits this at least one frequency mixer correction coefficient through this transmission end of signal and this at least one filter correction coefficient and loopback is returned, and carries out spectrum analysis to obtain at least one filter spectrum analysis result to it.
47. as the means for correcting of claim 45, and wherein this at least one filter correction coefficient at least includes one first filter correction coefficient and one second filter correction coefficient; This first filter correction coefficient is do not mate for the amplitude corrected between this first signal path with this second signal path; And this second filter correction coefficient is do not mate for the phase place corrected between this first signal path with this second signal path.
48. as the means for correcting of claim 47, and wherein this at least one filters to test signal has at least one filter correction test frequency, and this at least one filter correction test frequency by be positioned at this conveyer wish process frequency band range within.
49. as the means for correcting of claim 48, wherein this filter correction coefficient adjustment unit adjusts this first filter correction coefficient, and a mirror image signal of this at least one filters to test signal can be made to present this first filter correction coefficient of relative minimum as at least one first filter correction coefficient results; And adjust this second filter correction coefficient, and this mirror image signal of this at least one filters to test signal can be made to present this second filter correction coefficient of relative minimum as at least one second filter correction coefficient results.
50. as the means for correcting of claim 49, and wherein this tap coefficient calculation unit includes:
One second signal path frequency response computing unit, obtains at least one second signal path frequency response of this second signal path finite impulse response filter respectively on this at least one filter correction test frequency;
One main first signal path frequency response computing unit, be used for according to this at least one second signal path frequency response, to should this at least one first filter correction coefficient results of at least one filter correction test frequency and this at least one second filter correction coefficient results, obtain at least one first signal path frequency response; And
One coefficient calculation unit, is used for according to this at least one first signal path frequency response to obtain this at least one tap coefficient of this first signal path finite impulse response filter.
51. as the means for correcting of claim 50, wherein this second signal path frequency response computing unit is carry out Fu Liye conversion, to obtain this at least one second signal path frequency response respectively on this at least one filter correction test frequency of this second signal path finite impulse response filter at least one tap coefficient of this second signal path finite impulse response filter; And this coefficient calculation unit is for carry out Fu Li leaf inverse transform for this at least one first signal path frequency response, and real part is got to the result of Fu Li leaf inverse transform, to obtain this at least one tap coefficient of this first signal path finite impulse response filter of this transmission end.
52. as the means for correcting of claim 44, wherein this spectral analysis unit separately transmits signal second and after loopback returns, carries out spectrum analysis to obtain at least one filter spectrum analysis result to it without this at least one frequency mixer correction coefficient of this transmission end and through this at least one filter correction coefficient.
53. as the means for correcting of claim 52, and wherein this at least one filter correction coefficient at least includes one first filter correction coefficient and one second filter correction coefficient; This first filter correction coefficient is do not mate for the amplitude corrected between this first signal path with this second signal path; And this second filter correction coefficient is do not mate for the phase place corrected between this first signal path with this second signal path.
54. as the means for correcting of claim 53, and wherein this at least one filters to test signal has at least one filter correction test frequency, and this at least one filter correction test frequency by be positioned at this conveyer wish process frequency band range within.
55. as the means for correcting of claim 54, wherein this filter correction coefficient adjustment unit adjusts this first filter correction coefficient, and a mirror image signal of this at least one filters to test signal can be made to present this first filter correction coefficient of relative minimum as at least one first filter results; And adjust this second filter correction coefficient, and this mirror image signal of this at least one filters to test signal can be made to present this second filter correction coefficient of relative minimum as at least one second filter results.
56. as the means for correcting of claim 55, and wherein this tap coefficient calculation unit separately includes:
One auxiliary first signal path frequency response computing unit, is used for according to this first filter results and this second filter results to obtain at least one first signal path frequency response; And
One coefficient calculation unit, is used for according to this at least one first signal path frequency response to obtain this at least one tap coefficient of this first signal path finite impulse response filter.
57. as the means for correcting of claim 56, wherein this coefficient calculation unit is for carry out Fu Li leaf inverse transform for this at least one first signal path frequency response, and real part is got to the result of Fu Li leaf inverse transform, to obtain this at least one tap coefficient of this first signal path finite impulse response filter of this transmission end.
58. 1 kinds of signal means for correctings, for correcting one first signal path of a receiver and not mating between one second signal path, wherein this one of first signal path and this second signal path are a homophase signal path, another of this first signal path and this second signal path is an orthogonal signal path, and this means for correcting includes:
One frequency mixer correction coefficient unit, is coupled to a receiving terminal of this receiver, is set with at least one frequency mixer correction coefficient;
One frequency mixer test signal generation unit, is used for that at least one frequency mixer test signal is produced one first from a transmission end of this receiver and transmits signal;
One spectral analysis unit, this of returning in loopback first transmits signal after this at least one frequency mixer correction coefficient, carries out spectrum analysis to obtain at least one frequency mixer result of spectrum analysis to it;
One frequency mixer correction coefficient adjustment unit, be used for according to this at least one frequency mixer result of spectrum analysis to adjust this at least one frequency mixer correction coefficient of this receiving terminal, to obtain this final at least one frequency mixer correction coefficient, with not mating between a frequency mixer of this second signal path of the frequency mixer and this receiving terminal that correct this first signal path of this receiving terminal of this receiver; And
One finite impulse response filter unit, be coupled to this receiving terminal of this receiver, be used for additionally utilizing one first signal path finite impulse response filter this first signal path to this receiving terminal to carry out one first signal path finite impulse response (FIR) process, and additionally utilize one second signal path finite impulse response filter this second signal path to this receiving terminal to carry out one second signal path finite impulse response (FIR) process, with not mating between a filter of this second signal path of the filter and this receiving terminal that correct this first signal path of this receiving terminal of this receiver.
59. as the means for correcting of claim 58, and wherein this receiver is an OFDM modulation receiver.
60. as the means for correcting of claim 58, wherein this at least one frequency mixer correction coefficient at least includes one first frequency mixer correction coefficient and one second frequency mixer correction coefficient, and wherein this first frequency mixer correction coefficient is do not mate for the amplitude corrected between this first signal path with this second signal path; And this second frequency mixer correction coefficient is do not mate with the phase place of this second signal path for correcting this first signal path.
61. as the means for correcting of claim 60, wherein this at least one frequency mixer test signal includes one first frequency mixer correction test signal and one second frequency mixer correction test signal, and this first frequency mixer correction test signal has one first frequency mixer correction test frequency, this second frequency mixer corrects test signal and has one second frequency mixer correction test frequency; And this first frequency mixer corrects test frequency is that to add that a characteristic frequency and this second frequency mixer correct test frequency be that this local oscillator frequencies of this receiving terminal deducts this characteristic frequency for a local oscillator frequencies of this receiving terminal.
62. as the means for correcting of claim 61, wherein this frequency mixer correction coefficient adjustment unit adjusts this first frequency mixer correction coefficient, and a mirror image signal that this first frequency mixer can be made to correct test signal presents this first frequency mixer correction coefficient of relative minimum as one first result; Adjust this second frequency mixer correction coefficient, and this mirror image signal that this first frequency mixer can be made to correct test signal presents this second frequency mixer correction coefficient of relative minimum as one second result; Adjust this first frequency mixer correction coefficient, and a mirror image signal that this second frequency mixer can be made to correct test signal presents this first frequency mixer correction coefficient of relative minimum as one the 3rd result; Adjust this second frequency mixer correction coefficient, and this mirror image signal that this second frequency mixer can be made to correct test signal presents this second frequency mixer correction coefficient of relative minimum as one the 4th result; And produce this final the first frequency mixer correction coefficient according to this first result and the 3rd result, and produce this final the second frequency mixer correction coefficient according to this second result and the 4th result.
63. as the means for correcting of claim 58, wherein this spectral analysis unit separately carries out spectrum analysis at least one filters to test signal that this receiving terminal of this receiver receives, obtain at least one filter spectrum analysis result, and this means for correcting separately includes:
One filter correction coefficient elements, includes at least one filter correction coefficient;
One filters to test signal generation unit, is used for transmitting this at least one filters to test signal this receiving terminal to this receiver from this transmission end, and passes through this at least one filter correction coefficient of this receiving terminal;
One filter correction coefficient adjustment unit, is used for according to this at least one filter spectrum analysis result to adjust this at least one filter correction coefficient of this receiving terminal;
One tap coefficient calculation unit, is used for this at least one filter correction coefficient after according to adjustment to obtain at least one tap coefficient of this first signal path finite impulse response filter of this receiving terminal; And
One switch unit, be used for without this at least one filter correction coefficient, through this first signal path finite impulse response filter, this first signal path finite impulse response (FIR) process is carried out, with not mating between this filter of this filter and this second signal path of correcting this first signal path to this first signal path.
64. as the means for correcting of claim 63, wherein for utilizing a delay circuit string to be used as this second signal path finite impulse response filter, and this delay circuit string is for carry out a signal delay process for this second signal path, the time of delay of this first signal path finite impulse response (FIR) process for corresponding to this first signal path finite impulse response filter and carrying out time of delay of wherein this signal delay process.
65. as the means for correcting of claim 63, wherein this filters to test signal generation unit is used for transmitting this at least one filters to test signal this receiving terminal to this receiver from this transmission end further, and passes through this at least one frequency mixer correction coefficient and this at least one filter correction coefficient of this receiving terminal.
66. as the means for correcting of claim 64, wherein this at least one filter correction coefficient at least includes one first filter correction coefficient and one second filter correction coefficient, wherein this first filter correction coefficient is do not mate for the amplitude corrected between this first signal path with this second signal path, and this second filter correction coefficient is do not mate for the phase place corrected between this first signal path with this second signal path.
67. as the means for correcting of claim 66, and wherein this at least one filters to test signal has at least one filter correction test frequency, and this at least one filter correction test frequency by be positioned at this receiver wish process frequency band range within.
68. as the means for correcting of claim 67, wherein this filter correction coefficient adjustment unit adjusts this first filter correction coefficient, and a mirror image signal of this at least one filters to test signal can be made to present this first filter correction coefficient of relative minimum as at least one first filter correction coefficient results; And adjust this second filter correction coefficient, and this mirror image signal of this at least one filters to test signal can be made to present this second filter correction coefficient of relative minimum as at least one second filter correction coefficient results.
69. as the means for correcting of claim 68, and wherein this tap coefficient calculation unit includes:
One second signal path frequency response computing unit, is used for obtaining at least one second signal path frequency response of this second signal path finite impulse response filter respectively on this at least one filter correction test frequency;
One main first signal path frequency response computing unit, be used for according to this at least one second signal path frequency response and to should this at least one first filter correction coefficient results of at least one filter correction test frequency and this at least one second filter correction coefficient results to obtain at least one first signal path frequency response; And
One coefficient calculation unit, is used for according to this at least one first signal path frequency response to obtain this at least one tap coefficient of this first signal path finite impulse response filter.
70. as the means for correcting of claim 69, wherein this orthogonal signal path frequencies RESPONSE CALCULATION unit is carry out Fu Liye conversion, to obtain this at least one second signal path frequency response respectively on this at least one filter correction test frequency of this second signal path finite impulse response filter at least one tap coefficient of this second signal path finite impulse response filter; And this coefficient calculation unit is for carry out Fu Li leaf inverse transform for this at least one first signal path frequency response, and real part is got to the result of Fu Li leaf inverse transform, to obtain this at least one tap coefficient of this first signal path finite impulse response filter of this receiving terminal.
71. as the means for correcting of claim 63, wherein this filters to test signal generation unit is used for transmitting this at least one filters to test signal this receiving terminal to this receiver from this transmission end further, and without this at least one frequency mixer correction coefficient of this receiving terminal and through this at least one filter correction coefficient.
72. as the means for correcting of claim 71, wherein this at least one filter correction coefficient at least includes one first filter correction coefficient and one second filter correction coefficient, wherein this first filter correction coefficient is do not mate for the amplitude corrected between this first signal path with this second signal path, and this second filter correction coefficient is do not mate for the phase place corrected between this first signal path with this second signal path.
73. as the means for correcting of claim 72, and wherein this at least one filters to test signal has at least one filter correction test frequency, and this at least one filter correction test frequency by be positioned at this receiver wish process frequency band range within.
74. as the means for correcting of claim 73, wherein this filter correction coefficient adjustment unit adjusts this first filter correction coefficient, and a mirror image signal of this at least one filters to test signal can be made to present this first filter correction coefficient of relative minimum as at least one first filter results; And adjust this second filter correction coefficient, and this mirror image signal of this at least one filters to test signal can be made to present this second filter correction coefficient of relative minimum as at least one second filter results.
75. as the means for correcting of claim 74, and wherein this tap coefficient calculation unit separately includes:
One auxiliary first signal path frequency response computing unit, is used for according to this first filter results, this second filter results and this frequency mixer correction coefficient to obtain at least one first signal path frequency response; And
One coefficient calculation unit, is used for according to this at least one first signal path frequency response to obtain this at least one tap coefficient of this first signal path finite impulse response filter.
76. as the means for correcting of claim 75, wherein this coefficient calculation unit is for carry out Fu Li leaf inverse transform for this at least one first signal path frequency response, and real part is got to the result of Fu Li leaf inverse transform, to obtain this at least one tap coefficient of this first signal path finite impulse response filter of this receiving terminal.
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