CN103929396A - Processing method of MIMO-OFDM system downlink information data - Google Patents
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Abstract
The invention discloses a processing method of MIMO-OFDM system downlink information data. The problem that the optimum error rate performance cannot be obtained through a traditional downlink information data processing method is mainly solved. The processing method comprises the steps that (1) sub-carriers are subjected to grouping, and sending and receiving signal vectors corresponding to the groups of sub-carries and channel matrixes are established; (2) modulating signals corresponding to the groups of sub-carries are subjected to normalization and disturbance; (3) the signal vectors after normalization and disturbance are subjected to multithread interference rejection and emitting power control; (4) the receiving signal vectors corresponding to the groups of sub-carriers are subjected to gain compensation and modulus operation; (5) normalization modulating signal estimated values obtained after modulus operation are subjected to inverse normalization; and (6) estimated values of orthogonality amplitude modulating signal vectors after inverse normalization are subjected to demodulation. The method has the advantages of being low in error rate and adjustable in complexity, and the method is used for transceiver designing of an MIMO-OFDM communication system.
Description
Technical field
The invention belongs to communication technical field, relate to a kind of data processing method, can be used for the processing of transmitting terminal information and receiving terminal information data in MIMO-OFDM system down link.
Background technology
Multi-input multi-output-orthogonal frequency division multiplexing MIMO-OFDM technology is adopted by the 4th generation 4G mobile communication standard, the premium properties such as it has that the availability of frequency spectrum is high, stable signal transmission, transmission rate are fast, and be considered to one of core technology of future mobile communication system, adopt the communication system of this technology to be collectively referred to as MIMO-OFDM system.One of key technology of MIMO-OFDM system is exactly the treatment technology of downlink information data, by the information data sending being carried out preliminary treatment and at receiving terminal, the information data receiving is carried out to reprocessing at transmitting terminal, realize the diversity of MIMO-OFDM system descending data flow and multiplexing, improve transmission rate and the reliability of system.
Vector disturbance VP is one of a kind of best performance mimo system downlink information data processing technique of getting over, and within 2005, first by B.M.Hochwald, C.B.Peel and A.L.Swindlehurst propose, and prove that its performance approaches shannon limit.This technology obtains the Stephen O.Rice of ieee communication association awards in 2006, and a lot of researchers have started the research to this Novel descending information data treatment technology subsequently.Up to the present, had a variety of improved vector perturbation motion methods to be suggested, and be applied on the down channel of mimo system, but also not having researcher to deliver is applied to the vector disturbance treatment method on MIMO-OFDM system descending channel.This is because MIMO-OFDM system can be decomposed into the mimo system of N quadrature flat fading of equal valuely, wherein N is OFDM subcarrier number, and so the downlink information data processing of MIMO-OFDM system is regarded as merely the identical repetition on each subcarrier of mimo system downlink information data processing conventionally.Under the condition of disturbing between carrierfree, for example, for traditional downlink information data processing method: ZF ZF, least mean-square error MMSE, Tomlinson-Harashima, above-mentioned conclusion is set up, yet for vector disturbance preliminary treatment, this conclusion is no longer set up.Thereby, simply vector disturbance treatment method is expanded on each subcarrier of MIMO-OFDM system and can not make the error rate of system obtain optimum performance.
Summary of the invention
The object of the invention is to improve the deficiency of above-mentioned prior art, a kind of processing method of MIMO-OFDM system descending information data is provided, to improve the bit error rate performance of system.
Realizing technical thought of the present invention is: spatial domain and the frequency-domain combined channel matrix of structure MIMO-OFDM system, with its pseudo inverse matrix, transmitted signal is carried out to multithread and disturb inhibition, and transmitted signal is carried out to disturbance, and to maximize the transmit power efficiency of system, its concrete technical step is as follows:
(1) subcarrier is divided into groups: transmitting terminal is divided into M group by N subcarrier, in each group, comprise Q the mutually different subcarrier of frequency, with set I={1,2 ..., N} represents the 1st to N sub-carrier set, with set I
m={ n
m, 1, n
m, 2..., n
m,Qrepresent n in m group
m, 1to n
m,Qthe set of individual subcarrier, with set I
m '={ n
m ', 1, n
m ', 2..., n
m ', Qrepresent n in the m ' group
m ', 1to n
m ', Qthe set of individual subcarrier, the result of grouping is formulated as N=MQ, I
1∪ I
2∪ ... ∪ I
m=I,
In formula,
represent empty set, the span of M is 1 to N;
(2) construct every group of sending and receiving signal phasor and channel matrix that subcarrier is corresponding:
(2a) by the transmitted signal vector on m group subcarrier
X
m＝[X(n
m,1)
T,X(n
m,2)
T,…,X(n
m,i),…,X(n
m,Q)
T]
T，
Wherein, X (n
m,i)=[x
1(n
m,i), x
2(n
m,i) ..., x
b(n
m,i)]
trepresent the signal phasor on i the corresponding B of a subcarrier transmitting antenna of m group, i=1 ..., Q, subscript " T " representing matrix transposition;
(2b) the reception signal phasor on m group subcarrier is expressed as:
Y
m＝[Y(n
m,1)
T,Y(n
m,2)
T,…,Y(n
m,i),…,Y(n
m,Q)
T]
T，
Wherein, Y (n
m,i)=[y
1(n
m,i), y
2(n
m,i) ..., y
r(n
m,i)]
trepresent the signal phasor on i the corresponding R of a subcarrier reception antenna of m group, i=1 ..., Q;
(2c) by the additive white Gaussian noise vector representation on m group subcarrier, be:
Z
m＝[Z(n
m,1)
T,Z(n
m,2)
T,…,Z(n
m,i),…,Z(n
m,Q)
T]
T，
Wherein, Z (n
m,i)=[z
1(n
m,i), z
2(n
m,i) ..., z
r(n
m,i)]
trepresent the additive white Gaussian noise vector on i the corresponding R of a subcarrier reception antenna of m group, i=1 ..., Q;
(2d) channel matrix corresponding to m group subcarrier is expressed as:
H
m＝diag(H(n
m，1),H(n
m,2),…,H(n
m,i),…,H(n
m,Q))，
Wherein, H (n
m,i) be the mimo channel matrix on i subcarrier of m group, i=1 ..., Q, diag () represents to generate diagonal matrix;
(2e) model that equals to transmit with channel product plus noise according to the reception signal on each carrier wave, and (2a), the corresponding relation of (2b), (2c), (2d), obtain following relational expression:
Y
m＝H
mX
m+Z
m；
(3) every group of modulation signal corresponding to subcarrier is normalized and disturbance:
(3a) every group of modulation signal corresponding to subcarrier is normalized:
If A
m=[A (n
m, 1)
t, A (n
m, 2)
t..., A (n
m,i) ..., A (n
m,Q)
t]
tbe the quadrature amplitude modulation QAM signal phasor on m group subcarrier, wherein A (n
m,i)=[a
1(n
m,i), a
2(n
m,i) ..., a
k(n
m,i) ..., a
b(n
m,i)]
trepresent the QAM signal phasor on i the corresponding B of a subcarrier transmitting antenna of m group, wherein a
k(n
m,i) represent the QAM modulation symbol on corresponding k the transmitting antenna of i subcarrier of m group;
If comprise μ in quadrature amplitude modulation qam constellation figure
2individual modulation constellation points, a
k(n
m,i) real part and the value of imaginary part be included in set ± 1, ± 3 ..., ± (μ-1) } in, in order to make a
k(n
m,i) real part and the absolute value of imaginary part be less than or equal to 0.5, transmitting terminal is to A
msignal phasor is normalized with 2 μ, obtains the modulation signal vector S after normalization
mfor:
S
m＝A
m/2μ；
(3b) modulation signal vector S after structure normalization
mperturbing vector:
All QR * 1 n dimensional vector n l ' in search QR dimension complex integers territory
mvalue, choose and make function
corresponding l ' while reaching minimum value
mas S
mperturbing vector l
m, be formulated as:
In formula, argmin represents to ask the value of independent variable while making function reach minimum value,
represent QR dimension complex integers territory,
represent channel matrix H
mmoore-Penrose inverse matrix, || ||
2represent 2-norm;
(3c) use perturbing vector l
mto normalization modulation signal vector S
mdisturbance, obtains signal phasor T after disturbance
mfor: T
m=S
m+ l
m;
(4) with signal phasor T after disturbance
mpremultiplication
to suppress the interference between a plurality of transmission data flow, obtain the transmitted signal vector X on m group subcarrier
mfor:
(5) transmitting terminal is to M group transmitted signal vector X
m, m=1,2 ..., M carries out, after power control, by transmitting antenna, sending simultaneously;
(6) receiving terminal receives signal phasor Y to M group
m, m=1,2 ..., M, carries out gain compensation, and the reception signal phasor after compensation is asked to modular arithmetic, obtains the estimated value of normalization modulation signal vector S m
In formula,
represent to round downwards, j represents imaginary unit, and Re () represents real part, and Im () represents imaginary part;
(7) estimated value of receiving terminal to normalization modulation signal vector
with 2 μ, carry out renormalization, obtain the estimated value of quadrature amplitude modulation QAM signal phasor Am
(8) receiving terminal is to quadrature amplitude modulation QAM signal phasor A
mestimated value
m=1,2 ..., M, carries out demodulation, recovers the downlink information data that transmitting terminal sends.
Compared with prior art, tool has the following advantages in the present invention:
1, the present invention due to by MIMO-OFDM system the downlink information data on spatial domain and frequency domain carry out Combined Treatment, with respect to traditional downlink information data processing, only on the spatial domain of each subcarrier, carry out separately, the present invention can suppress when multithread is disturbed to maximize the transmit power efficiency of MIMO-OFDM system, thereby has reduced the error rate of downlink information transfer of data.
2, the present invention is because transmitting terminal can be chosen different subcarrier groupings and counts M value, thereby can regulate neatly bit error rate performance and the computation complexity of downlink information data processing.
Object of the present invention, execution mode can illustrate detailed description by the following drawings:
Accompanying drawing explanation
Fig. 1 is the communication scheme of existing MIMO-OFDM system;
Fig. 2 is schematic flow sheet of the present invention;
Fig. 3 is the BER Simulation performance comparison diagram that adopts the inventive method and existing downlink information data processing method;
Fig. 4 is the computation complexity simulation performance comparison diagram of the inventive method.
Embodiment
Referring to accompanying drawing, technical scheme of the present invention is described in further detail.
With reference to Fig. 1, the system that the present invention uses is a MIMO-OFDM system, and it consists of transmitting terminal and receiving terminal.Wherein, transmitter is equipped with B antenna and uses N subcarrier to send information data, and K receiver is equipped with R antenna and R≤B altogether.The present invention supposes on each subcarrier, the wireless channel H between transmitter antenna and receiver antenna
n, 1≤n≤N is flat fading channel.And each interchannel is separate.
With reference to Fig. 2, performing step of the present invention is as follows:
Step 1, divides into groups to subcarrier.
Transmitting terminal is divided into M group by N subcarrier, comprises Q the mutually different subcarrier of frequency in each group, with set I={1, and 2 ..., N} represents the 1st to N sub-carrier set, with set I
m={ n
m, 1, n
m, 2..., n
m,Qrepresent n in m group
m, 1to n
m,Qthe set of individual subcarrier, with set I
m '={ n
m ', 1, n
m ', 2..., n
m ', Qrepresent n in the m ' group
m ', 1to n
m ', Qthe set of individual subcarrier, the result of grouping is formulated as N=MQ, I
1∪ I
2∪ ... ∪ I
m=I,
In formula,
represent that empty set, the span of M are 1 to N, the computation complexity that transmitting terminal can bear according to the required bit error rate performance of system and transmitter hardware carries out the selection of M value.
Step 2, constructs every group of sending and receiving signal phasor and channel matrix that subcarrier is corresponding.
2.1) by the transmitted signal vector representation on m group subcarrier, be:
X
m＝[X(n
m,1)
T,X(n
m,2)
T,…,X(n
m,i),…,X(n
m,Q)
T]
T，
Wherein, X (n
m,i)=[x
1(n
m,i), x
2(n
m,i) ..., x
b(n
m,i)]
trepresent the signal phasor on i the corresponding B of a subcarrier transmitting antenna of m group, i=1 ..., Q, subscript " T " representing matrix transposition;
2.2) by the additive white Gaussian noise vector representation on m group subcarrier, be:
Z
m＝[Z(n
m,1)
T,Z(n
m,2)
T,…,Z(n
m,i),…,Z(n
m,Q)
T]
T，
Wherein, Z (n
m,i)=[z
1(n
m,i), z
2(n
m,i) ..., z
r(n
m,i)]
trepresent the additive white Gaussian noise vector on i the corresponding R of a subcarrier reception antenna of m group, i=1 ..., Q;
2.3) channel matrix corresponding to m group subcarrier is expressed as:
H
m＝diag(H(n
m,1),H(n
m,2),…,H(n
m,i),…,H(n
m,Q))，
Wherein, H (n
m,i) be the mimo channel matrix on i subcarrier of m group, i=1 ..., Q, diag () represents to generate diagonal matrix;
2.4) the reception signal phasor on m group subcarrier is expressed as:
Y
m＝[Y(n
m,1)
T,Y(n
m,2)
T,…,Y(n
m,i),…,Y(n
m,Q)
T]
T，
Wherein, Y (n
m,i)=[y
1(n
m,i), y
2(n
m,i) ..., y
r(n
m,i)]
trepresent the signal phasor on i the corresponding R of a subcarrier reception antenna of m group, i=1 ..., Q;
2.5) characteristic that equals to transmit with channel product plus noise according to the reception signal on each carrier wave, obtains step 2.4) with 2.1), 2.2), 2.3) corresponding relation be:
Y
m＝H
mX
m+Z
m。
Step 3, is normalized and disturbance every group of modulation signal corresponding to subcarrier.
In order to improve the power efficiency transmitting, first transmitting terminal need to be normalized the modulation signal sending on every group of subcarrier and antenna, then carries out disturbance, and its step is as follows:
3.1) every group of modulation signal corresponding to subcarrier is normalized:
If A
m=[A (n
m, 1)
t, A (n
m, 2)
t..., A (n
m,i) ..., A (n
m,Q)
t]
tbe the quadrature amplitude modulation QAM signal phasor on m group subcarrier, wherein A (n
m,i)=[a
1(n
m,i), a
2(n
m,i) ..., a
k(n
m,i) ..., a
b(n
m,i)]
trepresent the QAM signal phasor on i the corresponding B of a subcarrier transmitting antenna of m group, wherein a
k(n
m,i) represent the QAM modulation symbol on corresponding k the transmitting antenna of i subcarrier of m group;
If comprise μ in quadrature amplitude modulation qam constellation figure
2individual modulation constellation points, a
k(n
m,i) real part and the value of imaginary part be included in set ± 1, ± 3 ..., ± (μ-1) } in, in order to make a
k(n
m,i) real part and the absolute value of imaginary part be less than or equal to 0.5, transmitting terminal is to A
msignal phasor is normalized with 2 μ, obtains the modulation signal vector S after normalization
mfor:
S
m＝A
m/2μ；
3.2) modulation signal vector S after structure normalization
mperturbing vector:
All QR * 1 n dimensional vector n l ' in search QR dimension complex integers territory
mvalue, choose and make function
corresponding l ' while reaching minimum value
mas S
mperturbing vector l
m, be formulated as:
In formula, argmin represents to ask the value of independent variable while making function reach minimum value,
represent QR dimension complex integers territory,
represent channel matrix H
mmoore-Penrose inverse matrix, || ||
2represent 2-norm;
3.3) use perturbing vector l
mto normalization modulation signal vector S
mdisturbance, obtains signal phasor T after disturbance
mfor:
T
m＝S
m+l
m。
Step 4, multithread is disturbed and is suppressed.
For design procedure 2.1) in transmitted signal vector X on m group subcarrier
mconcrete structure, by step 3.3) signal phasor T after the disturbance that obtains
mpremultiplication
interference to exist between a plurality of data flow that suppress to send on different carrier and antenna, obtains X
mstructure expression:
Step 5, carries out transmitting power control.
For the power of the downlink transmission end of system is remained unchanged, must guarantee to carry out the transmitted signal X after above step process
1to X
mgross power consistent with the transmitting power of physical device, by transmitting terminal, M group transmitted signal vector is carried out to power control, carry out as follows:
5.1) calculate M group transmitted signal vector X
1to X
mtotal mean power ε
x:
In formula,
expression to normalization after modulation signal vector S
mand channel matrix H
mask expectation, min represents to ask minimum of a function value;
5.2) according to step 5.1) in the total mean power ε that calculates
x, transmitting terminal is to M group transmitted signal vector X
1to X
mcarry out power control, obtain the signal phasor after power is controlled
In formula, ε
ethe average transmit power that represents physical device.
Step 6, carries out receiving gain compensation.
In order to make the down link receiving terminal of system recover signal phasor T after disturbance
mamplitude, receiving terminal receives signal phasor Y1 to YM to M group and carries out gain compensation, is compensated rear signal phasor
Step 7, modular arithmetic.
In order to recover normalization modulation signal vector S m, receiving terminal is to the reception signal phasor after compensating
ask modular arithmetic, to remove perturbing vector l
m, obtain the estimated value of Sm
In formula,
represent to round downwards, j represents imaginary unit, and Re () represents real part, and Im () represents imaginary part.
Step 8, renormalization.
To the normalization modulation signal vector estimated value in step 7
with 2 μ carry out as shown in the formula renormalization, obtain quadrature amplitude modulation QAM signal phasor A
mestimated value
Step 9, to quadrature amplitude modulation QAM signal phasor A
mestimated value
m=1,2 ..., M, carries out demodulation, recovers the downlink information data that transmitting terminal sends.
Effect of the present invention can further illustrate by following simulation result:
1. simulated conditions: set a MIMO-OFDM system, it comprises 1 transmitting terminal and 2 receiving terminals.Suppose that transmitting terminal is equipped with 4 antennas, 2 antennas of each receiving terminal assembling, use 16 subcarriers; Channel model between every a pair of transmission/reception antennas all adopts 6 footpath frequency selective fading channels, and each footpath is modeled as Clarke flat fading model and the amplitude of fading is obeyed negative exponent distribution; Send data acquisition QPSK modulation system.
2. emulation content:
Emulation 1, adopt respectively downlink information data processing method of the present invention and traditional downlink information data processing method to carry out emulation to the sending and receiving of MIMO-OFDM system descending information data, obtain the error rate BER of MIMO-OFDM system with the performance curve of the variation of signal to noise ratio snr, result is as Fig. 3;
Emulation 2, the complexity of downlink information data processing method of the present invention is carried out to emulation, obtain counting M at subcarrier grouping and get respectively under 1,2,4,8 condition, the performance curve that the computation complexity of the inventive method changes with antenna number and sub-carrier number, result is as Fig. 4.
3. analysis of simulation result:
As can be seen from Figure 3, adopt bit error rate performance curve that downlink information data processing method of the present invention obtains along with the raising of signal to noise ratio, bit error rate performance curve lower than traditional ZF ZF downlink information data processing method, conventional vector disturbance VP downlink information data processing method, and increased BER slope of a curve, that is to say that downlink information data processing method of the present invention has improved the diversity gain of system, has optimized bit error rate performance.
Computation complexity in Fig. 4 is weighed by flops Flops, in conjunction with Fig. 3, as can be seen from Figure 4, adopt downlink information data processing method of the present invention between systematic function and computation complexity, to regulate flexibly, M value is less, and computation complexity is higher but error performance better, and contrary M value is larger, error performance variation, but computation complexity is less.
Claims (3)
1. a processing method for MIMO-OFDM system descending information data, comprises the steps:
(1) subcarrier is divided into groups: transmitting terminal is divided into M group by N subcarrier, in each group, comprise Q the mutually different subcarrier of frequency, with set I={1,2 ..., N} represents the 1st to N sub-carrier set, with set I
m={ n
m, 1, n
m, 2..., n
m,Qrepresent n in m group
m, 1to n
m,Qthe set of individual subcarrier, with set I
m '={ n
m ', 1, n
m ', 2..., n
m ', Qrepresent n in the m ' group
m ', 1to n
m ', Qthe set of individual subcarrier, the result of grouping is formulated as N=MQ, I
1∪ I
2∪ ... ∪ I
m=I,
In formula,
represent empty set, the span of M is 1 to N;
(2) construct every group of sending and receiving signal phasor and channel matrix that subcarrier is corresponding:
(2a) by the transmitted signal vector representation on m group subcarrier, be:
X
m＝[X(n
m,1)
T,X(n
m,2)
T,…,X(n
m,i),…,X(n
m,Q)
T]
T，
Wherein, X (n
m,i)=[x
1(n
m,i), x
2(n
m,i) ..., x
b(n
m,i)]
trepresent the signal phasor on i the corresponding B of a subcarrier transmitting antenna of m group, i=1 ..., Q, subscript " T " representing matrix transposition;
(2b) by the additive white Gaussian noise vector representation on m group subcarrier, be:
Z
m＝[Z(n
m,1)
T,Z(n
m,2)
T,…,Z(n
m,i),…,Z(n
m,Q)
T]
T，
Wherein, Z (n
m,i)=[z
1(n
m,i), z
2(n
m,i) ..., z
r(n
m,i)]
trepresent the additive white Gaussian noise vector on i the corresponding R of a subcarrier reception antenna of m group, i=1 ..., Q;
(2c) channel matrix corresponding to m group subcarrier is expressed as:
H
m＝diag(H(n
m,1),H(n
m,2),…,H(n
m,i),…,H(n
m,Q))，
Wherein, H (n
m,i) be the mimo channel matrix on i subcarrier of m group, i=1 ..., Q, diag () represents to generate diagonal matrix;
(2d) the reception signal phasor on m group subcarrier is expressed as:
Y
m＝[Y(n
m,1)
T,Y(n
m,2)
T,…,Y(n
m,i),…,Y(n
m,Q)
T]
T，
Wherein, Y (n
m,i)=[y
1(n
m,i), y
2(n
m,i) ..., y
r(n
m,i)]
trepresent the signal phasor on i the corresponding R of a subcarrier reception antenna of m group, i=1 ..., Q;
(2e) model that equals to transmit with channel product plus noise according to the reception signal on each carrier wave, and (2a), the corresponding relation of (2b), (2c), (2d), obtain following relational expression:
Y
m＝H
mX
m+Z
m；
(3) every group of modulation signal corresponding to subcarrier is normalized and disturbance:
(3a) every group of modulation signal corresponding to subcarrier is normalized:
If A
m=[A (n
m, 1)
t, A (n
m, 2)
t..., A (n
m,i) ..., A (n
m,Q)
t]
tbe the quadrature amplitude modulation QAM signal phasor on m group subcarrier, wherein A (n
m,i)=[a
1(n
m,i), a
2(n
m,i) ..., a
k(n
m,i) ..., a
b(n
m,i)]
trepresent the QAM signal phasor on i the corresponding B of a subcarrier transmitting antenna of m group, wherein a
k(n
m,i) represent the QAM modulation symbol on corresponding k the transmitting antenna of i subcarrier of m group;
If comprise μ in quadrature amplitude modulation qam constellation figure
2individual modulation constellation points, a
k(n
m,i) real part and the value of imaginary part be included in set ± 1, ± 3 ..., ± (μ-1) } in, in order to make a
k(n
m,i) real part and the absolute value of imaginary part be less than or equal to 0.5, transmitting terminal is to A
msignal phasor is normalized with 2 μ, obtains the modulation signal vector S after normalization
mfor:
S
m＝A
m/2μ；
(3b) modulation signal vector S after structure normalization
mperturbing vector:
All QR * 1 n dimensional vector n l ' in search QR dimension complex integers territory
mvalue, choose and make function
corresponding l ' while reaching minimum value
mas S
mperturbing vector l
m, be formulated as:
In formula, argmin represents to ask the value of independent variable while making function reach minimum value,
represent QR dimension complex integers territory,
represent channel matrix H
mmoore-Penrose inverse matrix, || ||
2represent 2-norm;
(3c) use perturbing vector l
mto normalization modulation signal vector S
mdisturbance, obtains signal phasor T after disturbance
mfor: T
m=S
m+ l
m;
(4) with signal phasor T after disturbance
mpremultiplication
to suppress the interference between a plurality of transmission data flow, obtain the transmitted signal vector X on m group subcarrier
mfor:
(5) transmitting terminal is to M group transmitted signal vector X
m, m=1,2 ..., M carries out, after power control, by transmitting antenna, sending simultaneously;
(6) receiving terminal receives signal phasor Y to M group
m, m=1,2 ..., M, carries out gain compensation, and the reception signal phasor after compensation is asked to modular arithmetic, obtains normalization modulation signal vector S
mestimated value
In formula,
represent to round downwards, j represents imaginary unit, and Re () represents real part, and Im () represents imaginary part;
(7) estimated value of receiving terminal to normalization modulation signal vector
with 2 μ, carry out renormalization, obtain quadrature amplitude modulation QAM signal phasor A
mestimated value
(8) receiving terminal is to quadrature amplitude modulation QAM signal phasor A
mestimated value
m=1,2 ..., M, carries out demodulation, recovers the downlink information data that transmitting terminal sends.
2. method according to claim 1, wherein the described transmitting terminal of step (5) carries out power control to M group transmitted signal vector, carries out as follows:
(5a) calculate M group transmitted signal vector X
1to X
mtotal mean power ε
x:
In formula,
expression is to the S in expression formula
mand H
mask expectation, min represents to ask minimum of a function value;
(5b) transmitting terminal is to M group transmitted signal vector X
1to X
mcarry out power control, obtain the signal phasor after power is controlled
In formula, ε
ethe transmitting power that represents physical device.
3. method according to claim 1, wherein the described receiving terminal of step (6) receives signal phasor Y to M group
1to Y
mcarry out gain compensation, be compensated rear signal phasor
In formula, ε
xrepresent M group transmitted signal vector X
1to X
mtotal mean power, ε
ethe transmitting power that represents physical device.
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|---|---|---|---|
| CN201410193497.3A CN103929396B (en) | 2014-05-08 | 2014-05-08 | processing method of MIMO-OFDM system downlink information data |
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Cited By (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104168237A (en) * | 2014-08-15 | 2014-11-26 | 西安电子科技大学 | Interference elimination method in MIMO alternating relay system on basis of amplifying and forwarding |
| CN106789775A (en) * | 2017-03-01 | 2017-05-31 | 吉林大学 | Logging cable high-speed data transmission method based on MIMO technology |
| CN106899332A (en) * | 2015-12-11 | 2017-06-27 | 北京信威通信技术股份有限公司 | Signaling method and device |
| CN107728166A (en) * | 2017-09-08 | 2018-02-23 | 哈尔滨工程大学 | A kind of more disturbance restraining methods of satellite navigation receiver based on time domain grouping processing |
| CN108781206A (en) * | 2016-03-31 | 2018-11-09 | 华为技术有限公司 | Method and apparatus for orthogonal signalling modulation |
| CN108833325A (en) * | 2018-06-08 | 2018-11-16 | 武汉理工大学 | A kind of new MIMO-OFDM nested design self-adaptive modulation method |
| CN110061941A (en) * | 2019-04-30 | 2019-07-26 | 蚌埠学院 | A kind of channel equalization method in 5G multi-carrier communications systems |
Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101854223A (en) * | 2009-03-31 | 2010-10-06 | 上海交通大学 | Generation method of vector quantization code book |
| EP2104259B1 (en) * | 2008-03-20 | 2012-11-14 | Kabushiki Kaisha Toshiba | MIMO wireless communication apparatus precoding information by perturbation prior to MIMO transmission |
| CN103297180A (en) * | 2012-03-02 | 2013-09-11 | 富士通株式会社 | Information feedback device and information feedback method |
-
2014
- 2014-05-08 CN CN201410193497.3A patent/CN103929396B/en active Active
Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP2104259B1 (en) * | 2008-03-20 | 2012-11-14 | Kabushiki Kaisha Toshiba | MIMO wireless communication apparatus precoding information by perturbation prior to MIMO transmission |
| CN101854223A (en) * | 2009-03-31 | 2010-10-06 | 上海交通大学 | Generation method of vector quantization code book |
| CN103297180A (en) * | 2012-03-02 | 2013-09-11 | 富士通株式会社 | Information feedback device and information feedback method |
Non-Patent Citations (1)
| Title |
|---|
| RUI CHEN等: ""Low complexity multi-user multi-stream MIMO vector perturbation precoder for FPGA implementation"", 《IEICE ELECTRONICS EXPRESS》 * |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN106899332A (en) * | 2015-12-11 | 2017-06-27 | 北京信威通信技术股份有限公司 | Signaling method and device |
| CN108781206A (en) * | 2016-03-31 | 2018-11-09 | 华为技术有限公司 | Method and apparatus for orthogonal signalling modulation |
| US10567210B2 (en) | 2016-03-31 | 2020-02-18 | Huawei Technologies Co., Ltd. | Method and apparatus for quadrature signal modulation |
| CN106789775A (en) * | 2017-03-01 | 2017-05-31 | 吉林大学 | Logging cable high-speed data transmission method based on MIMO technology |
| CN106789775B (en) * | 2017-03-01 | 2019-11-26 | 吉林大学 | Logging cable high-speed data transmission method based on MIMO technology |
| CN107728166A (en) * | 2017-09-08 | 2018-02-23 | 哈尔滨工程大学 | A kind of more disturbance restraining methods of satellite navigation receiver based on time domain grouping processing |
| CN107728166B (en) * | 2017-09-08 | 2020-12-22 | 哈尔滨工程大学 | Satellite navigation receiver multi-interference suppression method based on time domain packet processing |
| CN108833325A (en) * | 2018-06-08 | 2018-11-16 | 武汉理工大学 | A kind of new MIMO-OFDM nested design self-adaptive modulation method |
| CN108833325B (en) * | 2018-06-08 | 2020-07-24 | 武汉理工大学 | Novel MIMO-OFDM system grouping adaptive modulation method |
| CN110061941A (en) * | 2019-04-30 | 2019-07-26 | 蚌埠学院 | A kind of channel equalization method in 5G multi-carrier communications systems |
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