CN102368661B - Switching power supply with function of correcting power factor as well as control device and control method thereof - Google Patents
Switching power supply with function of correcting power factor as well as control device and control method thereof Download PDFInfo
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- CN102368661B CN102368661B CN201110033897.4A CN201110033897A CN102368661B CN 102368661 B CN102368661 B CN 102368661B CN 201110033897 A CN201110033897 A CN 201110033897A CN 102368661 B CN102368661 B CN 102368661B
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Abstract
The invention discloses a switching power supply with a function of correcting a power factor and a control device thereof. The control device of the switching power supply comprises a power factor corrector and a total harmonic distortion optimizer. An output end of the power factor corrector is connected with a power tube and the power factor corrector is used for determining turnon time and turnoff time of the power tube. An AC (alternate current) input voltage is input through an input end of the total harmonic distortion optimizer. An output end of the total harmonic distortion optimizer is connected with the power factor corrector. An AC input signal can be dynamically tracked by the total harmonic distortion optimizer. When the AC input voltage is increased, a peak current of an inductance of the switching power supply is reduced and a current that an AC power system charges a filter capacitor of the switching power supply is compensated; and when the AC input voltage is reduced, the peak current of the inductance of the switching power supply is increased and a current that the AC power system discharges the filter capacitor of the switching power supply is compensated. By utilizing the control device disclosed by the invention, the total harmonic distortion of the AC input current caused by the filter capacitor can be reduced and the power factor of the switching power supply is improved.
Description
Technical field
The present invention relates to field of switch power, relate in particular to the there is power factor correction Switching Power Supply control technology of (Power Factor Correction, PFC).
Background technology
From 220V, exchange (Alternating Current, AC) electrical network is supplied with direct current (Direct Current through conversion, DC) be in power electronic technology and electronic instrument, to apply a kind of basic conversion equipment very widely, computer for example, television set, display, the modern conventional electric equipment of fluorescent lamp etc. all can adopt AC-DC Switching Power Supply to power.
At present conventional AC-DC Switching Power Supply is generally comprised of power factor correction (PFC) device and DC-DC transducer, wherein said power factor corrector is as preconditioner, control and exchange input current, force and exchange input current waveform tracking interchange input sinusoidal voltage waveform, can approach sine wave so that exchange input current waveform.
Described power factor corrector reduces to exchange the harmonic components of input current on the one hand, and the harmonic component that exchanges input current the inside can flow backwards, and enters AC network, thus the harmonic pollution that causes to AC network; On the other hand, reduce to exchange the total harmonic distortion (Total Harmonic Distortion, THD) of input current, improve the power factor of described Switching Power Supply, can make power factor PF value approach 1.
Described power factor corrector adopts boost converter to realize, and this boost converter is one of the most frequently used topology for described power factor corrector.Boost topology can be operated in required power pattern, for example, can be operated in continuous conduction mode (CCM), be interrupted in conduction mode (DCM) and critical conduction mode (TM).
Simple in structure being widely used in middle low power applications of power factor corrector due to TM pattern.In general, the power factor corrector of TM pattern can have two kinds of implementations below: the one, and the power factor corrector of the TM pattern of controlling based on permanent ON time; The 2nd, the power factor corrector of the TM pattern based on multiplier.It has been generally acknowledged that these two kinds of technology provide substantially the same performance level.
As example, provide as shown in Figure 1 a kind of topological structure of Switching Power Supply of power factor corrector of traditional TM pattern based on multiplier.Switching Power Supply 100 in example comprises a boost converter and a power factor correcting 101.Described power factor corrector is the structure of the TM pattern based on multiplier.
Described boost converter comprises a diode full-wave rectification bridge 103, referred to as rectifier bridge.The input signal of described rectifier bridge is AC-input voltage.One end of a high-frequency filter capacitor Cin is connected to described rectifier bridge, the other end ground connection of filter capacitor Cin.An inductance L 1 is connected to the common port of filter capacitor Cin and described rectifier bridge, and other one end of inductance L 1 is connected to the drain terminal of a power tube M1, and the source of power tube M1 is connected to the sampling resistor Rs of a ground connection.The anodic bonding of a diode D1 is to the common port of inductance L 1 and power tube M1, and negative electrode is received one end of a capacitor C bulk, the other one end of capacitor C bulk ground connection.Described boost converter produces one on capacitor C bulk, and much larger than the VD that exchanges input maximum peak voltage, representative value is generally 400V, and described VD is provided for DC-DC transducer subsequently.
Described power factor corrector comprises:
Electric current induction comparator 106, the output signal Sm of described multiplier is provided described electric current induction comparator, as its input signal.The input of described electric current induction comparator another one is to flow through the voltage Srs that the electric current of described power tube produces on sampling resistor Rs, is called for short current sampling signal Srs.In some implementation, when described electric current induction comparator determines that two voltages in input equate, described electric current induction comparator resets trigger 108, and power tube M1 is turn-offed.After being processed by described power factor corrector, inductance L 1 peak current of described boost converter is by the sinusoidal waveform institute envelope through rectification.Can prove that described power factor corrector has produced constant ON time within the half period of input ac voltage.
After power tube M1 is turned off, diode D1 is because current continuity is forward biased.As a part for Boost topology, inductance L 1 will be discharged into the energy of its storage in the load of described Switching Power Supply.When inductance L 1 electric current drops to zero, zero current detector 107 detects the zero current condition of described inductance by coupling coil L2.The output of described zero current detector is connected to the set end of described trigger.When described zero current detector detects zero current, described zero current detector is set described trigger.When described trigger is set, power tube M1 starts conducting.At the duration of work of described Switching Power Supply, described trigger is by set and reset repeatedly.
In order to meet EMI requirement, described Switching Power Supply increases a little high-frequency filter capacitor Cin below at rectifier bridge 103.Due to the existence of filter capacitor Cin, cause described Switching Power Supply can run into the problem of intermodulation distortion, the harmonic component that exchanges input current is increased, it is large that the distortion factor becomes, thereby cause the power factor value of described Switching Power Supply to diminish.
Traditional method thinks that intermodulation distortion occurs in AC-input voltage between tour.More specifically, intermodulation distortion often occurs in AC-input voltage and drops to while approaching near 0 volt.When AC-input voltage drop to approach 0 volt near time, because the remnants on filter capacitor Cin are detained voltage, the diode of described rectifier bridge is reverse biased, the described remaining voltage that is detained is associated with filter capacitor Cin and described rectifier bridge.During this period, do not exchange input current and flow out from described rectifier bridge.As a result, the waveform of interchange input current may present intermodulation distortion effect.Cause AC-input voltage to drop to and approach at 0 o'clock, the voltage on filter capacitor Cin can depart from ideal value conventionally within a bit of time.
As shown in Figure 2, due to the existence of filter capacitor Cin, make AC-input voltage during voltage zero-cross, produce distortion after rectification, can cause exchanging input current and also can produce distortion when zero passage, and then make to exchange the input current distortion factor and increase.
Traditional method is in order to reduce intermodulation distortion effect, the method adopting is to approach very much in zero in AC-input voltage, extend the ON time of described power tube, electric charge on described filter capacitor is bled off to some more, just can reduce voltage distortion on described filter capacitor, thereby reach the object of optimizing the total harmonic distortion that exchanges input current.
Yet described traditional method but exists some deficiency, main cause is it on exchanging the analysis of input current total harmonic distortion impact, some is unilateral and careful not on filter capacitor Cin.In fact the main cause that exchanges input current generation total harmonic distortion is because described filter capacitor Cin can produce charging and discharging electric current.This electric current input that is added to, causes actual interchange input current and AC-input voltage homophase completely.When the electric current providing when the electric discharge of described filter capacitor in addition just can offer output circuit, AC network is input current more just, produces so-called conducting dead angle.
Electric current above described filter capacitor is:
I
Cin＝Cin×U
0×ω×cosωt (1)
U wherein
0be alternating current input voltage magnitude, ω is frequency input signal, and Cin is described filter capacitor capacitance.
When described filter capacitor discharging current surpasses output current I
otime, AC network is input current more just.Therefore conducting dead angle is:
α＝arccos(I
O/(Cin×U
0×ω)) (2)
From formula, can find out that conducting dead angle is with AC-input voltage, the relation between described filter capacitor and output current.
As shown in Figure 2, described filter capacitor Cin charges within the half period of the rising of AC-input voltage, in the half period declining, discharges in AC-input voltage.When AC-input voltage zero passage, the charging and discharging currents of described filter capacitor reaches maximum, and consequent current distortion is also maximum.
Described traditional method is not considered, at voltage zero-cross place, described filter capacitor becomes the situation of maximum charging current from maximum discharge current, therefore described traditional method just approaches in zero in AC-input voltage very much, extend the ON time of described power tube, electric charge above described filter capacitor is bled off to some more, is the charging and discharging currents distortion can not full remuneration producing due to described filter capacitor, the distortion producing in the time of can only compensating described filter capacitor maximum discharge current.
In described filter capacitor charging:
I
IN＝I
CC+I
L (3)
And in described filter capacitor electric discharge:
I
IN+I
CD＝I
L (4)
I wherein
iNto exchange input current, I
ldescribed inductance peak current, I
cCdescribed filter capacitor charging current, I
cDit is described filtered circuit discharging current.
Because current waveform distortion is to cause because described filter capacitor discharges and recharges, so in order to optimize total harmonic distortion, must compensate because described filter capacitor discharges and recharges the current waveform distortion causing.
Summary of the invention
The present invention will solve the deficiency of the total harmonic distortion optimization method existence of current power factor adjuster, and a kind of switch power controller and control method thereof with power factor correction is provided.The present invention simultaneously has also offered a kind of Switching Power Supply with power factor correction.
The Switching Power Supply with power factor correction comprises:
One switch power converter, converts AC-input voltage to direct-flow output signal.Described switch power converter comprises a high-frequency filter capacitor, an inductance and a power tube;
One Switching Power Supply control device, described Switching Power Supply control device comprises a power factor corrector and a total harmonic distortion optimization device, the output of described power factor corrector connects described power tube, determines ON time and the turn-off time of described power tube.The input input AC input voltage of described total harmonic distortion optimization device, output connects power factor corrector, can dynamically follow the tracks of ac input signal, when AC-input voltage increases, reduce the peak current of described inductance, the electric current of compensation AC network to described filter capacitor charging; When AC-input voltage reduces, increase the peak current of described inductance, the electric current of compensation AC network to described filter capacitor electric discharge.
Described power factor corrector comprises:
One error amplifier, the inverting input of described error amplifier is the dividing potential drop of the VD of Switching Power Supply, the normal phase input end of described error amplifier is reference voltage;
One multiplier, the rectification and voltage division signal that an input of described multiplier is AC-input voltage; Another input of described multiplier is from the output signal of described error amplifier;
One electric current induction comparator, the output signal of more described multiplier and current sampling signal, the output of described electric current induction comparator connects trigger, and the output signal of electric current induction comparator has determined the turn-off time of described power tube;
One zero current detector, the zero current condition in the inductance being used in sense switch power supply changeover device, the output of described zero current comparator connects described trigger, and the output signal of zero current comparator has determined the ON time of described power tube;
One trigger, the output of described trigger connects drive circuit;
One drive circuit, the output of described drive circuit connects described power tube.
Wherein, described current sampling signal is the voltage that the electric current of described power tube produces on sampling resistor Rs;
Further, described total harmonic distortion optimization device, can dynamically follow the tracks of ac input signal, when AC-input voltage increases, reduces the value of the output signal of described multiplier, or increases the value of described current sampling signal; When AC-input voltage reduces, increase the value of the output signal of described multiplier, or reduce the value of described current sampling signal.
The control method with the Switching Power Supply of power factor correction, comprising:
Step 3, multiplies each other described error amplification signal and described ac input signal to produce a product signal;
Step 4, compares described product signal and sampled signal, when described sampled signal is equal to or greater than described product signal, produces a power tube cut-off signals, stops from inductance Absorption Current;
Step 5, compares detection signal and the second reference signal, when described detection signal is equal to or less than described the second reference signal, produces a power tube Continuity signal, starts from described inductance Absorption Current.
When ac input signal increases, reduce the peak current of described inductance, the electric current of compensation AC network to described filter capacitor charging; When ac input signal reduces, increase the peak current of described inductance, the electric current of compensation AC network to described filter capacitor electric discharge.
Wherein, described sampled signal represents that current sampling signal is the voltage that the electric current of described power tube produces on sampling resistor; Wherein, described detection signal represents that coupling coil detects the zero current condition of described inductance.
The Switching Power Supply that the present invention proposes and control device thereof can reduce the total harmonic distortion of the interchange input current that described filter capacitor causes, improve the power factor of described Switching Power Supply.
Accompanying drawing explanation
Fig. 1 is the topological structure of Switching Power Supply of the power factor correction of the traditional TM pattern based on multiplier;
Fig. 2 is the input current of the Switching Power Supply shown in Fig. 1, voltage and filter capacitor Charge-discharge wave shape
Fig. 3 is the topological structure that the present invention proposes to have the switching power unit of power factor correction;
Fig. 4 is first specific embodiment of total harmonic distortion optimization device of the present invention;
Fig. 5 is second specific embodiment of total harmonic distortion optimization device of the present invention;
Fig. 6 is the topological structure of voltage rising or decline detector;
Fig. 7 is the 3rd specific embodiment of total harmonic distortion optimization device of the present invention;
Fig. 8 is the 4th specific embodiment of total harmonic distortion optimization device of the present invention;
Fig. 9 is the possible topological structure that in the present invention, filter capacitor discharges and recharges analog circuit.
Embodiment
Below in conjunction with accompanying drawing, further describe invention essence of the present invention and concrete technical scheme.
Fig. 3 is the Switching Power Supply with power factor correction that the present invention proposes, and this Switching Power Supply is the topological structure of the TM pattern based on multiplier.
Switching Power Supply 300 in Fig. 3 comprises a boost converter and a Switching Power Supply control device 301:
Described boost converter comprises a diode full-wave rectification bridge 303, referred to as rectifier bridge.The input signal of described rectifier bridge is AC-input voltage.One end of a high-frequency filter capacitor Cin is connected to described rectifier bridge, the other end ground connection of filter capacitor Cin.An inductance L 1 is connected to the common port of filter capacitor Cin and described rectifier bridge, and other one end of inductance L 1 is connected to the drain terminal of a power tube M1, and the source of power tube M1 is connected to the sampling resistor Rs of a ground connection.The anodic bonding of a diode D1 is to the common port of inductance L 1 and power tube M1, and negative electrode is received one end of a capacitor C bulk, the other one end of capacitor C bulk ground connection.Described switch power converter produces one on capacitor C bulk, and much larger than the VD that exchanges input maximum peak voltage, representative value is generally 400V, and described VD is provided for DC-DC transducer subsequently.
Described Switching Power Supply control device 301 comprises a power factor corrector 311 and a total harmonic distortion optimization device 310
Described power factor corrector comprises:
One error amplifier 304, described error amplifier is two input signals relatively: the input signal of its inverting input is the dividing potential drop that the VD of described switch power converter produces by resistance R _ f a and resistance R _ f b; The input signal of its normal phase input end is internal reference voltage VREF.Describedly misplace the amplifying signal that output signal Se is error between two input signals.Between the inverting input of error amplifier and output, there is a compensating network 302.
One multiplier 305, the described output signal Se that misplaces is provided for described multiplier 305, described multiplier 305 another one input signals are that AC-input voltage is through after described rectifier bridge rectification, the dividing potential drop Vi producing by resistance R 1a and resistance R 1b again, be called for short rectification and voltage division signal, the output signal Sm of multiplier is the product of two input signals.
One electric current induction comparator 306, the output signal Sm of described multiplier is provided described electric current induction comparator, as its input signal; The input of described electric current induction comparator another one is to flow through the voltage Srs that the electric current of described power tube produces on sampling resistor Rs, is called for short current sampling signal.The output of described electric current induction comparator connects trigger 308, and described electric current induction comparator output signal has determined the turn-off time of described power tube.
One zero current detector 307, the zero current condition in the inductance being used in sense switch power supply changeover device, the output of described zero current comparator 307 connects described trigger, and the output signal of zero current comparator has determined the ON time of described power tube.
One drive circuit 309, the input of described drive circuit is the output signal of described trigger, the output of described drive circuit connects power tube M1.
After being processed by described power factor corrector, inductance L 1 peak current of described switch power converter is by the sinusoidal waveform institute envelope through rectification.For example, can prove in half period of described power factor corrector place input ac voltage and produce constant ON time.
After power tube M1 is turned off, diode D1 is because current continuity is forward biased.As a part for Boost topology, inductance L 1 will be discharged into the energy of its storage in the load of described Switching Power Supply.When inductance L 1 electric current drops to zero, described zero current detector is by the zero current condition that described inductance detected of coupling coil L2.The output of described zero current detector is connected to the set end of described trigger.When described zero current detector detects zero current, described zero current detector is set described trigger.When described trigger is set, described power tube M1 starts conducting.At described Switching Power Supply duration of work, described trigger is by set and reset repeatedly.
Described total harmonic distortion optimization device 310 is accepted from rectification and voltage division signal Vi, exports a total harmonic distortion (THD) and optimizes signal Ctrl.Can dynamically follow the tracks of ac input signal, when AC-input voltage increases, reduce the value of the output signal Sm of described multiplier 305, or increase the value of described current sampling signal Srs; When AC-input voltage reduces, increase the value of the output signal Sm of described multiplier 305, or reduce the value of described current sampling signal Srs.Described total harmonic distortion optimization device can reduce the total harmonic distortion of the interchange input current that described filter capacitor causes, improves the power factor of described Switching Power Supply.
Described Switching Power Supply control device is chip.
Fig. 4 is first specific embodiment of described total harmonic distortion optimization device, and described total harmonic distortion optimization device comprises:
One subtracter 401, from a constant signal A1, after deducting rectification and voltage division signal Vi, through a weighter 402, produces an offset compensation signal Vi1;
One voltage rises or decline detector 403, and described voltage rising or decline detector, according to rectification and voltage division signal Vi, judge that described rectification and voltage division signal Vi is in enlarging state, still reduce state.When described rectification and voltage division signal Vi increases, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal Ctrl, equals negative offset compensation signal Vi1; When described rectification and voltage division signal Vi reduces, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal Ctrl, equals positive offset compensation signal Vi1;
One adder 404, adds the above total harmonic distortion (THD) optimization signal Ctrl from the output signal Sm the inside of multiplier 305, offers the inverting input of electric current induction comparator 306.
Fig. 5 is second specific embodiment of described total harmonic distortion optimization device.Described total harmonic distortion optimization device comprises:
One subtracter 501, from a constant signal A1, after deducting rectification and voltage division signal Vi, through a weighter 502, produces an offset compensation signal Vi1;
One voltage rises or decline detector 503, and described voltage rising or decline detector, according to rectification and voltage division signal Vi, judge that described rectification and voltage division signal Vi is in enlarging state, still reduce state.When described rectification and voltage division signal Vi increases, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal Ctrl, equals negative offset compensation signal Vi1; When described rectification and voltage division signal Vi reduces, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal Ctrl, equals positive offset compensation signal Vi1;
A subtracter 504, deducts total harmonic distortion (THD) from current sampling signal Srs the inside and optimizes signal Ctrl, offers the normal phase input end of electric current induction comparator 306.
Fig. 6 is a specific embodiment of the rising of voltage described in Fig. 4 or Fig. 5 or decline detector.The basic thought of described voltage rising or decline detector 600 is to use the method for sampling hold circuit and currency comparison to detect rising and falling waveform: when above up voltage is higher than the maintenance a certain value of voltage (being assumed to be 50mV), and rising edge sampling; Drop-out voltage when keeping a certain value of voltage (being assumed to be 50mV), trailing edge sampling; When rise and fall voltage (is assumed to be 50mV) with maintenance voltage deviation in a certain value, do not sample.
Described rectification and voltage division signal Vi is provided for level shift module 601.Described level shift module produces three level shift signals respectively: the first level shift signal V0 equals described rectification and voltage division signal Vi; Second electrical level displacement signal Va equals described rectification and voltage division signal Vi and adds a deviation delta; The 3rd level shift signal Vb equals described rectification and voltage division signal Vi and deducts a deviation delta.Described second electrical level displacement signal Va offers lower down-sampled comparator 602; Described the 3rd level shift signal Vb offers up-samples comparator 603.Electric capacity 607 inhibit signal Vsamp is above simultaneously provided to described up-samples comparator and described lower down-sampled comparator.
Described lower down-sampled comparator more described second electrical level displacement signal Va and described inhibit signal Vsamp, produce decline sampled signal Vc and offer rest-set flip-flop 605 and sampling pulse generator 604.The 3rd level shift signal Vb and described inhibit signal Vsamp that described up-samples comparator is relatively more described, produce up-samples signal Vd and offer described rest-set flip-flop and described sampling pulse generator.Described sampling pulse generator control switch 606 is sampled when described switch is closed, and described inhibit signal Vsamp equals described the first level shift signal V0, namely described rectification and voltage division signal Vi; When described switch disconnects, because electric capacity 607 exists, enter the maintenance stage.Described rest-set flip-flop produces judgement signal Ve.
The effect of described sampling pulse generator is in described decline sampled signal Vc or described up-samples signal Vd, to have one by low, to be jumped to when high, the pulse of exporting a high level fixed pulse width, and closed described switch, enters sample phase.
Described voltage raises or reduces sensors work process: the incipient stage, described sampling pulse generator is action not, and therefore described switch disconnects.If described rectification and voltage division signal Vi raises, described decline sampled signal Vc is always zero.Therefore as long as described up-samples comparator uprises once, described judgement signal Ve is always 1, represents that described rectification and voltage division signal Vi is in rising state.Owing to needing only described the 3rd level shift signal Vb higher than described inhibit signal Vsamp, just there is saltus step in described up-samples comparator, cause described in the signal controlling of a high level fixed pulse width of described sampling pulse generator output switch closed, will sample described rectification and voltage division signal Vi to electric capacity 607.So described rectification and voltage division signal Vi uphill process, the maximum difference of inhibit signal Vsamp and described rectification and voltage division signal Vi is less than Δ.
If described rectification and voltage division signal Vi voltage drop, described up-samples signal Vd is always zero.Therefore as long as described lower down-sampled comparator uprises once, described judgement signal Ve is always 0, represents in described rectification and voltage division signal Vi decline state.Owing to needing only described second electrical level displacement signal Va lower than described inhibit signal Vsamp, just there is saltus step in described lower down-sampled comparator, cause described in the signal controlling of a high level fixed pulse width of described sampling pulse generator output switch closed, will sample described rectification and voltage division signal Vi voltage to electric capacity 607.So described rectification and voltage division signal Vi decline process, the maximum difference of inhibit signal Vsamp and described rectification and voltage division signal Vi is less than Δ.The object of Δ setting is in order to prevent circuit generation misoperation.
Described voltage raises or reduces the judgement signal Ve that detector produces.While being described rectification and voltage division signal Vi rising (Ve is 1), represent the filter capacitor Cin charging stage, reduce the peak current of described inductance, the electric current of compensation AC network to described filter capacitor charging; When described rectification and voltage division signal Vi reduces (Ve is 0), represent described filter capacitor Cin discharge regime, increase the peak current of described inductance, the electric current of compensation AC network to described filter capacitor electric discharge.
Fig. 7 is the 3rd specific embodiment of described total harmonic distortion optimization device, and described total harmonic distortion optimization device comprises:
One filter capacitor discharges and recharges analog circuit 702, can carry out the charge and discharge process of analog filtering capacitor C according to rectification and voltage division signal Vi and capacitor C 1, produces total harmonic distortion (THD) and optimizes signal Ctrl;
One adder 703, adds total harmonic distortion (THD) optimization signal Ctrl from the output signal Sm the inside of described multiplier, offers the inverting input of electric current induction comparator 306.
Fig. 8 is the 4th specific embodiment of described total harmonic distortion optimization device, and described total harmonic distortion optimization device comprises:
One filter capacitor discharges and recharges analog circuit 802, can carry out the charge and discharge process of analog filtering capacitor C according to rectification and voltage division signal Vi and capacitor C 1, produces total harmonic distortion (THD) and optimizes signal Ctrl;
One subtracter 803, deducts total harmonic distortion (THD) from described current sampling signal Srs the inside and optimizes signal Ctrl, offers the normal phase input end of electric current induction comparator 306.
Fig. 9 is the possible topological structure that the filter capacitor shown in Fig. 7 or Fig. 8 discharges and recharges analog circuit.The base input signal of the one NPN pipe Q1 is rectification and voltage division signal (Vi), the collector electrode of the one NPN pipe Q1 is received power supply, the emitter of the one NPN pipe Q1 is received the constant-current source I2 of a ground connection, and the base stage of the 4th PNP pipe Q4 is received the common port of a NPN pipe Q1 and constant-current source I2; The base input signal of the 2nd PNP pipe Q2 is rectification and voltage division signal Vi, the collector electrode of the 2nd PNP pipe Q2 is received ground, the emitter of the 2nd PNP pipe Q2 is received a constant-current source I1 who connects power supply, and the base stage of the 3rd NPN pipe Q3 is received the common port of the 2nd PNP pipe Q2 and constant-current source I1; The emitter of the 3rd NPN pipe Q3 is connected with the emitter of the 4th PNP pipe Q4, receives other one end ground connection of the first described capacitor C 1, the first capacitor C 1; The collector electrode of the 3rd NPN pipe Q3 is received the input stage of the current mirror being comprised of a PMOS pipe M1 and the 2nd PMOS pipe M2; The collector electrode of the 4th PNP pipe Q4 is received the input stage of the current mirror being comprised of the 3rd NMOS pipe M3 and the 4th NMOS pipe M4, and the output stage of two described current mirrors is connected, and exports described total harmonic distortion optimization signal (Ctrl)
The invention discloses a kind of switching power unit that can reduce the power factor controlling of intermodulation distortion, and describe the specific embodiment of the present invention and effect with reference to the accompanying drawings.What should be understood that is that above-described embodiment is just to explanation of the present invention; rather than limitation of the present invention; any innovation and creation that do not exceed within the scope of connotation of the present invention; comprise that total harmonic distortion optimization device, voltage rising or decline detector, filter capacitor discharge and recharge the change of analog circuit and the replacement of other unsubstantialities or modification, within all falling into protection range of the present invention.
Claims (17)
1. the Switching Power Supply with power factor correction, comprising:
One switch power converter, converts AC-input voltage to direct-flow output signal, and described switch power converter comprises rectifier bridge, fly-wheel diode, shunt capacitance, high-frequency filter capacitor, an inductance and a power tube; With a Switching Power Supply control device;
Described Switching Power Supply control device comprises a power factor corrector and a total harmonic distortion optimization device, the output of described power factor corrector connects described power tube, determine ON time and the turn-off time of described power tube, the input input AC input voltage of described total harmonic distortion optimization device, output connects power factor corrector, can dynamically follow the tracks of ac input signal, when AC-input voltage increases, reduce the peak current of described inductance, the electric current of compensation AC network to described filter capacitor charging; When AC-input voltage reduces, increase the peak current of described inductance, the electric current of compensation AC network to described filter capacitor electric discharge;
It is characterized in that, described total harmonic distortion optimization device is a kind of in following manner:
(1) described total harmonic distortion optimization device comprises:
One subtracter, from a constant signal (A1), deducts rectification and voltage division signal (Vi) afterwards, through a weighter, produces an offset compensation signal (Vi1);
One voltage rises or decline detector, described voltage rising or decline detector are according to rectification and voltage division signal (Vi), judge that described rectification and voltage division signal (Vi) is in enlarging state, still reduce state: when described rectification and voltage division signal Vi increases, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal (Ctrl), equals negative offset compensation signal (Vi1); When described rectification and voltage division signal (Vi) reduces, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal (Ctrl), equals positive offset compensation signal (Vi1);
One adder, adds the above total harmonic distortion (THD) optimization signal (Ctrl) from the output signal Sm the inside of multiplier, offers the inverting input of electric current induction comparator;
Or (2) described total harmonic distortion optimization device comprises:
One subtracter, from a constant signal (A1), deducts rectification and voltage division signal (Vi) afterwards, through a weighter, produces an offset compensation signal (Vi1);
One voltage rises or decline detector, described voltage rising or decline detector are according to rectification and voltage division signal (Vi), judge that described rectification and voltage division signal (Vi) is in enlarging state, still reduce state, when described rectification and voltage division signal (Vi) increases, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal (Ctrl), equals negative offset compensation signal (Vi1); When described rectification and voltage division signal Vi reduces, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal (Ctrl), equals positive offset compensation signal (Vi1);
A subtracter, deducts total harmonic distortion (THD) from current sampling signal (Srs) the inside and optimizes signal (Ctrl), offers the normal phase input end of electric current induction comparator.
2. there is as claimed in claim 1 the Switching Power Supply of power factor correction, it is characterized in that described power factor corrector comprises:
One error amplifier, the inverting input of described error amplifier is the dividing potential drop of the VD of Switching Power Supply, the normal phase input end of described error amplifier is reference voltage, amplifies the dividing potential drop of described VD and the error between reference voltage;
One multiplier, the rectification and voltage division signal that an input of described multiplier is AC-input voltage; Another input of described multiplier is from the output signal of described error amplifier, and multiplier is by the signal multiplication of two input;
One electric current induction comparator, the output signal of more described multiplier and current sampling signal, the output of described electric current induction comparator connects trigger, and the output signal of electric current induction comparator has determined the turn-off time of described power tube;
One zero current detector, the zero current condition in the inductance being used in sense switch power supply changeover device, the output of described zero current comparator connects described trigger, and the output signal of zero current comparator has determined the ON time of described power tube;
One trigger, the output of described trigger connects drive circuit;
One drive circuit, the output of described drive circuit connects described power tube.
3. there is as claimed in claim 2 the Switching Power Supply of power factor correction, it is characterized in that described current sampling signal is the voltage that the electric current of described power tube produces on sampling resistor.
4. there is as claimed in claim 2 the Switching Power Supply of power factor correction, it is characterized in that described total harmonic distortion optimization device, can dynamically follow the tracks of ac input signal, when AC-input voltage increases, reduce the value of the output signal of described multiplier, or increase the value of described current sampling signal; When AC-input voltage reduces, increase the value of the output signal of described multiplier, or reduce the value of described current sampling signal.
5. there is as claimed in claim 1 the Switching Power Supply of power factor correction, it is characterized in that described voltage rises or the implementation of decline detector is: described rectification and voltage division signal (Vi) is provided for to level shift module, and described level shift module produces three level shift signals respectively: the first level shift signal (V0) equals described rectification and voltage division signal (Vi), second electrical level displacement signal (Va) equals described rectification and voltage division signal (Vi) and adds a deviation delta, the 3rd level shift signal (Vb) equals described rectification and voltage division signal (Vi) and deducts a deviation delta, and described second electrical level displacement signal (Va) offers lower down-sampled comparator, described the 3rd level shift signal (Vb) offers up-samples comparator, and the inhibit signal Vsamp above electric capacity is simultaneously provided to described up-samples comparator and described lower down-sampled comparator, the described more described second electrical level displacement signal of lower down-sampled comparator (Va) and described inhibit signal (Vsamp), produce decline sampled signal (Vc) and offer rest-set flip-flop and sampling pulse generator, the 3rd level shift signal (Vb) and described inhibit signal (Vsamp) that described up-samples comparator is relatively more described, produce up-samples signal (Vd) and offer described rest-set flip-flop and described sampling pulse generator, described sampling pulse generator control switch, when described switch is closed, sample, described inhibit signal (Vsamp) equals described the first level shift signal (V0), described rectification and voltage division signal (Vi) namely, when described switch disconnects, because electric capacity exists, enter the maintenance stage, described rest-set flip-flop produces judgement signal Ve.
6. there is as claimed in claim 1 the Switching Power Supply of power factor correction, it is characterized in that the base input signal that filter capacitor discharges and recharges a NPN pipe Q1 of analog circuit is rectification and voltage division signal (Vi), the collector electrode of the one NPN pipe Q1 is received power supply, the emitter of the one NPN pipe Q1 is received the constant-current source I2 of a ground connection, and the base stage of the 4th PNP pipe Q4 is received the common port of a NPN pipe Q1 and constant-current source I2; The base input signal of the 2nd PNP pipe Q2 is rectification and voltage division signal Vi, the collector electrode of the 2nd PNP pipe Q2 is received ground, the emitter of the 2nd PNP pipe Q2 is received a constant-current source I1 who connects power supply, and the base stage of the 3rd NPN pipe Q3 is received the common port of the 2nd PNP pipe Q2 and constant-current source I1; The emitter of the 3rd NPN pipe Q3 is connected with the emitter of the 4th PNP pipe Q4, receives other one end ground connection of the first capacitor C 1, the first capacitor C 1; The collector electrode of the 3rd NPN pipe Q3 is received the input stage of the current mirror being comprised of a PMOS pipe M1 and the 2nd PMOS pipe M2; The collector electrode of the 4th PNP pipe Q4 is received the input stage of the current mirror being comprised of the 3rd NMOS pipe M3 and the 4th NMOS pipe M4, and the output stage of two current mirrors is connected, and exports described total harmonic distortion optimization signal (Ctrl).
7. the control device with the Switching Power Supply of power factor correction, comprise a power factor corrector and a total harmonic distortion optimization device: the power tube of the output connecting valve power supply of described power factor corrector, determines ON time and the turn-off time of described power tube; The input input AC input voltage of described total harmonic distortion optimization device, output connects power factor corrector, can dynamically follow the tracks of ac input signal, when AC-input voltage increases, reduce the peak current of inductance, the electric current of compensation AC network to the filter capacitor charging of Switching Power Supply; When AC-input voltage reduces, increase the peak current of Switching Power Supply inductance, the electric current of compensation AC network to the filter capacitor electric discharge of Switching Power Supply;
It is characterized in that: described total harmonic distortion optimization device is a kind of in following manner;
(1) described total harmonic distortion optimization device comprises:
One subtracter, from a constant signal (A1), deducts rectification and voltage division signal (Vi) afterwards, through a weighter, produces an offset compensation signal (Vi1);
One voltage rises or decline detector, described voltage rising or decline detector are according to rectification and voltage division signal (Vi), judge that described rectification and voltage division signal (Vi) is in enlarging state, still reduce state: when described rectification and voltage division signal Vi increases, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal (Ctrl), equals negative offset compensation signal (Vi1); When described rectification and voltage division signal (Vi) reduces, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal (Ctrl), equals positive offset compensation signal (Vi1);
One adder, adds the above total harmonic distortion (THD) optimization signal (Ctrl) from the output signal Sm the inside of multiplier, offers the inverting input of electric current induction comparator;
Or (2) described total harmonic distortion optimization device comprises:
One subtracter, from a constant signal (A1), deducts rectification and voltage division signal (Vi) afterwards, through a weighter, produces an offset compensation signal (Vi1);
One voltage rises or decline detector, described voltage rising or decline detector are according to rectification and voltage division signal (Vi), judge that described rectification and voltage division signal (Vi) is in enlarging state, still reduce state, when described rectification and voltage division signal (Vi) increases, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal (Ctrl), equals negative offset compensation signal (Vi1); When described rectification and voltage division signal Vi reduces, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal (Ctrl), equals positive offset compensation signal (Vi1);
A subtracter, deducts total harmonic distortion (THD) from current sampling signal (Srs) the inside and optimizes signal (Ctrl), offers the normal phase input end of electric current induction comparator.
8. there is as claimed in claim 7 the control device of the Switching Power Supply of power factor correction, it is characterized in that described power factor corrector comprises:
One error amplifier, the inverting input of described error amplifier is the dividing potential drop of the VD of Switching Power Supply, the normal phase input end of described error amplifier is reference voltage, amplifies the dividing potential drop of described VD and the error between reference voltage;
One multiplier, the rectification and voltage division signal that an input of described multiplier is AC-input voltage; Another input of described multiplier is from the output signal of described error amplifier, and multiplier is by the signal multiplication of two input;
One electric current induction comparator, the output signal of more described multiplier and current sampling signal, the output of described electric current induction comparator connects trigger, and the output signal of electric current induction comparator has determined the turn-off time of described power tube;
One zero current detector, the zero current condition in the inductance being used in sense switch power supply changeover device, the output of described zero current comparator connects described trigger, and the output signal of zero current comparator has determined the ON time of described power tube;
One trigger, the output of described trigger connects drive circuit;
One drive circuit, the output of described drive circuit connects described power tube.
9. there is as claimed in claim 8 the control device of the Switching Power Supply of power factor correction, it is characterized in that described current sampling signal is the voltage that the electric current of described power tube produces on sampling resistor.
10. there is as claimed in claim 8 the control device of the Switching Power Supply of power factor correction, it is characterized in that described total harmonic distortion optimization device, can dynamically follow the tracks of ac input signal, when AC-input voltage increases, reduce the value of the output signal of multiplier, or increase the value of described current sampling signal; When AC-input voltage reduces, increase the value of the output signal of described multiplier, or reduce the value of described current sampling signal.
11. have the control device of the Switching Power Supply of power factor correction as claimed in claim 7, it is characterized in that described voltage rises or the implementation of decline detector is: described rectification and voltage division signal (Vi) is provided for to level shift module, described level shift module produces three level shift signals respectively: the first level shift signal (V0) equals described rectification and voltage division signal (Vi), second electrical level displacement signal (Va) equals described rectification and voltage division signal (Vi) and adds a deviation delta, the 3rd level shift signal (Vb) equals described rectification and voltage division signal (Vi) and deducts a deviation delta, and described second electrical level displacement signal (Va) offers lower down-sampled comparator, described the 3rd level shift signal (Vb) offers up-samples comparator, and the inhibit signal above electric capacity (Vsamp) is simultaneously provided to described up-samples comparator and described lower down-sampled comparator, the described more described second electrical level displacement signal of lower down-sampled comparator (Va) and described inhibit signal (Vsamp), produce decline sampled signal (Vc) and offer rest-set flip-flop and sampling pulse generator, the 3rd level shift signal (Vb) and described inhibit signal (Vsamp) that described up-samples comparator is relatively more described, produce up-samples signal (Vd) and offer described rest-set flip-flop and described sampling pulse generator, described sampling pulse generator control switch, when described switch is closed, sample, described inhibit signal Vsamp equals described the first level shift signal (V0), described rectification and voltage division signal (Vi) namely, when described switch disconnects, because electric capacity exists, enter the maintenance stage, described rest-set flip-flop produces judgement signal (Ve).
12. have the control device of the Switching Power Supply of power factor correction as claimed in claim 7, it is characterized in that the base input signal that filter capacitor discharges and recharges a NPN pipe Q1 of analog circuit is rectification and voltage division signal (Vi), the collector electrode of the one NPN pipe Q1 is received power supply, the emitter of the one NPN pipe Q1 is received the constant-current source I2 of a ground connection, and the base stage of the 4th PNP pipe Q4 is received the common port of a NPN pipe Q1 and constant-current source I2; The base input signal of the 2nd PNP pipe Q2 is rectification and voltage division signal Vi, the collector electrode of the 2nd PNP pipe Q2 is received ground, the emitter of the 2nd PNP pipe Q2 is received a constant-current source I1 who connects power supply, and the base stage of the 3rd NPN pipe Q3 is received the common port of the 2nd PNP pipe Q2 and constant-current source I1; The emitter of the 3rd NPN pipe Q3 is connected with the emitter of the 4th PNP pipe Q4, receives other one end ground connection of the first capacitor C 1, the first capacitor C 1; The collector electrode of the 3rd NPN pipe Q3 is received the input stage of the current mirror being comprised of a PMOS pipe M1 and the 2nd PMOS pipe M2; The collector electrode of the 4th PNP pipe Q4 is received the input stage of the current mirror being comprised of the 3rd NMOS pipe M3 and the 4th NMOS pipe M4, and the output stage of two current mirrors is connected, and exports described total harmonic distortion optimization signal (Ctrl).
13. total harmonic distortion optimization devices, is characterized in that comprising:
One subtracter, from a constant signal (A1), deducts rectification and voltage division signal (Vi) afterwards, through a weighter, produces an offset compensation signal (Vi1);
One voltage rises or decline detector, described voltage rising or decline detector are according to rectification and voltage division signal (Vi), judge that described rectification and voltage division signal (Vi) is in enlarging state, still reduce state, when described rectification and voltage division signal (Vi) increases, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal (Ctrl), equals negative offset compensation signal (Vi1); When described rectification and voltage division signal Vi reduces, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal (Ctrl), equals positive offset compensation signal (Vi1);
One adder, adds the above total harmonic distortion (THD) optimization signal (Ctrl), then output from the output signal Sm the inside of multiplier.
14. total harmonic distortion optimization devices, is characterized in that comprising:
One subtracter, from a constant signal (A1), deducts rectification and voltage division signal (Vi) afterwards, through a weighter, produces an offset compensation signal (Vi1);
One voltage rises or decline detector, described voltage rising or decline detector are according to rectification and voltage division signal (Vi), judge that described rectification and voltage division signal (Vi) is in enlarging state, still reduce state, when described rectification and voltage division signal Vi increases, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal (Ctrl), equals negative offset compensation signal (Vi1); When described rectification and voltage division signal (Vi) reduces, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal (Ctrl), equals positive offset compensation signal (Vi1);
A subtracter, deducts total harmonic distortion (THD) from current sampling signal Srs the inside and optimizes signal (Ctrl), then output.
15. as described in claim 13 or 14 total harmonic distortion optimization device, it is characterized in that described voltage rises or the implementation of decline detector is: described rectification and voltage division signal (Vi) is provided for to level shift module, described level shift module produces three level shift signals respectively: the first level shift signal (V0) equals described rectification and voltage division signal (Vi), second electrical level displacement signal (Va) equals described rectification and voltage division signal (Vi) and adds a deviation delta, the 3rd level shift signal (Vb) equals described rectification and voltage division signal (Vi) and deducts a deviation delta, and described second electrical level displacement signal (Va) offers lower down-sampled comparator, described the 3rd level shift signal (Vb) offers up-samples comparator, and the inhibit signal above electric capacity (Vsamp) is simultaneously provided to described up-samples comparator and described lower down-sampled comparator, the described more described second electrical level displacement signal of lower down-sampled comparator (Va) and described inhibit signal (Vsamp), produce decline sampled signal (Vc) and offer rest-set flip-flop and sampling pulse generator, the 3rd level shift signal (Vb) and described inhibit signal (Vsamp) that described up-samples comparator is relatively more described, produce up-samples signal (Vd) and offer described rest-set flip-flop and described sampling pulse generator, described sampling pulse generator control switch, when described switch is closed, sample, described inhibit signal (Vsamp) equals described the first level shift signal (V0), described rectification and voltage division signal (Vi) namely, when described switch disconnects, because electric capacity exists, enter the maintenance stage, described rest-set flip-flop produces judgement signal (Ve).
16. have the control method of the Switching Power Supply of power factor correction, comprise the steps:
Step 1, ac input signal converts direct-flow output signal to;
Step 2, compares described direct-flow output signal and the first reference signal, produces an error amplification signal;
Step 3, multiplies each other described error amplification signal and described ac input signal to produce a product signal;
Step 4, compares described product signal and sampled signal, when described sampled signal is equal to or greater than described product signal, produces a power tube cut-off signals, stops from inductance Absorption Current;
Step 5, compares detection signal and the second reference signal, when described detection signal is equal to or less than described the second reference signal, produces a power tube Continuity signal, starts from described inductance Absorption Current;
When ac input signal increases, reduce the peak current of described inductance, the electric current of compensation AC network to filter capacitor charging; When ac input signal reduces, increase the peak current of described inductance, the electric current of compensation AC network to described filter capacitor electric discharge;
The described Switching Power Supply with power factor correction, is characterized in that: comprise a total harmonic distortion optimization device, described total harmonic distortion optimization device is a kind of in following manner;
(1) described total harmonic distortion optimization device comprises:
One subtracter, from a constant signal (A1), deducts rectification and voltage division signal (Vi) afterwards, through a weighter, produces an offset compensation signal (Vi1);
One voltage rises or decline detector, described voltage rising or decline detector are according to rectification and voltage division signal (Vi), judge that described rectification and voltage division signal (Vi) is in enlarging state, still reduce state: when described rectification and voltage division signal Vi increases, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal (Ctrl), equals negative offset compensation signal (Vi1); When described rectification and voltage division signal (Vi) reduces, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal (Ctrl), equals positive offset compensation signal (Vi1);
One adder, adds the above total harmonic distortion (THD) optimization signal (Ctrl) from the output signal Sm the inside of multiplier, offers the inverting input of electric current induction comparator;
Or (2) described total harmonic distortion optimization device comprises:
One subtracter, from a constant signal (A1), deducts rectification and voltage division signal (Vi) afterwards, through a weighter, produces an offset compensation signal (Vi1);
One voltage rises or decline detector, described voltage rising or decline detector are according to rectification and voltage division signal (Vi), judge that described rectification and voltage division signal (Vi) is in enlarging state, still reduce state, when described rectification and voltage division signal (Vi) increases, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal (Ctrl), equals negative offset compensation signal (Vi1); When described rectification and voltage division signal Vi reduces, described voltage rises or the output total harmonic distortion (THD) of decline detector is optimized signal (Ctrl), equals positive offset compensation signal (Vi1);
A subtracter, deducts total harmonic distortion (THD) from current sampling signal (Srs) the inside and optimizes signal (Ctrl), offers the normal phase input end of electric current induction comparator.
17. methods as claimed in claim 16, is characterized in that:
Described sampled signal represents that current sampling signal is the voltage that the electric current of described power tube produces on sampling resistor;
Described detection signal represents that coupling coil detects the zero current condition of described inductance.
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Families Citing this family (21)
| Publication number | Priority date | Publication date | Assignee | Title |
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| CN113048871B (en) * | 2021-03-11 | 2022-04-05 | 中国人民解放军国防科技大学 | Harmonic component-based nonlinear real-time calibration method for capacitance displacement detection |
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Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US6178101B1 (en) * | 1997-08-15 | 2001-01-23 | Unitron, Inc. | Power supply regulation |
| CN101282079A (en) * | 2007-04-05 | 2008-10-08 | 昂宝电子（上海）有限公司 | System and method for power controller |
| CN101854116A (en) * | 2009-04-02 | 2010-10-06 | 辉芒微电子（深圳）有限公司 | Power factor correcting device and controller and THD (Total Harmonic Distortion) attenuator used therein |
-
2011
- 2011-01-30 CN CN201110033897.4A patent/CN102368661B/en active Active
Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US6178101B1 (en) * | 1997-08-15 | 2001-01-23 | Unitron, Inc. | Power supply regulation |
| CN101282079A (en) * | 2007-04-05 | 2008-10-08 | 昂宝电子（上海）有限公司 | System and method for power controller |
| CN101854116A (en) * | 2009-04-02 | 2010-10-06 | 辉芒微电子（深圳）有限公司 | Power factor correcting device and controller and THD (Total Harmonic Distortion) attenuator used therein |
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