CN101887095B - Method for testing radiated noises of digital gravity metering device - Google Patents
Method for testing radiated noises of digital gravity metering device Download PDFInfo
- Publication number
- CN101887095B CN101887095B CN2010102147835A CN201010214783A CN101887095B CN 101887095 B CN101887095 B CN 101887095B CN 2010102147835 A CN2010102147835 A CN 2010102147835A CN 201010214783 A CN201010214783 A CN 201010214783A CN 101887095 B CN101887095 B CN 101887095B
- Authority
- CN
- China
- Prior art keywords
- noise
- frequency
- common mode
- metering device
- omega
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Fee Related
Links
- 230000005484 gravity Effects 0.000 title claims abstract description 45
- 238000012360 testing method Methods 0.000 title claims abstract description 34
- 238000000034 method Methods 0.000 title claims abstract description 11
- 230000005855 radiation Effects 0.000 claims abstract description 24
- 238000012546 transfer Methods 0.000 claims abstract description 15
- 230000005684 electric field Effects 0.000 claims abstract description 9
- 238000010998 test method Methods 0.000 claims description 10
- 238000003780 insertion Methods 0.000 claims description 9
- 230000037431 insertion Effects 0.000 claims description 9
- 238000005259 measurement Methods 0.000 claims description 9
- 230000000875 corresponding effect Effects 0.000 claims description 8
- 238000000605 extraction Methods 0.000 claims description 8
- 238000004364 calculation method Methods 0.000 claims description 6
- 239000004020 conductor Substances 0.000 claims description 4
- 230000002596 correlated effect Effects 0.000 claims description 4
- 238000000926 separation method Methods 0.000 abstract description 3
- 230000005540 biological transmission Effects 0.000 description 10
- 239000000523 sample Substances 0.000 description 10
- 230000000694 effects Effects 0.000 description 5
- 238000001228 spectrum Methods 0.000 description 4
- 230000005670 electromagnetic radiation Effects 0.000 description 3
- NAWXUBYGYWOOIX-SFHVURJKSA-N (2s)-2-[[4-[2-(2,4-diaminoquinazolin-6-yl)ethyl]benzoyl]amino]-4-methylidenepentanedioic acid Chemical compound C1=CC2=NC(N)=NC(N)=C2C=C1CCC1=CC=C(C(=O)N[C@@H](CC(=C)C(O)=O)C(O)=O)C=C1 NAWXUBYGYWOOIX-SFHVURJKSA-N 0.000 description 2
- 101000831272 Oryza sativa subsp. japonica Cysteine proteinase inhibitor 5 Proteins 0.000 description 2
- 239000011324 bead Substances 0.000 description 2
- 238000004891 communication Methods 0.000 description 2
- 238000013461 design Methods 0.000 description 2
- 238000010586 diagram Methods 0.000 description 2
- 230000009977 dual effect Effects 0.000 description 2
- 238000002474 experimental method Methods 0.000 description 2
- 230000006698 induction Effects 0.000 description 2
- 230000005764 inhibitory process Effects 0.000 description 2
- 239000000203 mixture Substances 0.000 description 2
- 229910000859 α-Fe Inorganic materials 0.000 description 2
- 238000004458 analytical method Methods 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
- 230000001939 inductive effect Effects 0.000 description 1
Images
Landscapes
- Testing Electric Properties And Detecting Electric Faults (AREA)
- Measurement Of Current Or Voltage (AREA)
Abstract
The invention discloses a method for testing radiated noises of a digital gravity metering device, which comprises the following steps of: calculating corresponding transfer impedance according to a high-frequency current clamp structure; putting a measuring loop in the high-frequency current clamp on a power cord of the digital gravity metering device so as to extract a first noise voltage and a second noise voltage in the power cord; performing a vector operation and a vector difference operation on the first noise voltage and the second noise voltage by using a noise separation network so as to obtain a difference mode conducted noise voltage and a common mode conducted noise voltage; performing operation on the difference mode conducted noise voltage, the common mode conducted noise voltage and the transfer impedance of the high-frequency current clamp to obtain a difference mode conducted noise current and a common mode conducted noise current; and acquiring an electric field which emits the radiation noises in a free space according to a common mode noise current formula. In the method, the common mode noise current of a single-chip digital gravity metering device is measured by using the high-frequency current clamp and the noise separation network, and the radiated noises are predicted through the common mode noise current.
Description
Technical field
The present invention relates to a kind of radiation noise test method for digital gravity metering device, belong to electromagnetic compatibility test and power line communication field.
Background technology
Electronic equipment, must be by corresponding standard testing before carrying out marketing, and wherein one is exactly the Radiative EMI standard testing.And based on the radiated noise of single-chip microcomputer digital gravity metering device mainly because its transmission cable radiation causes.And the existing cost that adopts microwave dark room to measure electromagnetic radiation is higher, therefore how for the characteristics of single-chip microcomputer digital gravity metering device, developing a kind of short-cut method of radiation noise test method for digital gravity metering device is the problem that the present invention studies.
Summary of the invention
The object of the invention is to provide a kind of radiation noise test method for digital gravity metering device, the method is first measured the common mode noise current of single-chip microcomputer digital gravity metering device by high-frequency current clamp and noise separating network, then estimates radiated noise by this common mode noise current.
For achieving the above object, the technical solution used in the present invention is: a kind of radiation noise test method for digital gravity metering device comprises the following steps:
Step 1: the performance of test conducted noise separated network common mode insertion loss and differential mode rejection ratio in the radiated noise frequency range meets and measures requirement in the radiated noise frequency range to determine this conducted noise separated network;
Step 2: according to the high-frequency current clamp Structure Calculation, draw corresponding transfer impedance Z (ω), the specific formula for calculation of this transfer impedance Z (ω) is:
In formula, R
2For frequency spectrograph receives impedance, L
2For the high-frequency current clamp coefficient of self-induction, M is the coefficient of mutual inductance between test circuit and high-frequency current clamp, and ω is angular frequency, and j is the imaginary part of symbol;
Step 3: measure ring by one in high-frequency current clamp and be placed on the live wire and ground wire of digital gravity metering device power lead, with the first noise voltage (V of line over the ground of live wire in power lead in the extraction digital gravity metering device
1); Another measurement ring in high-frequency current clamp is placed on the center line and ground wire of digital gravity metering device power lead, with the second noise voltage (V of center line to ground wire in power lead in the extraction digital gravity metering device
2);
Step 4: by described the first noise voltage (V
1), the second noise voltage (V
2) in conjunction with the transfer impedance Z (ω) of described high-frequency current clamp, carry out computing, obtain differential mode noise electric current and common mode noise current;
Concrete formula is as follows:
In formula, R
2For frequency spectrograph receives impedance, L
2For the high-frequency current clamp coefficient of self-induction, M is the coefficient of mutual inductance between test circuit and high-frequency current clamp, and ω is angular frequency (rad/s), and j is imaginary part unit, I
CMFor common mode noise current (A), I
DMFor differential mode noise electric current (A);
Step 5: pass through following formula according to common mode noise current:
, obtain and launch the radiated noise electric field to free space, in formula, Z
0For the free space wave impedance, unit is Ω; L is conductor length, and unit is m; I
CMFor common mode noise current, unit is A; R is measuring distance, and unit is m; β
0Be 2 π/λ, wherein λ is the correlated frequency signal wavelength, and unit is m; E
θFor the radiated noise electric field, unit is dBuV/m; J is the imaginary part sign; θ is for measuring vector angle;
Described high-frequency current clamp is connected to noise separating network, and this noise separating network is connected to described frequency spectrograph.
Related content in technique scheme is explained as follows:
1, in such scheme, described common mode insertion loss and differential mode rejection ratio performance are that the conducted noise separated network is the performance more than 30MHz in frequency of operation.
2, in such scheme, described R
2For receiver internal impedance (Ω), L
2For sense (H) in high-frequency current clamp, M is the volume mutual inductance (H) between circuit and high-frequency current clamp, and ω is angular frequency (rad/s), and j is imaginary part unit.
Because technique scheme is used, the present invention compared with prior art has following advantages:
1, the present invention to be to measure the conducted noise in the single-chip microcomputer digital gravity metering device, and is isolated into common-mode noise and differential mode noise, and adopts corresponding squelch measure to make electric line communication system reach standard-required at conduction portion.
2, the present invention estimates for radiated noise according to common mode noise current, can save great number measurement expense such as utilizing microwave dark room.
3, the present invention adopts separated network to extract common-mode noise, and designs corresponding wave filter and suppress for its common-mode noise, thereby reaches the purpose that suppresses single-chip microcomputer digital gravity metering device radiated noise.Make the inhibition of radiation EMI noise more effective.
4, the present invention uses high-frequency current clamp can measure little electric current to the microampere magnitude.
5, measure traverse line of the present invention between balance to guarantee to optimize the integrality of signal.
The accompanying drawing explanation
The measurement system diagram that Fig. 1 high-frequency current clamp and noise separating network form;
Fig. 2 high-frequency current clamp circuit topological structure figure;
Fig. 3 RF current probe is estimated principle wherein, and I1, I2...In are every segment corresponding current, and E1, E2...En are every section electric field that electric current is corresponding;
Fig. 4, based on single-chip microcomputer digital gravity metering device circuit diagram, amplifies position for causing the radiated noise reason;
Fig. 5 high-frequency current clamp transfer impedance test pattern;
Fig. 6 noise separating network high frequency characteristics figure;
Fig. 7 radiated noise estimation results.
Embodiment
The invention will be further described below in conjunction with drawings and Examples:
Embodiment: a kind of radiation noise test method for digital gravity metering device comprises the following steps:
Step 1: the performance of test conducted noise separated network common mode insertion loss and differential mode rejection ratio in the radiated noise frequency range meets and measures requirement in the radiated noise frequency range to determine this conducted noise separated network;
Step 2: according to the high-frequency current clamp Structure Calculation, draw corresponding transfer impedance Z (ω), the specific formula for calculation of this transfer impedance Z (ω) is:
In formula, R
2For frequency spectrograph receives impedance, L
2For the high-frequency current clamp coefficient of self-induction, M is the coefficient of mutual inductance between test circuit and high-frequency current clamp, and ω is angular frequency, and j is the imaginary part of symbol;
Step 3: measure ring by one in high-frequency current clamp and be placed on the live wire and ground wire of digital gravity metering device power lead, with the first noise voltage (V of line over the ground of live wire in power lead in the extraction digital gravity metering device
1); Another measurement ring in high-frequency current clamp is placed on the center line and ground wire of digital gravity metering device power lead, with the second noise voltage (V of center line to ground wire in power lead in the extraction digital gravity metering device
2);
Step 4: by noise separating network by live wire noise voltage (V
L), center line noise voltage (V
N) carry out vector and phasor difference computing, obtain differential mode conducted noise voltage (V
DM) and common mode conducted noise voltage (V
CM), with differential mode conducted noise in the discrete conductive noise and common mode conducted noise;
Concrete formula is as follows:
In formula, V
1Be the first noise voltage, V
2Be the second noise voltage, V
DMFor differential mode conducted noise voltage, V
CMFor common mode conducted noise voltage.
Step 5: just described the first noise voltage (V
1), the second noise voltage (V
2) in conjunction with the transfer impedance Z (ω) of described high-frequency current clamp, carry out computing, obtain differential mode noise electric current and common mode noise current;
Concrete formula is as follows:
In formula, in formula, R
2For frequency spectrograph receives impedance, L
2For the high-frequency current clamp coefficient of self-induction, M is the coefficient of mutual inductance between test circuit and high-frequency current clamp, and ω is angular frequency (rad/s), and j is imaginary part unit, I
CMFor common mode noise current (A), I
DMFor differential mode noise electric current (A);
Step 6: pass through formula according to following common mode noise current:
, obtain and launch the radiated noise electric field to free space, in formula, Z
0For the free space wave impedance, unit is Ω; L is conductor length, and unit is m; I
CMFor common mode noise current, unit is A; R is measuring distance, and unit is m; β
0Be 2 π/λ, wherein λ is the correlated frequency signal wavelength, and unit is m; E
θFor the radiated noise electric field, unit is dBuV/m; J is the imaginary part sign; θ is for measuring vector angle.
Described high-frequency current clamp is connected to noise separating network, and this noise separating network is connected to described frequency spectrograph.
Described common mode insertion loss and differential mode rejection ratio performance are that the conducted noise separated network is the performance more than 30MHz in frequency of operation.
Described R
2For receiver internal impedance (Ω), L
2For sense (H) in high-frequency current clamp, M is the volume mutual inductance (H) between circuit and high-frequency current clamp, and ω is angular frequency (rad/s), and j is imaginary part unit.
The present embodiment foregoing specific explanations is as follows.
High-frequency current clamp and noise separating network extract for the common mode noise current of single-chip microcomputer gravity metering device, and then by common mode noise current, carry out the new test macro of the radiated noise in anticipator circuit.
Utilize the test macro of noise separating network and high-frequency current clamp composition circuit theory such as Fig. 1 for metering circuit electromagnetic interference noise electric current.Wherein, high-frequency current clamp utilizes the mutual inductance effect that actual electromagnetic interference noise in circuit is sensed in current clamp, and is received by spectrum analyzer.The equivalent model of high-frequency current clamp metering circuit as shown in Figure 2.According to Fig. 2 circuit, transfer impedance Z (ω) defines suc as formula shown in (1):
Wherein, V
2The magnitude of voltage (ω) measured for high-frequency current clamp, I
1(ω) be current value in circuit.Due to the mutual inductance effect of high-frequency current clamp, be not difficult to draw that the electromagnetic interference (EMI) electric current in circuit produces in current probe induction electromotive force is j ω MI
1(ω), because the internal impedance of surveying instrument is 50 Ω, identical with matched impedance again.Current probe measure circuital current in the voltage of gained and circuit relation suc as formula shown in (2):
Wherein, R
2Be 50 Ω loaded impedances, j ω MI
1The magnitude of voltage (ω) obtained by mutual inductance effect induction for voltage probe, L
1Self-induction for current probe.In circuit, because the matched impedance resistance is identical with the surveying instrument internal impedance, so can utilize the magnitude of voltage measured on matched impedance to come electric current in counting circuit suc as formula shown in (3):
V
3(ω)=R
1·I
1(ω)=50·I
1(ω) (3)
Wherein, R
1Be 50 Ω loaded impedances.So (2) formula can be converted to:
Utilize noise separating network, can extract high-frequency current clamp and measure the common mode component in the overall noise electric current.Single-chip microcomputer gravity metering device line noise voltage V
L, V
NBe defined as overall noise, can obtain differential mode noise in circuit and common-mode noise suc as formula shown in (5) (6) by both being carried out to vector and phasor difference:
For the conducted noise electric current, according to the electromagnetic compatibility theory, also it can be divided into to differential mode noise electric current and common mode noise current.The differential mode noise electric current results between live wire and center line, and it defines suc as formula shown in (7):
Common mode noise current is current noise sum on live wire and ground wire and zero line and ground wire, and it defines suc as formula shown in (8):
I
cm=I
L+I
N (8)
According to the common mode current shown in Fig. 1, flow to as can be known, because the impedance of reference ground is less than the inductive impedance of safety line value, so common mode current finally flows to reference ground after by live wire and zero line.Therefore, common mode current is the main cause that causes Radiative EMI.In the design of single-chip microcomputer gravity metering device, due to the existence of circuit intermediate ring road, cause existing in circuit the common mode current of this kind form, thereby cause the increase of its radiated noise.
As can be known by above analysis, the relation of common mode in the voltage measured and circuit (CM)/differential mode (DM) electric current can be meaned by formula (9):
The induced voltage that current probe can be measured by this formula and the common mode noise current in circuit and differential mode noise electric current interrelate, and by noise separating network, can obtain the common mode noise current of single-chip microcomputer gravity metering device, thereby estimate its radiated noise.Its concrete implementation step is as follows:
1, at first, the transfer impedance for current probe in frequency domain is tested, and considers that the equivalent electrical circuit of current probe is comprising self-induction and two aspects of mutual inductance, so can write out current probe partial circuit equation, is not difficult to derive V
2(ω) and V
1Relation (ω) is as shown in (4) formula.
2, for the performance of conducted noise separated network in the radiation frequency range, test, in the radiation frequency range, whether can meet the measurement requirement to determine its performance.
3, set up single-chip microcomputer numeral gravity metering device common mode noise current extraction system, this system is formed (seeing Fig. 1) by high-frequency current clamp, digital gravity metering device, spectrum analyzer and noise separating network.High-frequency current clamp 1 is clipped on live wire and ground wire, with the flow through electromagnetic interference noise electric current I L of live wire and ground wire of measurement; Simultaneously another high-frequency current clamp 2 is clipped on center line and ground wire, with the flow through electromagnetic interference noise electric current I N of center line and ground wire of measurement.By the output terminal access noise separated network of two high-frequency current clamp, in order to the common-mode noise in extraction system.And common-mode noise is converted into to common mode noise current, can estimate according to the common mode noise current of extracting the radiated noise of this system.The electromagnetic radiation of single-chip microcomputer digital gravity metering device is mainly derived from the common mode radiation on circuit, and common mode radiation derives from high frequency common mode current, common mode current is launched radiation field along transmission line to free space, and the field intensity computing formula is suc as formula shown in (10):
Wherein: Zo is free space wave impedance (Ω), and l is conductor length (m), I
CMFor common mode noise current (A), r is measuring distance (m), and β o=2 π/λ, λ are correlated frequency signal wavelength (m).
Along with the increase of frequency, the physical length of wire will be comparable with the physical dimension of wavelength, along the uniformity no longer of the distribution of current on wire.Wire evenly can be divided into to N segment for this reason, adopt the radio frequency high-frequency current clamp in the centre position of every segment, to measure its electric current (seeing Fig. 3) separately, establish and be respectively I1, I2...In, can adopt formula (10) to calculate for each section lead.
Adopt formula (10) to calculate the radiation field of each segment.Due to open testing field (OATS), normally measure the standard place of electromagnetic radiation, so need, consider the ground return effect, total equivalent radiated power field is calculated and is converted into suc as formula shown in (11).
Wherein, | EC| is radiated electric field, and 1 is every segment antenna eliminator length, and f means test frequency, and r means open testing field standard testing distance, and H means the test antenna height, and F is for calculating the modifying factor under the test environment of open testing field.
4, because the digital gravity metering device transmission cable is longer, therefore can utilize the test macro that high-frequency current clamp and noise separating network form to extract for the common mode noise current of zones of different on transmission cable, with the optimum position of determining that braking measure loads.
5, adopt ferrite bead to suppress for the radiated noise in single-chip microcomputer numeral gravity metering device, by relatively loading before and after ferrite bead on cable the attenuation degree of radiated noise to check the effect of method in literary composition.
The method of testing that the present invention adopts, can estimate for the radiation EMI noise on all kinds of single-chip microcomputer numeral gravity metering device transmission cables.Thereby adopt high-frequency current clamp and noise separating network to extract for the radiation EMI noise and estimate for common mode noise current on cable, the method is simple to operate and test is accurate.By this method of testing, can test the radiation EMI noise of single-chip microcomputer numeral gravity metering device transmission line, further for suppressing this radiation EMI noise, provide theoretical foundation.
As shown in Figure 4, it is due to due in circuit, the 12MHz clock circuit is coupled in transmission line that its radiated noise produces reason to its circuit.Set up test macro as shown in Figure 1, this test macro is comprised of high-frequency current clamp, noise separating network, spectrum analyzer and digital gravity metering device etc.
Concrete method of testing:
In time domain, its experiment connects as shown in Figure 5, this experiment utilizes signal generator in required measurement frequency range, to export the sinusoidal signal of different frequency in a port of dual trace oscilloscope, simultaneously high-frequency current clamp is carried on transmission line, the value measured is input to the another one port of dual trace oscilloscope, according to 3 formulas, can obtain on different frequency point the transfer impedance of this current probe.
The noise separating network adopted is measured in the performance of radiation frequency range, can be applied in the middle of estimating of radiated noise to determine this noise separating network.The good and bad leading indicator of judgement common-mode noise separated network performance be its common mode insertion loss (CMIL) and its definition of differential mode rejection ratio (DMRR) suc as formula shown in (12):
Wherein, V
CMFor common mode input, V
OCFor common mode output; V
DMFor difference-mode input, V
ODFor differential mode output.In the common mode separated network, the ideal value of common mode insertion loss should be 0, to guarantee that the loss of its common mode noise signal is less in the common-mode noise transmission; In like manner as can be known, its differential mode rejection ratio should be large as far as possible, to guarantee its differential mode noise, can not be coupled in the transmission of common mode noise signal, so the ideal value of its differential mode rejection ratio should be-∞.By test, can obtain its common mode insertion loss and differential mode rejection ratio test result as shown in Figure 6.This result shows that this separated network can apply to estimating of radiation EMI frequency range.
At the test noise separated network on the basis of radiation frequency range performance, can the connecting circuit system.By the digital gravity metering device energising, and high-frequency current clamp 1 is clipped on live wire and ground wire; Another high-frequency current clamp is clipped on center line and ground wire, to measure live wire noise and the center line noise V on cable
L, V
NIts frequency that exceeds standard is 36MHz (as shown in Figure 7).The output port of high-frequency current clamp is linked in noise separating network, by the noise inputs spectrum analyzer after separating to analyze the common mode noise current of single-chip microcomputer gravity metering device.
High-frequency current clamp is placed in to different places on the digital gravity metering device cable, to determine the position of radiation maximum on cable.In this case, be divided into nearly power end, mid point and nearly equipment end three places are detected, and its testing result is as shown in table 1:
Table 1 digital gravity metering device Conducted EMI noise separation result
Filter location | Nearly power end | Mid point | Nearly equipment end |
The radiated noise amplitude | 42dBuV | 42.9dBuV | 48dBuV |
Shown in table, its inhibition site should be at nearly equipment end place.
Above-described embodiment only is explanation technical conceive of the present invention and characteristics, and its purpose is to allow the person skilled in the art can understand content of the present invention and implement according to this, can not limit the scope of the invention with this.All equivalences that Spirit Essence is done according to the present invention change or modify, within all should being encompassed in protection scope of the present invention.
Claims (3)
1. radiation noise test method for digital gravity metering device is characterized in that: comprise the following steps:
Step 1: the performance of test conducted noise separated network common mode insertion loss and differential mode rejection ratio in the radiated noise frequency range meets and measures requirement in the radiated noise frequency range to determine this conducted noise separated network;
Step 2: according to the high-frequency current clamp Structure Calculation, draw corresponding transfer impedance Z (ω), the specific formula for calculation of this transfer impedance Z (ω) is:
In formula, R
2For frequency spectrograph receives impedance, L
2For the high-frequency current clamp coefficient of self-induction, M is the coefficient of mutual inductance between test circuit and high-frequency current clamp, and ω is angular frequency, and j is the imaginary part of symbol;
Step 3: measure ring by one in high-frequency current clamp and be placed on the live wire and ground wire of digital gravity metering device power lead, with the first noise voltage (V of line over the ground of live wire in power lead in the extraction digital gravity metering device
1); Another measurement ring in high-frequency current clamp is placed on the center line and ground wire of digital gravity metering device power lead, with the second noise voltage (V of center line to ground wire in power lead in the extraction digital gravity metering device
2);
Step 4: by described the first noise voltage (V
1), the second noise voltage (V
2) in conjunction with the transfer impedance Z (ω) of described high-frequency current clamp, carry out computing, obtain differential mode noise electric current and common mode noise current;
Concrete formula is as follows:
In formula, R
2For frequency spectrograph receives impedance, L
2For the high-frequency current clamp coefficient of self-induction, M is the coefficient of mutual inductance between test circuit and high-frequency current clamp, and ω is angular frequency (rad/s), and j is imaginary part unit, I
CMFor common mode noise current (A), I
DMFor differential mode noise electric current (A);
Step 5: pass through following formula according to common mode noise current:
, obtain and launch the radiated noise electric field to free space, in formula, Z
0For the free space wave impedance, unit is Ω; L is conductor length, and unit is m; I
CMFor common mode noise current, unit is A; R is measuring distance, and unit is m; β
0Be 2 π/λ, wherein λ is the correlated frequency signal wavelength, and unit is m; E
θFor the radiated noise electric field, unit is dBuV/m; J is the imaginary part sign; θ is for measuring vector angle;
Described high-frequency current clamp is connected to noise separating network, and this noise separating network is connected to described frequency spectrograph.
2. method according to claim 1 is characterized in that: also comprise: by noise separating network by the first noise voltage (V
1), the second noise voltage (V
2) carry out vector and phasor difference computing, obtain differential mode conducted noise voltage (V
DM) and common mode conducted noise voltage (V
CM), with differential mode conducted noise in the discrete conductive noise and common mode conducted noise;
Concrete formula is as follows:
In formula, V
1Be the first noise voltage, V
2Be the second noise voltage, V
DMFor differential mode conducted noise voltage, V
CMFor common mode conducted noise voltage.
3. method according to claim 1, it is characterized in that: described common mode insertion loss and differential mode rejection ratio performance are that the conducted noise separated network is the performance more than 30MHz in frequency of operation.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
CN2010102147835A CN101887095B (en) | 2010-07-01 | 2010-07-01 | Method for testing radiated noises of digital gravity metering device |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
CN2010102147835A CN101887095B (en) | 2010-07-01 | 2010-07-01 | Method for testing radiated noises of digital gravity metering device |
Publications (2)
Publication Number | Publication Date |
---|---|
CN101887095A CN101887095A (en) | 2010-11-17 |
CN101887095B true CN101887095B (en) | 2013-11-27 |
Family
ID=43073091
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
CN2010102147835A Expired - Fee Related CN101887095B (en) | 2010-07-01 | 2010-07-01 | Method for testing radiated noises of digital gravity metering device |
Country Status (1)
Country | Link |
---|---|
CN (1) | CN101887095B (en) |
Families Citing this family (11)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
EP2525503B1 (en) * | 2011-05-16 | 2018-03-07 | Sony Corporation | Power line communication modem, power line communication system, power line communication method |
CN102928691A (en) * | 2012-10-10 | 2013-02-13 | 中联重科股份有限公司 | System, method and device for detecting electromagnetic transient disturbance signal of electrical equipment |
CN102944701A (en) * | 2012-11-06 | 2013-02-27 | 西安开容电子技术有限责任公司 | Wide-frequency-band current testing calipers |
CN102944781A (en) * | 2012-11-06 | 2013-02-27 | 西安开容电子技术有限责任公司 | Miniaturized current test caliper |
CN102981086B (en) * | 2012-12-10 | 2015-05-20 | 江苏省产品质量监督检验研究院 | Analysis and measurement method for electromagnetic radiation of voltage driven radiation source |
CN103278713A (en) * | 2013-04-28 | 2013-09-04 | 江苏省产品质量监督检验研究院 | Radiation-source pre-estimation and calibration method of current-driven model |
CN104049162B (en) * | 2014-06-12 | 2017-02-01 | 吉林大学 | Device and method for testing noise tolerance characteristic of driving voltage of waveguide optical switch |
CN104502755B (en) * | 2014-12-15 | 2017-04-19 | 北京航空航天大学 | Gaussian even pulse high-current high-power broadband power line injection coupling network and construction method thereof |
CN108667506B (en) * | 2018-04-26 | 2020-11-20 | 北京空间飞行器总体设计部 | System and method for testing influence of satellite electric propulsion system on communication signal modulation |
JP6970140B2 (en) * | 2019-05-23 | 2021-11-24 | 株式会社ソニー・インタラクティブエンタテインメント | Power supply unit inspection device |
CN112881845B (en) * | 2021-01-26 | 2022-11-04 | 浙江亚太机电股份有限公司 | Device and method for measuring conduction emission current of ECU signal wire |
Citations (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2004317322A (en) * | 2003-04-17 | 2004-11-11 | Hitachi Ltd | Near noise measuring device for radio communication device |
CN201397367Y (en) * | 2009-03-19 | 2010-02-03 | 苏州泰思特电子科技有限公司 | Conducted electromagnetic interference noise analyzer of electronic device |
-
2010
- 2010-07-01 CN CN2010102147835A patent/CN101887095B/en not_active Expired - Fee Related
Patent Citations (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2004317322A (en) * | 2003-04-17 | 2004-11-11 | Hitachi Ltd | Near noise measuring device for radio communication device |
CN201397367Y (en) * | 2009-03-19 | 2010-02-03 | 苏州泰思特电子科技有限公司 | Conducted electromagnetic interference noise analyzer of electronic device |
Non-Patent Citations (1)
Title |
---|
董颖华等.电力线通讯辐射噪声的预估与抑制.《东南大学学报(自然科学版)》.2009,第39卷 * |
Also Published As
Publication number | Publication date |
---|---|
CN101887095A (en) | 2010-11-17 |
Similar Documents
Publication | Publication Date | Title |
---|---|---|
CN101887095B (en) | Method for testing radiated noises of digital gravity metering device | |
Hashmi et al. | Calibration of on-line partial discharge measuring system using Rogowski coil in covered-conductor overhead distribution networks | |
CN109031021B (en) | High-voltage single-core cable short-circuit fault positioning method, device and system | |
Papadopoulos et al. | Narrowband power line communication: Medium voltage cable modeling and laboratory experimental results | |
CN101458282B (en) | High-frequency circuit spacing electromagnetic radiation characteristic analyzing and predicting method | |
CN103969559A (en) | Method and system for positioning local discharge space of power equipment of transformer substation | |
CN203838296U (en) | Multi-path signal peak collection device based on partial-discharge spatial orientation system | |
CN103235168B (en) | Measuring system for shunt vectors of metal frames of large ground grids on basis of wireless transmission | |
CN108896872A (en) | Handheld cable fault detection system and method based on SSTDR | |
CN108646144A (en) | A kind of offline distance measuring method of high voltage single-core cable short trouble, apparatus and system | |
CN101820303A (en) | Radiation noise test method applied to power line communication network | |
CN103913661B (en) | Method for estimating influences on telecommunication cable E1 wire by electromagnetic disturbance | |
Li et al. | Measurements of medium-frequency propagation characteristics of a transmission line in an underground coal mine | |
CN207301251U (en) | Transformer insulated property detection device | |
CN101738557A (en) | Method for diagnosing radiation noise type by using GTEM chamber | |
CN105116306A (en) | Acquisition method and device of substation partial discharge live detection electromagnetic interference | |
CN105388368B (en) | A kind of impedance load(ing) point choosing method of high pressure overhead power line electromagnetic scattering | |
CN201724993U (en) | Radiation noise testing system for digital gravity metering device | |
CN105653848A (en) | Method for measuring coupling coil parameters by single-port impendence and sensitivity | |
Zhao et al. | Induction coupling between jointless track circuits and track-circuit-reader antenna | |
CN206038784U (en) | Live line measurement zinc oxide arrester's wireless tester | |
Tani et al. | Characterization of AC/coaxial adapter for LISN calibration above 30 MHz using improved equivalent circuit model | |
RU2012107837A (en) | METHOD FOR EVALUATING ELECTROMAGNETIC COMPATIBILITY OF ON-BOARD EQUIPMENT IN THE COMPOSITION OF THE AIRCRAFT IN THE RANGE OF FREQUENCIES FROM 10 kHz TO 400 MHz | |
Mohos et al. | A correction method for the phase angle error of surface impedance measurements in the 2 kHz–150 kHz frequency range | |
Rhee et al. | Noise source impedance extraction method of switched-mode power supply (SMPS) in PC according to the frequency range |
Legal Events
Date | Code | Title | Description |
---|---|---|---|
C06 | Publication | ||
PB01 | Publication | ||
C10 | Entry into substantive examination | ||
SE01 | Entry into force of request for substantive examination | ||
C14 | Grant of patent or utility model | ||
GR01 | Patent grant | ||
CF01 | Termination of patent right due to non-payment of annual fee | ||
CF01 | Termination of patent right due to non-payment of annual fee |
Granted publication date: 20131127 |