CN101366254B - Dual carrier modulator for a multiband OFDM transceiver - Google Patents

Abstract

Dual Carrier Modulator (DCM) for a Multiband OFDM (Orthogonal Frequency Division Multiplexing) Transceiver of a Ultra Wide Band (UWB) wireless personal access network transmitting OFDM modulated symbols, wherein each OFDM symbol is modulated by a predetermined number (N CBPS) of encoded bits, the Dual Carrier Modulator (1) comprising: (g) a grouping unit (1-1) for grouping NCBPS encoded bits of a serial bit stream into bit groups each having a predetermined number (m) of bits; (h) a mapping unit (1-2) for mapping each bit group received from the grouping unit to complex symbols (y) using an orthogonal transform; and (i) a reordering unit (1-3) for reordering the complex symbols (y) mapped by the mapping unit, wherein each complex symbol (y) is provided to modulate a corresponding data tone of an OFDM symbol.

Description

The dual carrier modulator that is used for multiband OFDM transceiver

Technical field

The present invention relates to a kind of dual carrier modulator that is used for the multiband OFDM transceiver of ultrabroad band (UWB) radio individual access network.

Background technology

Fig. 1 shows the transfer of data in the wireless system of prior art.Several transceivers that belong to same wireless lan (wlan) utilize same data transmission channel by means of timesharing.In any specific moment, only a transceiver transmits.Therefore, all be burst (burst) formula from the transmission of every transceiver.In order to help the pulse of receiver recognition data transmitting burst, and in order to extract the information data that has transmitted, transmitter sent predefined preamble signal earlier before the data division that sends the transfer of data burst.The transceiver that receives this transfer of data burst comprises the preamble detecting unit, this detecting unit identification preamble, thereby the pulse of recognition data transmitting burst.Transceiver further is used for needed transfer of data of data estimator information extraction and channel parameter with this preamble, such as channel response and carrier wave and timing slip.

Usually, several kinds of shared same data transfer medium of communication network.Particularly the wireless network of coexistence utilizes same frequency spectrum.

Fig. 2 illustrates the wireless network according to two coexistences of prior art.

A kind of new communication form of wireless lan (wlan) representative between other equipment of perhaps hoping the transmission numerical data between the personal computer.Wireless network does not rely on cable as communication medium.No matter be that twisted-pair feeder, coaxial cable or the optical fiber, the hardwired that are used for the data communication system of building environment all is expensive and installs, safeguard and change and all be out of order easily.For fear of these shortcomings, the signal that the wireless network utilization covers the wide frequency ranges from several megahertzes to several terahertzs transmits data aloft.According to the frequency that is comprised, wireless network comprises radio net, microwave wireless network and infrared radio network.

Wireless network is mainly used in the equipment in the building is linked to each other with network, perhaps portable or mobile device is linked to each other with network.Application in addition is to keep mobile device and database and the for example AD-HOC network in the committee or business meetings to interrelate.

Wireless lan (wlan) and wireless personal-area network (WPAN) are used for transmission information in short relatively scope.In IEEE 802.15.3 standard, defined wireless personal-area network (WPAN).

In many situation and scheme, several wireless lan (wlan)s are worked in same regional area each other simultaneously.Typical situation is big office, and wherein many offices cubicle belongs to the different departments of same company, for example research department, Accounting Department, sales department.In this case, the computer of each department all connects through wireless lan (wlan) independently.The wireless lan (wlan) that comprises several transceivers is called piconet (Piconet).

Fig. 2 illustrates typical protocols, and wherein two wireless lan (wlan)s are worked in same regional area.

In an example shown, first transmitter A2 receiver A4 to the first WLAN WLAN on the data transmission channel of WLAN WLANA sends data.In addition, the transmitter B3 of second WLAN WLANB receiver B1 to same WLAN WLANB on the data transmission channel of this WLAN sends data.Exchanges data between the transceiver is carried out with half-duplex mode, promptly can data be sent to another transceiver of same WLAN or receive data from this transceiver via data link.Come swap data via packet.

Each piconet WLANi has its data transmission channel separately, and all transceivers of promptly corresponding piconet WLANi use the data transmission channel of piconet WLANi oneself.

In most of the cases, WLAN WLAN available frequency resources receives the restriction of rule.Be generally WLAN and distribute special frequency band.In this frequency band, need the radiation of each transceiver to be no more than the average power spectrum density (PSD) of appointment.

Proposed in order to operate several kinds of motions of several WLANs simultaneously.

In frequency division multiplex (FDM) system, the frequency band that distributes is divided into several sub-frequency bands according to prior art.In the FDM system, each data transmission channel and therefore each piconet all utilize different sub-bands.Like this, can carry out the transfer of data in the different piconets (WLAN) and not disturbing simultaneously.

The shortcoming of FDM system is, uses the situation of the frequency band of whole distribution to compare with allowing any piconet, and the available capacity of each piconet reduces.

Following formula has provided channel capacity:

$\mathrm{cap}=\∫\log (1+\frac{\mathrm{PSD}\left(f\right)}{N\left(f\right)})\mathrm{df}$

If allow each piconet to use whole frequency bands rather than only use the sub-band distributed, the capacity of each piconet is bigger so.The capacity of FDM system reduces and directly changes total throughout (throughput) reduction into.Therefore, reduced the data bit-rate that is reached of any particular transmitter-receiver distance in the FDM system.

In CDMA-DSSS (CDMA(Code Division Multiple Access)-Direct swquence spread spectrum) system, Direct swquence spread spectrum is used as modulation scheme according to prior art.In DSSS, send a sequence of many short data symbols for each information symbol.In order to support several data transmission channels or piconet, the different pieces of information sequence that will between different pieces of information transmission channel or piconet, have low cross correlation is used for different data transmission channels.

In the CDMA-DSSS system, each channel whole frequency band capable of using is up to the total throughout that can realize maximum possible.If some piconets are in same regional work, the transmission of a piconet is regarded as additional noise by other piconets so.

The shortcoming of CDMA-DSSS system is to exist so-called nearly problem far away.When the transceiver in the piconet is transmitting, this transmission will be regarded as additional noise by other piconets.Cross-correlation between the power level of additional noise level and sequence spreading and the interference signal that receives is proportional.For example; If the interference transceiver of piconet A is near the reception transceiver of piconet B; Promptly than the transmitter of piconet B more near the receiver of piconet B; The additional noise level seen of the receiver of the piconet B bit rate that causes this receptions function to realize obviously reduces so, so even the total blockage of data transmission channel can occur.

Another motion that is used for operating several wireless lan (wlan)s simultaneously according to prior art is to utilize CDMA-FH (CDMA visit-frequency hopping) system.In this CDMA-FH system, original frequency band is divided into several sub-frequency bands.Any transmitter moves to next frequency band then utilizing a certain sub-band at interval sometime.The order of predefined frequency hop sequences control sub-band, thus make transmission and receiver have the information that when is transformed into next frequency and when is transformed into what sub-band.

In the CDMA-FH of routine system, for different data transmission channels distributes different frequency hop sequences.

Fig. 3 A illustrates the CDMA-FH system with a plurality of data transmission channels according to prior art.4 piconets or wireless lan (wlan) can be operated simultaneously at same regional area by CDMA-FH system with 4 data transmission channels.In an example shown, any transceiver all uses special frequency band in the transmission intercal of 242ns, keeps the free time of the predetermined guard time of 70ns, and in next transmission intercal, uses next frequency band etc.

For any data transmission channel A, B, C, D confirm frequency hop sequences.In the instance that provides, data transmission channel A has frequency hop sequences abc, and channel B has frequency hop sequences acb, and channel C has frequency hop sequences aabbcc, and channel D has frequency hop sequences aaccbb.

, two transceivers can clash when utilizing identical frequency band simultaneously.For example, all utilize in the process of first transmission intercal of frequency f a and all utilize once more in the process of the 4th transmission intercal of frequency f a, between data transmission channel A and data transmission channel B, clash at channel A, B at channel A, B.Conflict in addition for example all utilizes in the process of first transmission intercal of frequency a and in channel B, D utilize the process of the 6th transmission intercal of frequency f b, between channel B and channel D, takes place at channel B, D.

When the frequency hop sequence of two wireless networks not simultaneously, two transceivers that belong to different wireless local area network can be launched simultaneously.Contingent is that two transceivers utilize identical carrier frequency simultaneously.

A kind of possible CDMA-FH solution is based on OFDM, and is referred to as multi-band OFDM.In this case, transceiver sends single OFDM in a frequency band, jump to next frequency band in order to send next OFDM symbol then.Fig. 3 A draws 6 OFDM of each channel.

Shown in Fig. 3 A, multiband OFDM transceiver interweaves in temporal frequency and carries out frequency band in (TFI) pattern and jump, wherein, and transmission OFDM symbol in each frequency band.The frequency band jump sequence is defined by the TFC sign indicating number of storing in the internal memory (temporal frequency sign indicating number).Different co-existin networks utilizes different TFC sign indicating numbers.This can make various network transmit simultaneously.OFDM symbol from a plurality of co-existin networks clashes.Under common situation, conflict level (level) can be communicated by letter effectively.Yet in some cases, conflict situations is very serious, and communication is not effective.In order to overcome the serious conflict between the transmission of heterogeneous networks, can implement the frequency domain separation (being called FDM) between the wireless network.This accomplishes through the TFC sign indicating number that increase has the constant frequency band of use (fixed frequency band).Therefore, can between temporal frequency interlace mode (TFI pattern) and fixed frequency interlace mode (FFI pattern), change according to the multiband OFDM transceiver of prior art.Fig. 3 B shows 7 channels (7 TFC), and wherein 4 channels are TFI types, and 3 channels are FFI types.

As seeing among Fig. 3 B, transceiver occupies 3 frequency bands in the TFI pattern, and wherein each frequency band has predetermined frequency bandwidth.

Multi-band OFDM standard according to development; The cycle of an OFDM symbol was 312.5 nanoseconds, i.e. the data length of 242.5 nanoseconds (with 128 samplings of 528Msps speed sampling) and the dead time of 70 nanoseconds (with 37 samplings of 528Msps speed sampling) between twice transmission.Therefore, OFDM symbol rate RS=3.2MHz=1/312.5 nanosecond.When using three frequency bands, 7 possible temporal frequency sign indicating numbers (TFC) are arranged.Preceding 4 TFC sign indicating numbers have defined when transceiver and have been in the frequency band jump sequence in the TFI pattern.When transceiver was transformed into the FFI pattern, this transceiver was transmitted in the signal in the fixed frequency band.Shown in following table and Fig. 3 B, the 5th TFC sign indicating number shows that transceiver is transmitted in the signal in first frequency band, and the 6th TFC sign indicating number shows that transceiver is transmitted in the signal in second frequency band, and the 7th TFC sign indicating number shows that transceiver is transmitted in the signal in the 3rd frequency band.

Following TFC sign indicating number has three frequency bands as summarizing in the following table:

Table 1:

The TFC index	Sign indicating number	Type
			1	[1，2，3]	TFI
2	[1，3，2]	TFI
			3	[1，1，2，2，3，3]	TFI
4	[1，1，3，3，2，2]	TFI
			5	[1]	FFI
6	[2]	FFI
			7	[3]	FFI

TFC index 1-7 in this table is corresponding to the channel A-G among Fig. 3 B.

The single burst of transmission is called the PLCP frame.Fig. 4 illustrates the data format of the used PLPC frame of multiband OFDM transceiver.Each frame all is made up of preamble, header and payload data section.The PLPC header transmits with the constant data rate of per second 39.4Mbit, and payload data is transmitted with the different data rate that between per second 53.3Mbit and per second 480Mbit, changes according to the selected mode of operation of OFDM transceiver.PLCP frame as shown in Figure 4 is made up of many OFDM symbols, and wherein each OFDM symbol is by predetermined quantity (N _CBPS) encoded data bits form.According to selected data transfer rate, each OFDM symbol comprises for example 100 or 200 encoded data bits.Like what from Fig. 3 B, seen, the frequency hopping pattern that each OFDM symbol basis is scheduled to is at different frequency band f _a, f _b, f _cMiddle transmission.For example, the OFDM transceiver adopts for example three frequency band f _a, f _b, f _c, therefore via corresponding quantity data transmission channel A, B, C, D, E, F, G, 7 different frequency hopping patterns shown in Fig. 3 B also are possible.Each frequency band f that the OFDM transceiver adopts _a, f _b, f _cAll comprise centre frequency, the subcarrier or the tone (tone) of predetermined quantity is provided around this centre frequency.Frequency comprises 122 subcarriers for example being made up of pilot subcarrier, protection information sub carrier wave and data subcarriers.Each subcarrier subcarrier all adjacent thereto is an equidistance, and can modulate it respectively.

Fig. 5 illustrates the OFDM transceiver according to prior art.This transceiver comprises transmitter and receiver, and this transmitter and receiver all links to each other with higher communication layers piece.OFDM transceiver according to as shown in Figure 5 prior art is a multiband OFDM transceiver, and wherein transmitter sends the OFDM symbol via data transmission channel, and receiver receives the OFDM symbol from said data transmission channel.Illustrate in greater detail the transmitter of routine as shown in Figure 5 among Fig. 6.Higher communication layers circuit is supplied with the header generator with bit stream, and this header generator increases header to the payload that receives from higher communication layers.The header generator links to each other with the error correction encoder, and this error correction encoder is encoded the data flow that receives.The error correction encoder is connected to interleave circuit at its output.This interleave circuit interweaves the bit stream that receives to improve the performance of transfer of data.The bit stream that interweaves acts on the frequency expansion unit in the transmitter.Frequency expansion unit by using frequency expansion factor FSF expands the bit that receives in frequency domain, according to the data transfer rate that higher communication layers acted on FSF is provided with.

The frequency expansion unit links to each other with the OFDM Symbol modulator, and this OFDM Symbol modulator is modulated each subcarrier or data tones in this frequency band according to data transfer rate or transmission mode.The OFDM Symbol modulator according to prior art as shown in Figure 6 comprises qpsk modulator, is used to carry out the IFFT unit and the parallel-to-serial converter of invert fast fourier transformation.The output of OFDM Symbol modulator is connected to the temporal extension unit of transmitter, and this temporal extension unit utilizes the temporal extension factor (TSF) in time domain, to expand the OFDM symbol according to the data transfer rate of being set by higher communication layers.

At last, data flow is transferred to the frequency hopping transmitter, this transmitter is sent in similar and different frequency band F according to predetermined frequency hopping pattern _a, F _b, F _cIn the OFDM symbol that interweaves and expand.Frequency hopping pattern is decided by the selected data transmission channel of OFDM transceiver.

Fig. 7 illustrates the conventional receiver in the OFDM transceiver as shown in Figure 5.Receiver shown in Fig. 7 comprises frequency-hopping receiver, and the OFDM symbol demodulator links to each other with this frequency-hopping receiver.Frequency goes expansion (de-spreading) unit and time to go expanding element that demodulated OFDM symbol is gone expansion in frequency domain and time domain.Deinterleave circuit deinterleaves the bit stream that receives, and for example Viterbi (Viterbi) decoder of error correcting/decoding device is provided for error correction.At last, the header extraction unit extracts the header of the packet that receives, thereby data transfer rate adjustment deinterleave circuit, time and the frequency of the data flow that this header extraction unit identification receives are gone expanding element and error correction unit.The OFDM Symbol modulator that in conventional transmitter, provides as shown in Figure 6 has some serious defectives.The OFDM Symbol modulator comprises qpsk modulator.The binary data of having encoded and having interweaved is divided into many group bits and is converted into the plural number of representing the QPSK constellation point.The QPSK modulation is used for a plurality of groups of being made up of 2 coded-bits are mapped as complex symbol.With the OFDM symbol packets, increase the set of pilot tone, and no data tones is made as zero.In order to make this signal transition is that time domain provides IFFT the unit.With the output serialization of IFFT unit, and send it in the air by the frequency hopping transmitter.

Because the multipath in the wireless medium, the common response of data transmission channel has frequency selectivity.In the transmitter according to prior art as shown in Figure 7, each coded-bit is loaded on the data tone in the single OFDM symbol.If data tones is destroyed, can change the information that this coded-bit comprises so.When thereby data transmission channel makes the data tones complete attenuation cause frequency spectrum is zero or during serious tone signal to noise ratio, the entrained information of coded-bit can be lost fully.Particularly for High Data Rate, it does not have application extension and encoding rate quite high, and frequency spectrum is that the zero performance that causes reduces like this.Under the condition of selective channel, the error correcting/decoding device does not prevent the bit loss of the data tones of serious decay effectively.For given noise level N, the frequency-selective channels state has reduced signal to noise ratio (snr).Low signal-to-noise ratio (SNR) according to the conventional transmitter of prior art causes that the error rate (BER) increases as shown in Figure 6.For given data transfer rate, the OFDM Symbol modulator that provides in conventional transmitter according to prior art as shown in Figure 6 can not realize reliable communication,, can not be implemented in the signal to noise ratio (snr) of the data transmission channel low error rate (BER) when very low that is.

Therefore, the purpose of this invention is to provide a kind of modulator that is used for multiband OFDM transceiver, itself in addition when the signal to noise ratio (snr) of data transmission channel is very low, allow the transfer of data on the data transmission channel to have lowest bit error rate (BER).

The dual carrier modulator (DCM) of the characteristic through having claim 1 is realized this purpose.

The present invention provides a kind of dual carrier modulator (DCM) of multi-band OFDM (Orthodoxy Frequency Division Multiplex) transceiver of ultrabroad band (UWB) the radio individual access network that is used for the transmission OFDM modulation symbol, wherein by predetermined quantity (N _CBPS) coded-bit each OFDM symbol is modulated, said dual carrier modulator comprises:

(a) grouped element is used for the N with serial bit stream _CBPSIndividual coded-bit is divided into a plurality of bit groups, and each bit group all has the bit of predetermined quantity (m);

(b) map unit is used for each the bit group that receives from said grouped element is mapped as complex symbol (y); And

(c) unit that reorders is used for complex symbol (y) rearrangement with said map unit mapping,

Each complex symbol (y) wherein is provided, so that the corresponding data tones of Modulation OFDM symbol.

Realized low error rate (BER) according to dual carrier modulator of the present invention (DCM) for the given signal to noise ratio (snr) of the transfer of data of given data transfer rate.Therefore, comprise according to the transceiver of dual carrier modulator of the present invention (DCM) and can under difficult data transmission conditions, work, and can allow more noise and even a data transmission channel that has more the frequency options.Compare with the MB-OFDM transceiver of routine and to have improved performance.

In the preferred embodiment according to dual carrier modulator of the present invention, grouped element is divided into a plurality of bit groups with 200 coded-bits, and each bit group has 4 bits.

In preferred embodiment according to dual carrier modulator of the present invention; Map unit is mapped as 2 complex symbols respectively with a plurality of bit groups so that for 100 data tones modulating an OFDM symbol produce 100 complex symbols, each said bit group all comprises 4 bits.

In preferred embodiment according to dual carrier modulator of the present invention; Map unit comprises first map level and second map level; First map level is used for the one pole bit value of the coded-bit of each bit group is mapped as bipolar bit value; Second map level is mapped as 2 complex symbols with 4 bipolar bits in each bit group, is described below:

$\left(\begin{array}{c}{y}_n\\ y_{n+50}\end{array}\right)=\frac{1}{\sqrt{b^2+1}}\left(\begin{array}{cc}1& b\\ b& -1\end{array}\right)\left(\begin{array}{cc}{x}_{a\left(n\right)}& {\mathrm{jx}}_{a\left(n\right)+50}\\ x_{a\left(n\right)+1}& {\mathrm{jx}}_{a\left(n\right)+51}\end{array}\right)$

n＝0，1...49

$a\left(n\right)=\left\{\begin{array}{cc}2n& n=\mathrm{0,1,2},...24\\ 2n+50& n=\mathrm{25,26},...49\end{array}\right.$

Wherein b is a constant.

In the preferred embodiment according to dual carrier modulator of the present invention, map unit is formed by the look-up table of storing in the internal memory.

In preferred embodiment according to dual carrier modulator of the present invention, the look-up table of storing in the internal memory that is given in as described below:

In the preferred embodiment according to dual carrier modulator of the present invention, constant b is 2.

In the preferred embodiment according to dual carrier modulator of the present invention, scale factor K is chosen as

K wherein ₀It is the corresponding scale factor of QPSK modulation.

The present invention further provides a kind of metric calculation unit that is used for the multiband OFDM transceiver of ultrabroad band (UWB) radio individual access network, and said transceiver receives via the OFDM symbol that data transmission channel transmitted, wherein predetermined quantity (N _CBPS) coded-bit each OFDM symbol is carried out two carrier modulation (DCM), each coded-bit is 2 data tones of Modulation OFDM symbol all, said metric calculation unit comprises:

(a) channel and noise estimation unit estimate that channel response and noise level calculate corresponding estimation receiving symbol (y (n)) thereby be used to each data tones n;

(b) equalizer is used for each is estimated that receiving symbol y (n) and equalizer coefficients eq (n) multiply each other so that be each data tones n calculating weighting receiving symbol (w (n)=y (n) * eq (n));

(c) computing unit is according to being that weighting receiving symbol (w) that one group of data tones is calculated is each bit calculation tolerance via said data transmission channel transmitted by said equalizer.

In preferred embodiment according to metric calculation unit of the present invention; Computing unit according to by equalizer be weighting receiving symbol (W) that 2 data tones are calculated be each bit calculation in 4 bits forms a group as the log-likelihood ratio of measuring (LLR), said each bit is all modulated 2 data tones of the OFDM symbol that transmits via said data transmission channel.

In the preferred embodiment according to metric calculation unit of the present invention, channel and noise estimation unit for each data tones are estimated channel response (h) and noise variance (V) at preamble in the stage according to predetermined preamble signal.

In preferred embodiment, estimate that it all is plural number that receiving symbol (y), equalizer coefficients (eq) and weighting receive signal (w) according to metric calculation unit of the present invention.

In preferred embodiment according to metric calculation unit of the present invention, the equalizer coefficients (eq) of the equalizer of selecting for each data tones in the stage at preamble as follows: eq (N)=h ^*(n)/and V (n), wherein V (n) is the estimating noise variance of data tones, h ^*(n) be the conjugation of the channel response h (n) of data tones n.

In preferred embodiment, be each tone n calculated value P (n)=h (n) h according to metric calculation unit of the present invention ^*(n)/V (n).Then, be every couple of used tone n of two carrier modulation of modulating 4 bits ₁, n ₂Calculate following real-valued:

dp(n ₁，n ₂)＝4·b·[p(n ₁)-p(n ₂)]。

In a preferred embodiment, be similar to the division that carries out with V (n) to draw eq (n) and P (n) through right-shift operation (with 2 ^kRemove, k is an integer).

In the preferred embodiment according to metric calculation unit of the present invention, computing unit is two data tone (n according to weighting plural number receiving symbol ₁, n ₂) calculate said group the log-likelihood ratio (LLR) that 4 bits are formed, be described below:

dw _r＝2[b·w _r，1-w _r，2]

sw _r＝2[w _r，1+b·w _r，2]

q _r＝2(1+b)·w _r，1+2(b-1)·w _r，2

dw _i＝2[b·w _i，1-w _i，2]

sw _i＝3[w _i，1-w _i，2]

q _i＝2(1+b)·w _i，1+2(b-1)·w _i，2

LLR(bit#1)＝q _r+log{1+exp(dp-dw _r)}-log{1+exp(dp+dw _r)}

LLR(bit#2)＝q _r+log{1+exp(dp-sw _r)}-log{1+exp(dp+sw _r)}

LLR(bit#3)＝q _i+log{1+exp(dp-dw _i)}-log{1+exp(dp+dw _i)}

LLR(bit#4)＝q _i+log{1+exp(dp-sw _i)}-log{1+exp(dp+sw _i)}

W wherein _{R, n}Be the real part of W (n), w _{I, n}It is the imaginary part of W (n).

Description of drawings

Hereinafter, be described with reference to the drawings according to the dual carrier modulator (DCM) of the multiband OFDM transceiver of ultrabroad band of the present invention (UWB) radio individual access network and the preferred embodiment of metric calculation unit.

Fig. 1 illustrates the transfer of data wireless system according to prior art;

Fig. 2 illustrates the wireless network according to the coexistence of prior art;

Fig. 3 a illustrates the TFI frequency hopping pattern according to the OFDM transceiver of prior art;

Fig. 3 b illustrates the frequency hopping pattern according to the OFDM transceiver that comprises TRI pattern and FFI pattern of prior art;

Fig. 4 illustrates the data structure of the PLCP frame that is adopted like conventional OFDM transceiver;

Fig. 5 illustrates the block diagram of the conventional OFDM transceiver with transmitter and receiver;

Fig. 6 illustrates the block diagram according to the transmitter of prior art;

Fig. 7 illustrates the block diagram according to the receiver of prior art;

Fig. 8 illustrates the block diagram that comprises according to the transmitter of DCM modulator of the present invention;

Fig. 9 illustrates the block diagram according to the preferred embodiment of DCM modulator of the present invention;

Figure 10 illustrates the block diagram of the map unit in the DCM modulator according to the present invention;

Figure 11 illustrates the block diagram that comprises according to the receiver of metric calculation unit of the present invention.

Embodiment

As from Fig. 8, seeing, DCM modulator 1 according to the present invention forms the part of the OFDM Symbol modulator 2 in the transmitter 3.This transmitter 3 comprises input 4, and higher communication layers piece is supplied with this input with serial bit stream.Bit stream from higher communication layers piece is received by the header generator 5 in the transmitter 3, and this header generator adds the PHY header on the information payload to.In the PHY header, the initialize data rate.Header generator 5 is connected to error correction encoder 6 at its output, and this encoder is encoded the data flow that receives.The error correction encoder is encoded these bits through the convolution code with perforation.In addition, utilize Reed Solomon sign indicating number that the PLCP header of PLCP frame is encoded.Error correction encoder 6 is connected to interleave circuit 7 at its output.Interleave circuit 7 interweaves these bits.Interleave circuit 7 interweaves the bit stream that receives, thereby improves the performance of transfer of data, and the bit that wherein will interweave is supplied with the frequency expansion unit 8 in the transmitter 3.Frequency expansion unit 8 utilizes frequency expansion factor FSF that the bit that receives is expanded in frequency domain, and FSF sets according to the data transfer rate of transceiver.

Frequency expansion unit 8 links to each other with OFDM Symbol modulator 2 in the transmitter 3, and this OFDM Symbol modulator comprises according to DCM modulator 1 of the present invention.Dual carrier modulator 1 receives the bit stream of being expanded by frequency expansion unit 8 that interweaves, and carries out two carrier modulation (DCM) according to the data transfer rate of this transceiver for each subcarrier in the selected frequency band or data tones.

Fig. 9 is illustrated in the OFDM modulator 2 of transmitter 3 block diagram according to the preferred embodiment of DCM modulator 1 of the present invention.For the multiband OFDM transceiver with ultrabroad band (UWB) radio individual access network provides dual carrier modulator 1 as shown in Figure 9, this transceiver emission modulated symbols.Through the coded predetermined quantity (N of error correction encoder 6 _CBPS) bit modulate each symbol.

Dual carrier modulator 1 according to the present invention comprises grouped element 1-1, and it 8 receives bit streams from the frequency expansion unit, and with the N of serial bit stream _CBPSIndividual coded-bit is divided into a plurality of bit groups, and each bit group all has the bit of predetermined quantity m.In a preferred embodiment, grouped element 1-1 is with 200 coded-bit (N _CBPS=200) be divided into a plurality of bit groups, each bit group all has 4 bits (m=4).

Dual carrier modulator 1 further comprises map unit 1-2.In order to be mapped as complex symbol (y) from each bit group that grouped element 1-1 receives and map unit 1-2 to be provided.In a preferred embodiment, map unit 1-2 is mapped as 2 complex symbols respectively with a plurality of bit groups (containing 4 bits) so that produce 100 complex symbols for 100 data tones modulating an OFDM symbol.Grouped element 1-1 is a square with bit stream groupings.Each square that map unit 1-2 forms 4 bits all changes 2 complex symbol y into.

Figure 10 illustrates the preferred embodiment of the map unit 1-2 of dual carrier modulator 1.Map unit 1-2 comprises the first map level 1-2a and the second map level 1-2b.The first map level 1-2a is provided so that the one pole bit value of coded-bit in each bit group is mapped as bipolar value, promptly bit from 0, and the 1} value be mapped as bipolar value 1 ,+1}.

The second map level 1-2b is mapped as 2 complex symbols with 4 bipolar bits in each bit group, is described below:

$\left(\begin{array}{c}{y}_n\\ y_{n+50}\end{array}\right)=\frac{1}{\sqrt{{\mathrm{<figure-callout\; id="2"\; label="b"\; filenames="H2005814684X20061110E000011.png"\; state="\{\{state\}\}">b</figure-callout>}}^2+1}}\left(\begin{array}{cc}1& b\\ b& -1\end{array}\right)\left(\begin{array}{cc}{x}_{a\left(n\right)}& {\mathrm{jx}}_{a\left(n\right)+50}\\ x_{a\left(n\right)+1}& {\mathrm{jx}}_{a\left(n\right)+51}\end{array}\right)$

n＝1，2...49

$a\left(n\right)=\left\{\begin{array}{cc}2n& n=\mathrm{0,1,2},...24\\ 2n+50& n=\mathrm{25,26},...49\end{array}\right.$

Wherein b is a constant.

Map unit 1-2 output is many to complex symbol, and each all has 2 complex symbol y to complex symbol _n, y _N+50100 this complex symbol y ₀... y ₉₉Be used for being modulated at 100 data tones of single OFDM symbol.

Bit groupings provides good performance and error-correcting code and interleaver (interleaver) design.DCM modulator 1 according to the present invention further comprises the unit 1-3 that reorders that links to each other with the output of map unit 1-2.The complex symbol y rearrangement that the unit 1-3 that reorders exports map unit 1-2.

As seeing from Fig. 9, through these bits are divided into the group of for example being made up of 4 bits, guaranteed the adjacent bit in coded bit stream, i.e. the adjacent bit of error correction encoder 6 outputs can not participated in same group that 4 bits are formed.Other data tones of the two carrier modulation of a plurality of in addition participations are at N _CBPSSeparated by a distance in the frequency domain of/4 data tones, this distance equals the half the of frequency band part.

As from Fig. 8, seeing, linking to each other with IFFT unit 9 in the OFDM Symbol modulator 2 as shown in Figure 9 according to the output of dual carrier modulator 1 of the present invention.Thereby it is time signal with this signal transition that IFFT unit 9 carries out invert fast fourier transformation.Parallel-to-serial converter 10 in the OFDM Symbol modulator 2 is with the output serialization of IFFT unit 9.At output, OFDM Symbol modulator 2 links to each other with temporal extension unit 11, and these these symbols of temporal extension unit extensions are in order to improve processing gain and Fen Ji (diversity).At last, frequency hopping transmitter 12 is via data transmission channel emission OFDM symbol.

In a preferred embodiment, as shown in Figure 9 dual carrier modulator 1 according to the present invention is realized by the look-up table of storing in the internal memory.

In a preferred embodiment, the look-up table in the internal memory begins to provide as follows:

In the preferred embodiment according to dual carrier modulator of the present invention, scale factor K is chosen to be

K wherein ₀It is the corresponding scale factor of QPSK modulation.

Constant b is preferably set to 2 (b=2).

The optimal value of parameter b depends on several characteristics and parameter.It depends on the design of channel transfer functions and other modem parameters.For example, there are several kinds of data rate modes in the MB OFDM transceiver for as proposing at the IEEE 802.15.3a that is used for the UWB modulator-demodulator, and wherein each data rate mode is characterized as being one group of error correction code rate and expansion level, i.e. time domain and frequency domain expansion.Error correction code rate and expansion level have determined the selected value of " b ".When using bigger expansion, the optimum value of " b " is less and more approach 1.For in the higher data than high s/n ratio place work, the optimum value of " b " approaches 2 more greatly and more.For little signal to noise ratio snr, the optimum value of constant b levels off to b=1.For big signal to noise ratio snr, optimum value levels off to b=2.

Figure 11 is illustrated in the block diagram according to metric calculation unit 13 of the present invention in the receiver 14.Receiver 14 is carried out the operation opposite with transmitter shown in Fig. 83.Receiver 14 comprises frequency-hopping receiver 15, and it receives the OFDM symbol that sends according to predetermined frequency hopping pattern.Serial-to-parallel converter 16 changes the output of frequency-hopping receiver 15 into be applied to fast fourier transform unit 17 parallel signal.Fast Fourier transform (FFT) is applied on the selected frame of time-domain signal.

There is a signal in output in FFT unit 17, and this signal is the noisy shifted version of the input of the contrary FFT in transmitter place.

For sending symbol x (n), the following symbol y (n) of FFT unit 17 outputs in each of input place of contrary FFT unit: y (n)=h (n) x (n)+γ (n), wherein h (n) is the channel response of tone separately, γ (n) is a noise signal.

The variance of noise signal γ (n) is V (n).In general, the channel response h (n) of data transmission channel is a plural number.

The output of FFT unit 17 links to each other with a tap equalizer 13-1 in the metric calculation unit 13 according to the present invention.Metric calculation unit 13 comprises equalizer 13-1, channel and noise estimation unit 13-2, log-likelihood calculations unit 13-3, like what in Figure 11, can see.The output of equalizer 13-1 goes expanding element 18 and time to go expanding element 19 to link to each other with frequency, and the operation opposite with the 3 medium frequency expanding elements 8 of transmitter shown in Fig. 8 and temporal extension unit 11 carried out in these two unit.The output of metric calculation unit 13 links to each other with deinterleave circuit 20, and this deinterleave circuit is carried out the operation opposite with interleave circuit shown in Fig. 87.The output of interleave circuit 20 links to each other with error correcting/decoding device 21, for example Viterbi decoder.The data transfer rate of the data flow of the OFDM symbol that 22 identifications of header extractor receive, and remove expanding element 18,19 and error correcting/decoding device 21 for deinterleave circuit 20, time and frequency and adjust data transfer rates.

In order to estimate that for each data tones n channel response and noise level provide the metric calculation unit 13 that comprises interchannel noise estimation unit 13-2 so that calculate corresponding estimation receiving symbol Y (n).Channel links to each other with FFT unit 17 at its input with noise estimation unit 13-2, links to each other with equalizer unit 13-1 with LLR computing unit 13-3 at its output.Channel and noise estimation unit 13-2 for each data tones estimate channel response h and noise level V at preamble in the stage according to the predetermined preamble coded signal, and possibly adjust it in the stage in payload.In the processing stage of this preamble, adjust the equalizer coefficients of equalizer 13-1 for each data tones by channel and noise estimation unit 13-2:

eq(n)＝2h ^*(n)/V(n)

H wherein ^*(n) be the conjugation of estimated channel response h (n).As shown in Figure 11, channel and noise estimation unit 13-2 adjust via control pair equalizer coefficients eq.

Can be many group adjacent tone, and even for whole frequency band calculating V (n), in order to reduce complexity.

In addition, calculate following real number for each data tones:

$p\left(n\right)=\frac{{\left|h\left(n\right)\right|}^2}{v\left(n\right)}$

Channel and noise estimation unit 13-2 are set and the real-valued p (n) that each data tones in each used band is calculated equalizer coefficients eq (n) and channel response h (n).

In unit 13-2, for being used to modulate every couple of used tone n of two carrier modulation of 4 bits ₁, n ₂Calculate following real-valued:

dp(n ₁，n ₂)＝4·b·[p(n ₁)-p(n ₂)]。

In a preferred embodiment, n ₂=n ₁+ N _CBPS/ 2=n ₁+ 50.

Equalizer 13-2 and each the estimation receiving symbol y (n) that receives from FFT unit 17 multiply each other, thereby are that each data tones n calculates weighting receiving symbol w (n).

w(n)＝y(n)·eq(n)＝y(n)·2h ^*(n)/v(n)。

The value of equalizer coefficients depends on tone index, band index (in frequency hop sequences) and possibly depend on temporary transient Noise Estimation amount.

LLR computing unit 13-3 is each bit calculation tolerance via data transmission channel transmitted according to the weighting receiving symbol (w) that is one group of data tones output by said equalizer 13-1.In a preferred embodiment; Computing unit 13-3 according to by equalizer 13-1 be weighting receiving symbol (w) that 2 data tones are calculated be each bit calculation in 4 bits forms a group as the log-likelihood ratio of measuring (LLR), said 4 bit modulation are via 2 data tones of the OFDM symbol that data transmission channel transmitted.

In a preferred embodiment, computing unit 13-1 is according to being used for two data tone (n ₁, n ₂) weighting plural number receiving symbol (w (n ₁), w (n ₂)) calculate said group the log-likelihood ratio of forming by 4 bits (LLR), be described below:

dw _r＝2[b·w _r，1-w _r，2]

sw _r＝2[w _r，1+b·w _r，2]

q _r＝2(1+b)·w _r，1+2(b-1)·w _r，2

dw _i＝2[b·w _i，1-w _i，2]

sw _i＝3[w _i，1-w _i，2]

q _i＝2(1+b)·w _i，1+2(b-1)·w _i，2

LLR(bit#1)＝q _r+log{1+exp(dp-dw _r)}-log{1+exp(dp+dw _r)}

LLR(bit#2)＝q _r+log{1+exp(dp-sw _r)}-log{1+exp(dp+sw _r)}

LLR(bit#3)＝q _i+log{1+exp(dp-dw _i)}-log{1+exp(dp+dw _i)}

LLR(bit#4)＝q _i+log{1+exp(dp-sw _i)}-log{1+exp(dp+sw _i)}

Carry out log{1+exp (x) by look-up table in one embodiment } calculating.In alternate embodiments, replace top function with following being similar to:

Advantage according to metric calculation unit 13 of the present invention is lower technical sophistication degree.For the required extra computation of log-likelihood ratio (LLR) that draws every coded-bit comprises the multiply operation of multiplying each other with constant and some real numbers and the map operation of 2 look-up tables.For special circumstances b=1, complexity even littler only comprises the map operation of 5 real number additions and 2 look-up tables.From complexity, the embodiment with constant b=1 provides minimum complexity.Can select other values of b for more performance.In a preferred embodiment, scale factor is chosen as b=2.In this embodiment, the extra computation for the log-likelihood ratio that draws every bit is the map operation of 6 additions and 2 look-up tables.

The present invention is provided for improving the device of the performance of coded OFDM symbol, special multi-band OFDM symbol.Compare performance with the transceiver that utilizes conventional qpsk modulator and be improved, must be from frequency-selective channel in conventional qpsk modulator the restore errors correcting layer.Increased frequency diversity to obtain less variability and to improve the overall performance of error correction layer according to dual carrier modulator of the present invention (DCM).In a preferred embodiment, dual carrier modulator is based on a pair of tone being divided into groups and 4 bits being carried in each on the tone.Causing quality like this is that the signal to noise ratio (snr) of bit metric is similar.A data tone decay is being replaced input at the error correction layer have in two specific embodiments that can wipe bit to zero (spectral null); According to dual carrier modulator of the present invention and corresponding metric calculation unit 13 two tones are used for each bit, and other tones provide Useful Information probably.In a preferred embodiment, the DCM modulator is used to the mapping of 2 * 2 quadratures to produce two symbols of two tones of modulation., the error correction layer can realize significant improvement when using High Data Rate.

Claims (13)

1. the dual carrier modulator (DCM) of multi-band OFDM (Orthodoxy Frequency Division Multiplex) transceiver of ultrabroad band (UWB) wireless network that is used for the transmission OFDM modulation symbol is wherein by the first predetermined quantity N _CBPSCoded-bit each OFDM symbol is modulated, said dual carrier modulator (1) comprising:

(a) grouped element (1-1) is used for the N with serial bit stream _CBPSIndividual coded-bit is divided into a plurality of bit groups, and each bit group has 4 bit (m ₁, m ₂, m ₃, m ₄);

(b) map unit (1-2), the bit group that is used for each that receives from said grouped element (1-1) had 4 bits is mapped as two complex symbols,

First bit (the m of each bit group wherein ₁, m ₂) be mapped as the real part of two complex symbols, and

Second bit (the m of each bit group wherein ₃, m ₄) be mapped as the imaginary part of two complex symbols; And

(c) unit (1-3) that reorders is used for the complex symbol rearrangement with said map unit mapping,

The corresponding data tones of each complex symbol Modulation OFDM symbol wherein;

Wherein grouped element (1-1) is with N _CBPS=200 coded-bits are divided into a plurality of bit groups, and each bit group has 4 bits;

Wherein map unit (1-2) is mapped as 2 complex symbol (y respectively with a plurality of bit groups that each comprises 4 bits _ny _N+NCBPS/4) so that for modulating the N of an OFDM symbol _CBPS/ 2 data tones and produce N _CBPS/ 2 complex symbol (y ₀... y _NCBPS/2-1).

2. according to the dual carrier modulator (DCM) of claim 1, wherein map unit (1-2) comprising:

First map level, it is used for the one pole bit value of the coded-bit of each bit group is mapped as bipolar bit value, and

Second map level, quadrature 2 * 2 mappings that it provides 2 plural numbers that 4 bipolar bits are formed to be mapped as 2 complex symbols, wherein said quadrature 2 * 2 mapping definitions are:

$\left(\begin{array}{c}{y}_n\\ y_{n+50}\end{array}\right)=\frac{1}{\sqrt{b^2+1}}\left(\begin{array}{cc}1& b\\ b& -1\end{array}\right)\left(\begin{array}{c}{x}_{a\left(n\right)}+j{x}_{a\left(n\right)+50}\\ x_{a\left(n\right)+1}+j{x}_{a\left(n\right)+50}\end{array}\right)$

n＝0，1...49

$a\left(n\right)=\left\{\begin{array}{cc}2n& n=\mathrm{0,1,2},...24\\ 2n+50& n=\mathrm{25,26},...49\end{array}\right.$

Wherein b is a constant,

X wherein _iIt is bipolar bit value by said first map level output.

3. according to the dual carrier modulator (DCM) of claim 2, wherein map unit (1-2) is formed by the look-up table of storing in the internal memory.

4. according to the dual carrier modulator of claim 3, the said look-up table of wherein in said internal memory, storing is as shown in the table:

Wherein

Be real constant, and m ₁, m ₂, m ₃, m ₄Be four bits of a bit group.

5. according to the dual carrier modulator (DCM) of claim 2 or claim 4, wherein constant b is 2.

6. metric calculation unit that is used for multi-band OFDM (Orthodoxy Frequency Division Multiplex) transceiver of ultrabroad band (UWB) radio individual access network; Said transceiver receives the OFDM symbol via data transmission channel transmitted; Wherein each OFDM symbol is carried out two carrier modulation, by predetermined quantity N by the described dual carrier modulator of claim 1 (DCM) _CBPS2 data tones of each Modulation OFDM symbol of coded-bit,

Said metric calculation unit (13) comprising:

(a) channel and noise estimation unit (13-2), be used to each data tones n estimate channel response h (n) and noise level v (n) thus calculate the emission symbol y (n) of corresponding estimation;

(b) equalizer (13-1) is used for the emission symbol y (n) of each calculating is multiplied each other with equalizer coefficients eq (n) so that be each data tones n calculating weighting receiving symbol w (n);

(c) computing unit (13-3) is each the bit calculation tolerance via said data transmission channel transmitted according to the weighting receiving symbol w (n) that is calculated for each data tones n by said equalizer (13-1);

Wherein computing unit (13-3) basis is 2 data tone (n by equalizer ₁, n ₂) the weighting receiving symbol (w (n that calculated ₁), w (n ₂)) and be that each bit calculation in 4 bits form a group is estimated 2 data tone (n of the OFDM symbol that said each bit modulation is transmitted via said data transmission channel as the log-likelihood ratio (LLR) of tolerance ₁, n ₂);

Wherein channel and noise estimation unit (13-2) are that each data tones n estimates channel response h (n) and noise variance V (n) according to predetermined preamble signal in the stage at preamble,

Wherein computing unit (13-3) is according to weighting receiving symbol (w (n ₁), w (n ₂)) and be 2 data tone (n ₁, n ₂) calculate said group the log-likelihood ratio that 4 bits are formed, be described below:

dw _r＝2[b·w _r，1-w _r，2]

sw _r＝2[w _r，1+b·w _r，2]

q _r＝2(1+b)·w _r，1+2(b-1)·w _r，2

dw _i＝2[b·w _i，1-w _i，2]

sw _i＝3[w _i，1-w _i，2]

q _i＝2(1+b)·w _i，1+2(b-1)·w _i，2

LLR(bit#1)＝q _r+log?{1+exp(dp-dw _r)}-log{1+exp(dp+dw _r))

LLR(bit#2)＝q _r+log{1+exp(dp-sw _r)}-log{1+exp(dp+sw _r)}

LLR(bit#3)＝q _i+log?{1+exp(dp-dw _i)}-log{1+exp(dp+dw ₁)}

LLR(bit#4)＝q _i+log(1+exp(dp-sw ₁)}-log(1+exp(dp+sw _i)}

W wherein _{R, n}Be the real part of weighting receiving symbol w (n), and w _{I, n}Be the imaginary part of weighting receiving symbol w (n),

Dw wherein _r, sw _r, q _r, dw _i, sw _i, q _iBe variable, b is a constant, and LLR is a log-likelihood ratio, and dp is real-valued, wherein dp=4b [p (n ₁)-p (n ₂)], and p (n ₁), p (n ₂) calculate through using following formula: p (n)=h (n) h ^*(n)/and V (n), h ^*(n) be the conjugation of the channel response h (n) of said data tones n.

7. according to the metric calculation unit of claim 6, wherein channel and noise estimation unit (13-2) are many group adjacent data tone estimating noise variable v according to predetermined preamble signal in the stage at preamble.

8. according to the metric calculation unit of claim 6, emission symbol y (n), equalizer coefficients eq (n) and the weighting receiving symbol w (n) that wherein estimates is plural number.

9. according to the metric calculation unit of claim 6 or 7, the equalizer coefficients eq (n) of the said equalizer of wherein selecting for each data tones in the stage at preamble (13-2) as follows: eq (n)=2h ^*(n)/v (n)

Wherein v (n) is the estimated level of noise of said data tones,

h ^*(n) be the conjugation of the channel response h (n) of said data tones n.

10. according to the metric calculation unit of claim 9, wherein calculate following real-valued: p (n)=h (n) h for each data tones ^*(n)/V (n).

11., wherein be every couple of data tone n of said dual carrier modulator (DCM) modulation according to the metric calculation unit of claim 10 ₁, n ₂4 used bits calculate following real-valued:

dp＝4·b·[p(n ₁)-p(n ₂)]，

Wherein b is a constant, and p (n) is real-valued.

12. according to the metric calculation unit of claim 6, wherein realize function log{1+exp (x) } by look-up table.

13., wherein come approximating function log{1+exp (x) by following formula according to the metric calculation unit of claim 6 }:

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