CN100571002C - A kind of asymmetric formula current regulator - Google Patents
A kind of asymmetric formula current regulator Download PDFInfo
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- CN100571002C CN100571002C CNB2005100118324A CN200510011832A CN100571002C CN 100571002 C CN100571002 C CN 100571002C CN B2005100118324 A CNB2005100118324 A CN B2005100118324A CN 200510011832 A CN200510011832 A CN 200510011832A CN 100571002 C CN100571002 C CN 100571002C
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Abstract
A kind ofly be used for the current regulator that superconducting magnet discharges and recharges, by voltage cell (U
V), transformer unit (U
T) and current unit (U
I) form.Voltage cell (U
V) be that a plurality of DC side are the voltage source converter of capacitor, current unit is the current source converter (csc) of a direct current side joint superconducting magnet (L), the interchange outlet side of voltage source converter links to each other with the former limit of discrete transformer, the interchange outlet side of current source converter (csc) links to each other with the two ends of series transformer secondary, wherein transformer unit (U
T) be in series by a plurality of transformers, the quantity of transformer equals the quantity of voltage source converter.Voltage cell (U
V) adopt the bridge Phase shifted PWM Controlled mode, and current unit (U
I) by voltage cell (U
V) the auxiliary electromotive force that provides, when the electric current commutation, realize zero-current switching.The present invention is simple and compact for structure, and the power density height has not only improved the performance of magnet charge-discharge system, and can reduce cost.Owing to realized also having reduced switching loss by zero-current switching, improved efficient, prolonged the life-span of switching tube.
Description
Technical field
The present invention relates to a kind of current regulator that superconducting magnet discharges and recharges that is used for, particularly asymmetric formula current regulator.
Background technology
Zero resistance that superconduction has and the big characteristic of high-intensity magnetic field download stream ability, make superconducting magnet obtain using widely, particularly in high-energy physics experiment, be used to produce the large-scale superconducting magnet of high-intensity magnetic field, almost be substituted the conventional magnet that all volumes are big, power consumption is many; Simultaneously, along with the development of superconducting power technology, particularly miniature superconducting energy storage, commercialization abroad is widely used in and improves the quality of power supply, raising stability of power system etc., and these all make superconducting magnet obtain unprecedented application.
The general running current of superconducting magnet is all in the kA level, and is a big inductance, and this technology of discharging and recharging to superconducting magnet has proposed new requirement.Charging and discharging currents is big, voltage is low, and charging/discharging voltage excursion stable and voltage is big, needs the switching frequency height simultaneously, power density is big and control performance good, these all are the basic demands that superconducting magnet discharges and recharges, and particularly require more urgent on the miniature superconducting energy storage of commercialization.
At present prior art scheme commonly used all is to adopt each cover of charging/discharging apparatus, United States Patent (USP) Pub.No.US2002/0030952 " superconducting magnet charging method and device " for example, United States Patent (USP) 5,181,170 " superconducting magnet and electric supply installations thereof ".In the above-mentioned prior art: charging can be finished two functions: during stable state to superconducting magnet charging and to keep magnet current constant; Discharge equipment is that chopper is finished quick discharge function.The problem that exists is: discharging and recharging not only needs two complete equipments, and if charging device should keep that magnet current is constant finishes quick-charge function then capacity is very big again, as United States Patent (USP) 6,157,094 " superconducting magnet and electric supply installation thereof "; The US2002/0030952 that discharge equipment, Fig. 1 show " superconducting magnet charging method and device ", 10,11 is magnet part among the concrete structure figure, 19 is the magnet charge power supply, other parts are discharge portion, also are chopper, and it is directly converted to voltage with the electric current of superconducting magnet.It is directly cut magnet current by switch 20 and 22, this makes switching loss very big, and the condenser capacity that direct voltage 25 parts need is very big, thereby the exciting voltage of magnet is big, this is stable not only bad for magnet, and make the magnet A.C.power loss increase, improved the operating cost of magnet.
Summary of the invention
For overcoming the deficiency of prior art, the invention provides a kind of current regulator that superconducting magnet discharges and recharges that is used for, it is made up of voltage cell, transformer unit and current unit three parts.Voltage cell is that a plurality of DC side are the voltage source converter of capacitor, current unit is the current source converter (csc) of a direct current side joint superconducting magnet, the interchange outlet side of voltage source converter links to each other with the former limit of discrete transformer, the interchange outlet side of current source converter (csc) links to each other with the two ends of series transformer secondary, wherein transformer unit is in series by a plurality of transformers, and the quantity of transformer equals the quantity of voltage source converter.The present invention not only can charge to magnet, the electric energy of storing in the magnet can also be discharged, and charging/discharging voltage is adjustable flexibly.Current unit electric current of the present invention is big but voltage is low, and voltage cell electric current and voltage are all little for contact capacity, this has not only reduced switching loss, can also improve switching frequency, thereby reduced the capacitor volume in the voltage cell greatly, dwindle the volume of transformer in the transformer unit, thereby improved power density and systematic function.Because a plurality of voltage source converters are arranged,, so both can reduce the capacity of single voltage source converter among the present invention, can improve the power that discharges and recharges on the whole again so voltage cell can insert cascaded inverter.Owing to only insert a superconducting magnet,, thereby reduce device cost so the quantity of current source converter (csc) can reduce the quantity of switching tube so only with one.Only compare with voltage cell with the current regulator of a voltage source converter, owing to adopted a plurality of voltage source converters, so can improve the power that discharges and recharges greatly.And compare with the structure that adopts the single current adjustor module to connect, this current regulator only need be with a current source converter (csc), thereby can reduce cost greatly under the prerequisite of performance guaranteeing.
Voltage cell of the present invention adopts the bridge Phase shifted PWM Controlled mode, and the auxiliary electromotive force that current unit provides by voltage cell is realized zero-current switching when the electric current commutation.Phase shifting control is the impulse phase complementation that makes underarm on the bridge of voltage source converter, and the pulse sequence of bridge diagonal arm homophase not, leading or the lag time of the bridge diagonal arm pulse by regulation voltage source converter, change the control mode of the pulsewidth of described asymmetric formula current regulator output voltage.And the principle of auxiliary electromotive force is to realize the key of zero-current switching.So-called auxiliary electromotive force, be exactly in the switching tube of two brachium pontis of current source converter (csc) the moment in commutation, give the switching tube triggering signal that to open brachium pontis earlier, the switching tube of control voltage source converter then, make it on the former limit of transformer, to produce commutation voltage, after being folded to secondary since with the current opposite in direction that flows through the switching tube that will turn-off, flow through this branch current and reduce thereby make; And because identical, flow through this branch current and increase, by the time after flowing through the electric current of the switching tube that will turn-off and reducing to zero, turn-off this switching tube again, thereby realized the shutoff of zero current thereby make with the sense of current that flows through the switching tube that to open.Owing to have only a current source converter (csc), and corresponding a plurality of voltage source converter, so, in the method for this asymmetric current regulator phase shifting control, need the leading-bridge of each voltage source converter and the pulse of lagging leg to coordinate mutually, thereby increase work efficiency.The present invention is simple and compact for structure, the power density height, and volume is little, has not only improved the performance of magnet charge-discharge system, and can significantly reduce cost.Owing to realized also having significantly reduced switching loss by zero-current switching, improved efficient, and prolonged the life-span of switching tube.
Description of drawings
Fig. 1 is the schematic diagram of prior art U.S. Pat 2002/0030952;
Fig. 2 is main line figure of the present invention.Among the figure: U
IBe current unit, U
TTransformer unit, U
VVoltage cell, S1, S2, S3, S4, S5, S6, S7, S8, S9, S10, Sn5, Sn6, Sn7, Sn8, Sn9 and Sn10 are switch, DC1, DCn is a DC power supply, LOAD1 and LOADn are load, and C1 and Cn are capacitor, and TR1 and TRn are common transformer, o indication transformer end of the same name, L are superconducting magnet;
Fig. 3 is 2 voltage source converters of the specific embodiment of the invention and the main circuit principle schematic of 1 current source converter, among the figure: U
IBe current unit, U
TTransformer unit, U
VVoltage cell, S1, S2, S3, S4, S5, S6, S7, S8, S9, S10, S11, S12, S13, S14, S15 and S16 are switch, DC1, DC2 is a DC power supply, LOAD1 and LOAD2 are load, and C1 and C2 are capacitor, and TR1 and TR2 are common transformer, o indication transformer end of the same name, L are superconducting magnet;
Fig. 4 is specific embodiments of the invention 1, wherein D1, D2, D3, D4 are diode, T1, T2, T3, T4, T5, T6, T7, T8, T9, T10, T11 and T12 are IGBT, and DC1, DC2 are DC power supply, LOAD1 and LOAD2 are load, C1 and C2 are capacitor, and S13, S14, S15 and S16 are switch, and TR1 and TR2 are common transformer, o indication transformer end of the same name, L are superconducting magnet;
Fig. 5 is the schematic diagram of the phase shift charging control mode of the embodiment of the invention 1;
Fig. 6 is the schematic diagram of the phase shift discharge control mode of the embodiment of the invention 1;
Fig. 7 is embodiments of the invention 2, wherein G1, G2, G3, G4 are thyristor, T5, T6, T7, T8, T9, T10, T11 and T12 are IGBT, and DC1, DC2 are DC power supply, LOAD1 and LOAD2 are load, C1 and C2 are capacitor, and S13, S14, S15 and S16 are switch, and TR1 and TR2 are common transformer, o indication transformer end of the same name, L are superconducting magnet;
Fig. 8 is the schematic diagram of the phase shift charging control mode of the embodiment of the invention 2;
Fig. 9 is the schematic diagram of the phase shift discharge control mode of the embodiment of the invention 2;
Embodiment
Below in conjunction with accompanying drawing the present invention is further described:
Main circuit line map of the present invention as shown in Figure 2.It is by voltage cell U
V, transformer unit U
TWith current unit U
IThree parts are formed.Transformer unit U
TBy a plurality of transformer TR1, TR2 ... the TRn secondary is cascaded and forms.Current source converter (csc) CSC is composed in parallel by two brachium pontis, and first switch S 1 and the 3rd switch S 3 constitute one of them brachium pontis, and second switch S2 and the 4th switch S 4 constitute wherein another one brachium pontis.The two ends of described two brachium pontis constitute the dc output end of current source converter (csc) CSC, and L links to each other with superconducting magnet; The mid point of described two brachium pontis constitutes the ac output end of current source converter (csc) CSC, transformer TR1, TR2 that secondary is connected mutually ... among the TRn: two ports that the first transformer TR1, n transformer TRn do not connect mutually link to each other with the ac output end of current source converter (csc) CSC respectively.The first voltage source converter VSC1 is also composed in parallel by two brachium pontis, and the 5th switch S 5 and minion are closed S7 and constituted one of them brachium pontis, and the 6th switch S 6 and octavo are closed S8 and constituted wherein another one brachium pontis.The two ends of described two brachium pontis constitute the first voltage source converter VSC1 dc output end, link to each other with the first capacitor C1, and the mid point of described two brachium pontis constitutes the ac output end of the first voltage source converter VSC1, link to each other with the two ends of the first transformer TR1.The first capacitor C1 of the first voltage source converter VSC1 dc output end parallel connection be connected in parallel by the 9th switch S 9 and the first DC power supply DC1, the tenth switch S 10 and the first load LOAD1 branch road of forming that is in series respectively.Other transformer TR2 ... TRn, second voltage source converter to the n voltage source converter VSC1 ... all the other n-1 structure of VSCn is identical with structure and the connected mode of the described first voltage source converter VSC1 with connected mode, and n is the integer more than or equal to 2.
2 voltage source converters of the specific embodiment of the invention and the main circuit principle schematic of 1 current source converter are as shown in Figure 3.It is by voltage cell U
V, transformer unit U
TWith current unit U
IThree parts are formed.Transformer unit U
TBe cascaded and form by transformer TR1, TR2 secondary.Current source converter (csc) CSC is composed in parallel by two brachium pontis, and first switch S 1 and the 3rd switch S 3 constitute one of them brachium pontis of current source converter (csc) CSC, and second switch S2 and the 4th switch S 4 constitute the another one brachium pontis of current source converter (csc) CSC.The two ends of described two brachium pontis constitute the dc output end of current source converter (csc) CSC, and L links to each other with superconducting magnet; The mid point of described two brachium pontis constitutes current source converter (csc) CSC ac output end, and two ports of the first transformer TR1, the second transformer TR2 that connects mutually with secondary link to each other.The first voltage source converter VSC1 is also composed in parallel by two brachium pontis, the 5th switch S 5 and minion are closed S7 and are constituted first one of them brachium pontis of voltage source converter VSC1, and the 6th switch S 6 and octavo are closed the another one brachium pontis that S8 constitutes the first voltage source converter VSC1.The two ends of described two brachium pontis constitute the dc output end of the first voltage source converter VSC1, link to each other with the first capacitor C1, and the mid point of described two brachium pontis constitutes the ac output end of its first voltage source converter VSC1, link to each other with the two ends of the first transformer TR1.The first capacitor C1 of the first voltage source converter VSC1 dc output end parallel connection be connected in parallel by the 9th switch S 9 and the first DC power supply DC1, the tenth switch S 10 and the first load LOAD1 branch road of forming that is in series respectively.The structure of the second transformer TR2, the second voltage source converter VSC2 is identical with structure and the method for attachment of the above-mentioned first voltage source converter VSC1 with connected mode.
The course of work that current regulator of the present invention is described according to Fig. 3 is as follows.
The course of work of the first voltage source converter VSC1: the 13 switch S 13 closures, when the 14 switch S 14 was opened, promptly the first voltage source converter VSC1 linked to each other with DC power supply DC1, and L charges to magnet.The 5th switch S 5 and minion are closed the S7 angle of flow and are differed 180 °, a bit of dead band that is separated by, centre.Octavo is closed S8 and the 6th switch S 6 also differs 180 °, a bit of dead band that is separated by, centre.It is leading-bridge that the 5th switch S 5 and minion are closed S7, and octavo is closed S8 and the 6th switch S 6 is a lagging leg.When the switch S 5 that will form the voltage converter is respectively alternately cut-off with S8, S6 and S7, the interchange outlet side of voltage converter, the former limit that promptly is the first transformer TR1 is output as ac square wave, the secondary output of first transformer also is ac square wave, this moment, switch S 1, S2, S3 and the S4 of electric current converter worked in rectification state, gave magnet L charging.The big I of magnet L two ends charging voltage is recently regulated by switch S 5 of regulating the first voltage converter VSC1 and the duty of S8, S6 and S7.Logical relation is as follows: switch S 5 and S8 closure, switch S 6 is opened with S7, the former limit of the first transformer T R1 is output as the voltage of the first capacitor C1, be positive voltage, this moment Closing Switch S2 and S3, transformer secondary two ends be output as after the transformer transformation on the occasion of voltage, voltage direction is determined by end of the same name, size is voltage/transformer voltage ratio of the first capacitor C1, gives magnet L charging.If open switch S 5, closed minion is closed S7, then transformer T primary current is by switch S 7 and S8 afterflow, the former limit output voltage of the first transformer TR1 is zero, the voltage at transformer secondary two ends is therefore vanishing also, thereby making magnet L both end voltage is zero, and the electric current I of magnet L remains unchanged, and more than is the upper half of the action of switch S 5 and S8, S6 and S7; Connect half cycle, Closing Switch S6, the former limit of opening switch S 8, the first transformer TR1 is output as the reverse voltage of the first capacitor C1, is negative voltage, this moment Closing Switch S1 and S4, transformer secondary two ends are output as the negative value voltage after the first transformer TR1 transformation, and voltage direction is determined that by end of the same name size is voltage/transformer voltage ratio of the first capacitor C1, magnet L both end voltage is opposite with the direction of both ends of the first transformer TR1 secondary, and its value of equal and opposite in direction is still for just.The voltage of the first capacitor C1 after the transformer transformation and the merchant of transformer voltage ratio, identical with switch S 5 with the upper half of the action of S8, switch S 6 and S7, give magnet L charging; If open switch S 7, Closing Switch S5, then transformer T primary current is by switch S 5 and S6 afterflow, the former limit output voltage of the first transformer TR1 is zero, the voltage at secondary two ends is therefore vanishing also, is zero thereby make magnet L both end voltage, and the electric current I of magnet L remains unchanged, this is similar to the upper half of the action of S7 to switch S 5 and S8, switch S 6, is switch S 5 and the lower half of the action of S6, S7 and S8.By the relative phase shift of by-pass cock S5 and switch S 7 and S6 and S8, the average voltage at scalable magnet L two ends, the i.e. charging voltage of flexible magnet L.The second voltage source converter VSC2 and the first voltage source converter VSC1 are identical, a because shared current source converter (csc), so need to coordinate the action of these voltage source converters, can make the action of lagging leg of these voltage source converters identical, control the charge power of each voltage source converter by the relative displacement of adjusting leading-bridge and lagging leg flexibly.
Switch S 14 closures, when switch S 13 was opened, voltage regulator VSC1 linked to each other with the first load LOAD1, and L discharges to magnet.The switching logic relation is as follows: switch S 2, S3 and switch S 1, S4 closure, superconducting magnet electric current are by switch S 2, S3 and switch S 1, S4 afterflow, and neither charging is not discharged yet.Switch S 5 and S8 closure, switch S 6 and S7 open, the former limit of the first transformer TR1 is output as the forward voltage of the first capacitor C1, be positive voltage, the secondary two ends be output as after the first transformer TR1 transformation on the occasion of voltage, the voltage direction of transformer secondary with flow through switch S 1 and, the current opposite in direction of S4, thereby make flow through switch S 1 and, the electric current of S4 reduces; And with flow through switch S 2 and, the sense of current of S3 is identical, thereby make flow through switch S 2 and, the electric current of S3 increases.When flow through switch S 1 and, the electric current of S4 reduces to zero, open switch S 1 and, S4, thereby realized zero-current switching, and then switch S 5 is opened, switch S 7 closures, then the first transformer TR1 primary current by switch S 7 and, the S8 afterflow, former limit output voltage is zero, the voltage at secondary two ends is therefore vanishing also, is zero thereby make magnet L both end voltage, and the electric current I of magnet L remains unchanged.And then make switch S 6 closures, switch S 8 is opened, the former limit of the first transformer TR1 is output as the reverse voltage of the first capacitor C1, be negative voltage, the secondary two ends are output as the negative value voltage (voltage direction is determined that by end of the same name size is voltage/transformer voltage ratio of the first capacitor C1) after the transformer transformation, that is to say magnet L both end voltage, it is opposite with the electric current I direction of magnet, magnet L discharge.It more than is the upper half of the action of switch S 2 and S3, switch S 1 and S4, switch S 5 and S8 and switch S 6 and S7; Connect half cycle, Closing Switch S1 and S4, the former limit of the first transformer T R1 is output as the reverse voltage of the first capacitor C1, be negative voltage, the secondary two ends are output as the negative value voltage after the transformer transformation, the voltage direction of secondary with flow through switch S 1 and, the sense of current of S4 is identical, thereby make flow through switch S 1 and, the electric current of S4 increases; The voltage of secondary with flow through switch S 2 and, the opposite current of S3, thereby the electric current that flows through switch S 2 and S3 is reduced.Reduce to zero when the electric current of flow through switch S 2 and S3, open switch S 2 and S3, thereby realized zero-current switching.Closing Switch S5 opens switch S 7 then, and then the first transformer TR1 primary current is by switch S 5 and S6 afterflow, the former limit output voltage of the first transformer TR1 is zero, the voltage at secondary two ends is therefore vanishing also, is zero thereby make magnet L both end voltage, and the electric current I of magnet L remains unchanged.And then switch S 6 is opened, switch S 8 closures, the former limit of the first transformer TR1 is output as the forward voltage of the first capacitor C1, be positive voltage, the secondary two ends be output as after the transformer transformation on the occasion of voltage, voltage direction is identical with the direction of end decision of the same name, size is voltage/transformer voltage ratio of the first capacitor C1, that is to say magnet L both end voltage, it is opposite with the electric current I direction of magnet, magnet L discharge.It more than is the lower half of the action of switch S 2 and S3, switch S 1 and S4, switch S 5 and S8 and switch S 6 and S7.By the duty ratio in half cycle of by-pass cock S2 and S3, switch S 1 and S4, switch S 5 and S8 and switch S 6 and S7, the average voltage at scalable magnet L two ends, the i.e. discharge voltage of flexible magnet L.The switch motion principle of the second voltage source converter VSC2 and the first voltage source converter VSC1 are identical, a but because shared current source converter (csc), simultaneously in order to improve the speed of commutation, can make the switch motion of leading-bridge identical, thereby make them when commutation, the auxiliary electromotive force that all provides is realized zero-current switching, and by changing the relative displacement of leading-bridge and lagging leg, controls the discharge power of each voltage source converter.
Fig. 4 is the electrical schematic diagram of embodiments of the invention 1.The present invention is by current unit U
I, transformer unit U
T, with voltage cell U
VThree parts are formed.Transformer unit U
TIndependently transformer TR1, TR2 are in series to be two.Voltage cell U
VBe two independently voltage source converter VSC1, VSC2.The first voltage source converter VSC1 is composed in parallel by two brachium pontis, pentasyllabic quatrain edge gate pole bipolar transistor IGBT T5 and four-line poem with seven characters to a line edge gate pole bipolar transistor IGBT T7 constitute one of them brachium pontis, and the 6th insulation gate pole bipolar transistor IGBT T6 and the 8th insulation gate pole bipolar transistor IGBT T8 constitute wherein another one brachium pontis.The two ends of described two brachium pontis constitute the dc output end of the first voltage source converter VSC1, and in parallel with the first capacitor C1, the mid point of described two brachium pontis constitutes the ac output end of the first voltage source converter VSC1, link to each other with the two ends of the first transformer TR1.The first capacitor C1 of the first voltage source converter VSC1 dc output end parallel connection be connected in parallel by the 9th switch S 9 and the first DC power supply DC1, the tenth switch S 10 and the first load LOAD1 branch road of forming that is in series respectively.The structure of the second voltage source converter VSC2 and the first voltage source converter VSC1 are identical; Current unit U
IBe a current source converter (csc) CSC, it also is made of two brachium pontis, the first insulation gate pole bipolar transistor IGBT T1, the first diode D1, the 3rd insulation gate pole bipolar transistor IGBT T3 and the 3rd diode D3 constitute one of them brachium pontis of current source converter (csc) CSC, and the second insulation gate pole bipolar transistor IGBT T2, the second diode D2, the 4th insulation gate pole bipolar transistor IGBT T4 and the 4th diode D4 constitute the another one brachium pontis of current source converter (csc) CSC.The mid point of described two pairs of brachium pontis constitutes the ac output end of current source converter (csc) CSC, and the two ends of described two brachium pontis constitute the dc output end of current source converter (csc) CSC.The mid point of current source converter (csc) CSC, promptly the ac output end of current source converter (csc) CSC links to each other with series transformer TR1, TR2 two ends.The dc output end of current source converter (csc) CSC is in parallel with superconducting magnet L.Insulation gate pole bipolar transistor IGBT T1, T2, T3, T4, T5, T6, T7, T8, T9, T10, T11 and T12 can also be gate level turn-off thyristor GTO, field of electric force effect transistor MOSFET or other active electric power electronic device or superconducting switch, transformer TR1 and TR2 can be conventional transformer or superconducting transformer, and switch S 13, S14, S15 and S16 can be solid-state switch or electric switch.
Fig. 5 is example 1 a charging control mode schematic diagram of the present invention, and the action logic relation of switching device is described with regard to this schematic diagram below.The action logic relation of switching device is as follows: switch S 13 and S15 closure, when switch S 14 and S16 opened, L charged to magnet.Insulation gate pole bipolar transistor IGBT T1, T2, T3 and T4 are permanent closed when charging, carry out rectification by diode D1, D2, D3 and D4.Insulation gate pole bipolar transistor IGBT T5 and T7 differ 180 °, a bit of dead band that is separated by, centre.Insulation gate pole bipolar transistor IGBT T8 and T5 also differ 180 °, a bit of dead band that is separated by, centre.Insulation gate pole bipolar transistor IGBT T5 and T7 are leading-bridge, and insulation gate pole bipolar transistor IGBT T8 and T6 are lagging leg.For the first voltage source converter VSC1, if insulation gate pole bipolar transistor IGBT T5 and T8 closure, insulation gate pole bipolar transistor IGBT T6 and T7 open, the former limit winding of the first transformer TR1 is output as the voltage of the first capacitor C1, be positive voltage, the two ends of the first transformer TR1 secondary be output as after the transformer transformation on the occasion of voltage, voltage direction is determined by end of the same name, size is voltage/transformer voltage ratio of the first capacitor C1, gives magnet L charging.After charging a period of time, if insulation gate pole bipolar transistor IGBT T5 opens, insulation gate pole bipolar transistor IGBT T7 closure, the state of insulation gate pole bipolar transistor IGBT T6 and T8 is constant, then the first transformer TR1 primary current is by the inverse parallel diode continuousing flow of insulation gate pole bipolar transistor IGBT T8 and T7, the output voltage of the former limit winding of the first transformer TR1 is zero, the also vanishing of the voltage of secondary winding, and superconducting magnet is neither charged and is not also discharged.The control mode of the second voltage source converter VSC2 and the first voltage source converter VSC1 are identical, and can independently control.It more than is the action upper half of insulation gate pole bipolar transistor IGBT T5, T6, T7, T8, T9, T10, T11 and T12; Connect the sequential of half cycle, open insulation gate pole bipolar transistor IGBT T8, closed insulation gate pole bipolar transistor IGBT T6, gate pole bipolar transistor IGBT T6 and T7 closure insulate this moment, insulation gate pole bipolar transistor IGBT T5 and T8 open, the two ends of the first transformer TR1 secondary are output as the negative value voltage after the transformer transformation, voltage direction is determined by end of the same name, size is voltage/transformer voltage ratio of the first capacitor C1, the magnet both end voltage is opposite with the voltage direction at the first transformer TR1 secondary two ends, and its value of equal and opposite in direction still is positive.Give magnet L charging.After charging a period of time, if insulation gate pole bipolar transistor IGBT T7 opens, the T5 closure, the state of insulation gate pole bipolar transistor IGBT T6 and T8 is constant, then the transformer primary current is by the inverse parallel diode continuousing flow of insulation gate pole bipolar transistor IGBT T6 and T5, the output voltage of the former limit winding of the first transformer TR1 is zero, the also vanishing of the voltage of secondary winding, and superconducting magnet is neither charged and is not also discharged.The control mode of the second voltage source converter VSC2 and the first voltage source converter VSC 1 are identical, and can independently control.
Fig. 6 is example 1 a discharge control mode schematic diagram of the present invention, and the action logic relation of switching device is described with regard to this schematic diagram below.The action logic relation of switching device is as follows: switch S 14 and S16 closure, when switch S 13 and S15 opened, L discharged to magnet.If the electric current I direction of magnet as shown in Figure 3, for the first voltage source converter VSC1, if insulation gate pole bipolar transistor IGBT T5 and T8 closure, insulation gate pole bipolar transistor IGBT T6 and T7 open, the former limit of the first transformer TR1 is output as the voltage of the first capacitor C1, be positive voltage, gate pole bipolar transistor IGBT T1 and T4 closure insulate this moment, insulation gate pole bipolar transistor IGBT T2 and T3 open, the first transformer TR1 secondary be output as after the transformer transformation (voltage direction is determined by end of the same name on the occasion of voltage, size is voltage/transformer voltage ratio of the first capacitor C1), that is to say magnet L both end voltage, it is opposite with the electric current I direction of magnet, magnet L discharge.After discharge a period of time, open insulation gate pole bipolar transistor IGBT T2 and T3, because the first transformer TR1 secondary is output as positive voltage, this voltage increases the electric current that flows through insulation gate pole bipolar transistor IGBT T2 and T3, the electric current of insulation gate pole bipolar transistor IGBT T1 and T4 reduces, after the electric current of insulation gate pole bipolar transistor IGBT T1 and T4 reduces to zero, thereby open insulation gate pole bipolar transistor IGBT T1 and T4 and realized zero-current switching, have no progeny and open insulation gate pole bipolar transistor IGBT T5 in the pass, closed insulation gate pole bipolar transistor IGBT T7, the transformer primary current is by the inverse parallel diode continuousing flow of insulation gate pole bipolar transistor IGBT T8 and T7, the output voltage of the former limit winding of the first transformer TR1 is zero, the also vanishing of the voltage of secondary winding, superconducting magnet L neither charges and does not also discharge.The control mode of the second voltage source converter VSC2 and the first voltage source converter VSC1 are identical, can be different but it should be noted that the effective times of its discharge, in the moment of electric current commutation, the moment that insulation gate pole bipolar transistor IGBT T5 and T9 open must equate substantially, helps accelerating the speed of commutation like this and guarantees finishing smoothly of zero current commutation.It more than is the upper half of the action of insulation gate pole bipolar transistor IGBT T5, T6, T7, T8, T9, T10, T11 and T12; Connect the sequential of half cycle, after afterflow a period of time, closed insulation gate pole bipolar transistor IGBT T6 opens insulation gate pole bipolar transistor IGBT T8, and the former limit of the first transformer TR1 is output as the reverse voltage of the first capacitor C1, be negative voltage, the voltage direction of the first transformer TR1 secondary is determined that by end of the same name size is voltage/transformer voltage ratio of the first capacitor C1, and voltage direction is opposite with the direction of end decision of the same name, also the electric current I direction with magnet L is opposite, magnet L discharge.After this, open insulation gate pole bipolar transistor IGBT T1 and T4, the negative value voltage of the two ends output of the first transformer TR1 secondary increases the electric current that flows through insulation gate pole bipolar transistor IGBT T1 and T4, the electric current of insulation gate pole bipolar transistor IGBT T2 and T3 reduces, when the electric current of insulation gate pole bipolar transistor IGBT T2 and T3 reduces to zero fully, turn-off insulation gate pole bipolar transistor IGBT T2 and T3, thereby realized the shutoff of zero current, have no progeny and open insulation gate pole bipolar transistor IGBT T7 in the pass, closed insulation gate pole bipolar transistor IGBT T5, the transformer primary current is by the inverse parallel diode continuousing flow of insulation gate pole bipolar transistor IGBT T6 and T5, the output voltage of the former limit winding of the first transformer TR1 is zero, the also vanishing of the voltage of secondary winding, superconducting magnet L neither charges and does not also discharge.The control mode of the second voltage source converter VSC2 and the first voltage source converter VSC1 are identical, can be different but it should be noted that the effective times of its discharge, in the moment of electric current commutation, the moment that insulation gate pole bipolar transistor IGBT T7 and T11 open must equate substantially, helps accelerating the speed of commutation like this and guarantees finishing smoothly of zero current commutation.It more than is the lower half of the action of insulation gate pole bipolar transistor IGBT T5, T6, T7, T8, T9, T10, T11 and T12.
Fig. 7 is embodiments of the invention 2.The present invention is by current unit U
I, transformer unit U
T, with voltage cell U
VThree parts are formed.Transformer unit U
TIndependently transformer TR1 and TR2 are in series to be two.Voltage cell U
VBe two independently voltage source converter VSC1 and VSC2.Current source converter (csc) CSC is composed in parallel by two brachium pontis, and the first thyristor G1 and the 3rd thyristor G3 constitute one of them brachium pontis of current source converter (csc) CSC, and the second thyristor G2 and the 4th thyristor G4 constitute current source converter (csc) CSC another one brachium pontis.The two ends of described two brachium pontis constitute current source converter (csc) CSC dc output end, and L links to each other with superconducting magnet; The mid point of described two brachium pontis constitutes current source converter (csc) CSC ac output end, and the transformer TR1 that connects mutually with secondary and two ports of TR2 link to each other.The first voltage source converter VSC1 is also composed in parallel by two brachium pontis, pentasyllabic quatrain edge gate pole bipolar transistor IGBT T5 and four-line poem with seven characters to a line edge gate pole bipolar transistor IGBT T7 constitute first one of them brachium pontis of voltage source converter VSC1, and the 6th insulation gate pole bipolar transistor IGBT T6 and the 8th insulation gate pole bipolar transistor IGBT T8 constitute the first voltage source converter VSC1 another one brachium pontis.The two ends of described two brachium pontis constitute the dc output end of the first voltage source converter VSC1, link to each other with the first capacitor C1, and the mid point of described two brachium pontis constitutes the ac output end of the first voltage source converter VSC1, link to each other with the two ends of the first transformer TR1.The first capacitor C1 of the first voltage source converter VSC1 dc output end parallel connection be connected in parallel by the 9th switch S 9 and the first DC power supply DC1, the tenth switch S 10 and the first load LOAD1 branch road of forming that is in series respectively.Wherein the first DC power supply DC1 is the controlled rectification bridge, and the structure of the second voltage source converter VSC 2 and the first voltage source converter VSC 1 are identical.Insulation gate pole bipolar transistor IGBT T5, T6, T7, T8, T9, T10, T11 and T12 can also be gate level turn-off thyristor GTO, field of electric force effect transistor MOSFET or other active electric power electronic device or superconducting switch, transformer TR1, TR2 can be conventional transformer or superconducting transformer, and switch S 13, S14, S15 and S16 can be solid-state switch or electric switch.
Fig. 8 is example 2 charging control mode schematic diagrams of the present invention, its schematic diagram and Fig. 4 are basic identical, different is: at upper half, before insulation gate pole bipolar transistor IGBT T5 and T8, insulation gate pole bipolar transistor IGBT T9 and the T12 while closure, must give thyristor G2 and G3 trigger impulse, and after insulation gate pole bipolar transistor IGBT T5 and T8 closure, keep a period of time, to guarantee the conducting of thyristor G2 and G3 energy; At lower half, before insulation gate pole bipolar transistor IGBT T6 and T7, insulation gate pole bipolar transistor IGBT T10 and the T11 while closure, must give thyristor G1 and G4 trigger impulse, and after insulation gate pole bipolar transistor IGBT T5 and T8 closure, keep a period of time, can conducting to guarantee thyristor G1 and G4.
Fig. 9 is example 2 discharge control mode schematic diagrams of the present invention, its principle and Fig. 5 are basic identical, different is: at upper half, before insulation gate pole bipolar transistor IGBT T5 and T9 shutoff, must give thyristor G2 and the enough wide trigger impulse of G3, with assurance thyristor G2 and G3 conducting, and thyristor G1 and G4 are turn-offed; At lower half, before insulation gate pole bipolar transistor IGBT T7 and T11 shutoff, must give thyristor G1 and the enough wide trigger impulse of G4, with assurance thyristor G1 and G4 conducting, and thyristor G2 and G3 are turn-offed.
Claims (1)
1, a kind of asymmetric formula current regulator is by voltage cell (U
V), transformer unit (U
T) and current unit (U
I) three parts composition; Transformer unit (U
T) by a plurality of transformers (TR1, TR2 ... TRn) the secondary formation that is cascaded, the quantity of transformer equals the quantity of voltage source converter; Current unit (U
I) form by current source converter (csc) (CSC); Voltage cell (U
V) by voltage source converter (VSC1 ... VSCn) form; Voltage cell (U
V) and transformer unit (U
T) a side link to each other current unit (U
I) and transformer unit (U
T) opposite side link to each other; Current source converter (csc) (CSC) is composed in parallel by two brachium pontis, first switch (S1) and the 3rd switch (S3) constitute a brachium pontis of current source converter (csc) (CSC), second switch (S2) and the 4th switch (S4) constitute another brachium pontis of current source converter (csc) (CSC), the two ends of described two brachium pontis constitute the dc output end of current source converter (csc) (CSC), (L) links to each other with superconducting magnet, the mid point of described two brachium pontis constitutes the ac output end of current source converter (csc) (CSC), transformer (TR1, TR2 ... TRn) secondary is connected mutually, first transformer (TR1), two ports that n transformer (TRn) is not connected mutually link to each other with the ac output end of current source converter (csc) (CSC) respectively; First voltage source converter (VSC1) is also composed in parallel by two brachium pontis, the 5th switch (S5) and minion are closed the brachium pontis that (S7) constitutes first voltage source converter (VSC1), the 6th switch (S6) and octavo are closed the another one brachium pontis that (S8) constitutes first voltage source converter (VSC1), the two ends of described two brachium pontis constitute the dc output end of first voltage source converter (VSC1), (C1) links to each other with first capacitor, the mid point of described two brachium pontis constitutes the ac output end of first voltage source converter (VSC1), links to each other with the two ends of first transformer (TR1); First capacitor (C1) of first voltage source converter (VSC1) dc output end parallel connection be connected in parallel by the 9th switch (S9) and first DC power supply (DC1), the tenth switch (S10) and first load (LOAD1) branch road of forming that is in series respectively; Other transformer (TR2 ... TRn), all the other n-1 of second voltage source converter to the n voltage source converter voltage source converter (VSC2 ... VSCn) structure is identical with the structure and the connected mode of described first voltage source converter (VSC1) with connected mode, n is the integer more than or equal to 2, it is characterized in that voltage cell (U
V) the employing phase-shift control mode, make the impulse phase complementation of underarm on the bridge of voltage source converter, and the pulse sequence of bridge diagonal arm homophase not, leading or the lag time of the bridge diagonal arm pulse by regulating described voltage source converter, change the pulsewidth of described asymmetric formula current regulator output voltage; Current unit (U
I) by voltage cell (U
V) commutation voltage that provides carries out commutation, commutation voltage is by two pairs of switches of voltage source converter: the 5th switch (S5) and octavo are closed (S8) conducting simultaneously, and the 6th switch (S6) and minion are closed (S7) conducting simultaneously generation; In the moment of the switch commutation of described two brachium pontis of current source converter (csc), give earlier the switch triggering signal that will open brachium pontis: when commutation voltage is that first switch (S1) and the 4th switch (S4) triggering signal are given in timing, when commutation voltage when negative to second switch (S2) and the 3rd switch (S3) triggering signal; Control voltage source converter then, make it on the former limit of transformer, to produce commutation voltage, after being folded to secondary, when commutation voltage is timing, electric current flows through the second switch (S2) and the 3rd switch (S3) that will turn-off, when commutation voltage when negative, electric current flows through first switch (S1) and the 4th switch (S4) that will turn-off, owing to, flow through this switching current minimizing thereby make with the current opposite in direction that flows through the switch that will turn-off; Since with flow through the switch that will open: first switch (S1) and the 4th switch (S4), or second switch (S2) is identical with the sense of current of the 3rd switch (S3), flow through this switching current increase thereby make, by the time flow through the described switch that will turn-off: second switch (S2) and the 3rd switch (S3), or after the electric current of first switch (S1) and the 4th switch (S4) reduces to zero, turn-off the described switch that will turn-off again: second switch (S2) and the 3rd switch (S3), or first switch (S1) and the 4th switch (S4).
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|---|---|---|---|
| CNB2005100118324A CN100571002C (en) | 2005-06-01 | 2005-06-01 | A kind of asymmetric formula current regulator |
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|---|---|---|---|
| CNB2005100118324A CN100571002C (en) | 2005-06-01 | 2005-06-01 | A kind of asymmetric formula current regulator |
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| CN100571002C true CN100571002C (en) | 2009-12-16 |
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| CN100571003C (en) * | 2005-06-01 | 2009-12-16 | 中国科学院电工研究所 | A kind of asymmetric formula current regulator and ambipolar control method thereof |
| US9270189B2 (en) * | 2012-05-18 | 2016-02-23 | General Electric Company | Power converter and method |
| JP6504832B2 (en) | 2014-01-28 | 2019-04-24 | ゼネラル・エレクトリック・カンパニイ | Integrated mounting and cooling devices, electronic devices and vehicles |
| US10073512B2 (en) | 2014-11-19 | 2018-09-11 | General Electric Company | System and method for full range control of dual active bridge |
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| US5159261A (en) * | 1989-07-25 | 1992-10-27 | Superconductivity, Inc. | Superconducting energy stabilizer with charging and discharging DC-DC converters |
| US5965959A (en) * | 1996-07-02 | 1999-10-12 | American Superconductor Corporation | Superconducting magnets and power supplies for superconducting devices |
| CN1567689A (en) * | 2003-06-24 | 2005-01-19 | 中国科学院电工研究所 | A current regulator for charging and discharging of superconducting magnet |
| CN1874127A (en) * | 2005-06-01 | 2006-12-06 | 中国科学院电工研究所 | Asymmetry type curent regulator, and ambipolar control method |
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2005
- 2005-06-01 CN CNB2005100118324A patent/CN100571002C/en not_active Expired - Fee Related
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| US5159261A (en) * | 1989-07-25 | 1992-10-27 | Superconductivity, Inc. | Superconducting energy stabilizer with charging and discharging DC-DC converters |
| US5965959A (en) * | 1996-07-02 | 1999-10-12 | American Superconductor Corporation | Superconducting magnets and power supplies for superconducting devices |
| CN1567689A (en) * | 2003-06-24 | 2005-01-19 | 中国科学院电工研究所 | A current regulator for charging and discharging of superconducting magnet |
| CN1874127A (en) * | 2005-06-01 | 2006-12-06 | 中国科学院电工研究所 | Asymmetry type curent regulator, and ambipolar control method |
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