CN100433494C - Vector control method for rectifier of UPS - Google Patents
Vector control method for rectifier of UPS Download PDFInfo
- Publication number
- CN100433494C CN100433494C CNB2003101166716A CN200310116671A CN100433494C CN 100433494 C CN100433494 C CN 100433494C CN B2003101166716 A CNB2003101166716 A CN B2003101166716A CN 200310116671 A CN200310116671 A CN 200310116671A CN 100433494 C CN100433494 C CN 100433494C
- Authority
- CN
- China
- Prior art keywords
- circuit
- pfc
- rectification
- current
- rectifier
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Lifetime
Links
- 238000000034 method Methods 0.000 title claims abstract description 16
- 238000006243 chemical reaction Methods 0.000 claims abstract description 11
- 230000009466 transformation Effects 0.000 claims description 12
- 230000003068 static effect Effects 0.000 claims description 9
- 230000001105 regulatory effect Effects 0.000 claims description 6
- 238000005070 sampling Methods 0.000 claims description 6
- 230000009897 systematic effect Effects 0.000 claims description 3
- 230000003321 amplification Effects 0.000 abstract 1
- 238000003199 nucleic acid amplification method Methods 0.000 abstract 1
- 239000003990 capacitor Substances 0.000 description 12
- 102100029469 WD repeat and HMG-box DNA-binding protein 1 Human genes 0.000 description 2
- 101710097421 WD repeat and HMG-box DNA-binding protein 1 Proteins 0.000 description 2
- 238000011217 control strategy Methods 0.000 description 2
- 230000000875 corresponding effect Effects 0.000 description 2
- 238000010586 diagram Methods 0.000 description 2
- 230000000694 effects Effects 0.000 description 2
- 238000001914 filtration Methods 0.000 description 2
- 238000009413 insulation Methods 0.000 description 2
- 230000001276 controlling effect Effects 0.000 description 1
- 230000002596 correlated effect Effects 0.000 description 1
- 230000008676 import Effects 0.000 description 1
Images
Landscapes
- Rectifiers (AREA)
Abstract
The present invention discloses a vector control method for a rectifier in an uninterrupted power supply. The rectifier comprises a VIENNA-like circuit. In the method, the output of a voltage loop PI adjustor using the DC bus voltage of the rectifier as a target is used as a specified value of a current loop; an active component and a reactive component of a space current vector can be obtained according to the three-phase input current of the input side of the rectifier through 3/2 conversion and still / rotation conversion; the pulse width modulation switching value of the rectifier in the three-phase uninterrupted power supply is obtained by PI regulation calculation and conversion according to the difference of the specified value of an active and reactive current adjustor, and the active component and the reactive component of the space current vector; the three-phase input voltage of the input side of the rectifier is distinguished to be positive or negative, and generates the IGBT pulse width quantity of each path of power factors together with the pulse width modulation (PWM) switching value of the three-phase uninterrupted power supply so that the vector control of the VIENNA-like circuit is realized by the IGBT pulse width quantity through power amplification.
Description
Technical field
(Uninterruptible Power Supply, UPS) technology relate in particular to the vector control method of rectifier in the uninterrupted power supply to the present invention relates to uninterrupted power supply.
Background technology
Along with the aggravation of market competition, the price cost squeeze of uninterrupted power supply product is increasing.Use the main circuit topology of Vienna-class (VIENNA-like) circuit as the UPS rectifier, can save battery feed circuit whole power factor corrector (Power Factor Correction, PFC) circuit, thereby reduced the complete machine cost.
The circuit topology of VIENNA-like as shown in Figure 1.Among the figure, S1-1～6-1 is a main road rectification thyristor (SCR), is connected with three phase mains by filter circuit, is used for the main road rectification; S1-2～6-2 is powered battery SCR, is used for powered battery; Q1-1, Q1-2, Q2-1, Q2-2, Q3-1, Q3-2 are the insulation gate pole bipolar transistor (IGBT) of main road and battery sharing pfc circuit; L1～L6 is the inductance of main road and battery sharing pfc circuit.
Present discrete ratio-integration (the Proportionalplus Integral that is controlled to be 6 road PFC to the VIENNA-like circuit, PI) control, because the circuit symmetrical characteristic that the VIENNA-like circuit is good, therefore, control to entire circuit can equivalence be the control of two half-bridges, thereby makes control structure simplify; But also there are many drawbacks in this control method, and is undistinct as the physical significance of regulated quantity in the control, thereby relatively more responsive for the variation of input filtering parameter; Simultaneously, if the distributed constant of 6 road PFC slightly different (as the difference of track lengths), but and Control Parameter is identical, then can cause the characteristic variation of this VIENNA-like circuit.
Summary of the invention
The object of the present invention is to provide the vector control method of rectifier in a kind of uninterrupted power supply, with the performance of further raising UPS rectifier.
Realize technical scheme of the present invention:
The vector control method of rectifier in a kind of uninterrupted power supply, described uninterrupted power supply comprises with Vienna-class circuit being rectifier, IGBT drive circuit, testing circuit and the digital signal processor of rectification circuit, wherein, three phase mains is connected with the input side of rectifier, testing circuit is connected between rectifier and the digital signal processor, and the IGBT drive circuit is connected between rectifier and the digital signal processor;
Described method comprises step:
The DC bus-bar voltage of A, testing circuit sampling rectifier outlet side, and utilize digital signal processor that described DC bus-bar voltage is carried out PI and regulate computing, the set-point of active current ring obtained;
The three-phase input current of B, testing circuit sampling input side rectifier, and described three-phase input current carried out 3/2 conversion (PARK conversion) and static/rotation transformation (CLARK conversion), obtain the real component and the idle component of space current vector;
C, described real component is carried out PI as the set-point of the feedback quantity of active current pi regulator and described active current ring regulate computing, obtain active current and regulate output;
D, idle component is carried out PI as the set-point of the feedback quantity of reactive current pi regulator and reactive current ring regulate computing, obtain reactive current and regulate output;
E, described active current is regulated output and reactive current regulate output and carry out 3/2 inverse transformation and static/rotation inverse transformation, obtain pulse-width modulation (Pulse Width Modulation, the PWM) switching value of three phase mains;
The three-phase input voltage of F, the input side rectifier that obtains according to sampling is differentiated the positive and negative of input voltage, and with the common IGBT pulsewidth amount that produces each each the road power factor corrector of road power factor corrector in the described VIENNA-like circuit of the pwm switch amount of described three phase mains, the power drive signal that is produced by this IGBT pulsewidth amount control IGBT drive circuit is realized the vector control to the VIENNA-like circuit.
Wherein:
Also introduce the feedforward component of DC bus-bar voltage and the decoupling zero component of reactive current and the PI adjusting acting in conjunction as a result of described active current ring pi regulator among the step C and obtain active current adjusting output.
Also introduce the decoupling zero component of active current and the PI adjusting acting in conjunction as a result of described reactive current ring pi regulator among the step D and obtain reactive current adjusting output.
According to the systematic function requirement, carry out corresponding reactive power compensation or the set-point of reactive current ring is made as 0 by the set-point of regulating the reactive current ring.
The present invention is by the VIENNA-like circuit is carried out vector control, and is clear to the physical significance of UPS rectifier control, can control by real component and idle component, helps to improve the performance of UPS rectifier; Simultaneously, in conjunction with the common characteristic of vector control and VIENNA-like circuit, by vector control the overall performance of UPS rectifier is significantly improved, adopt the VIENNA-like circuit can save UPS complete machine cost, therefore, adopt the present invention can make the UPS complete machine have very high cost performance.
Description of drawings
Fig. 1 is the VIENNA-like circuit of UPS;
Fig. 2 is the theory diagram of UPS;
Fig. 3 is the vector control block diagram based on the VIENNA-like circuit;
Fig. 4 is a process chart of the present invention.
Embodiment
The circuit topology of VIENNA-like circuit as shown in Figure 1, comprise the internal cell power supply circuits, be connected the rectification circuit between internal cell power supply circuits and the three phase mains, described rectification circuit comprises first rectification circuit, second rectification circuit and the 3rd rectification circuit, wherein at three phase mains wherein first rectification circuit of a phase comprise: first inductance L 19, first capacitor C 7, the first current measuring element H1, the first rectification thyristor S1-1, the 4th rectification thyristor S4-1 and the pfc circuit of forming by positive half cycle circuit of PFC and PFC negative half period circuit
Wherein, wherein mutually an output of one end of first inductance L 19 and three phase mains connects, the other end of first inductance L 19 is connected with first capacitor C 7, wherein first inductance L 19 and first capacitor C 7 constitute filter circuit, the end that first inductance L 19 is connected with first capacitor C 7 is told first branch and second branch by the first current measuring element H1, first branch is connected with the anode of the first rectification thyristor S1-1, the negative electrode of the first rectification thyristor S1-1 is connected with the positive half cycle circuit of PFC, the positive half cycle circuit of described PFC comprises: a PFC inductance L 1, the one PFC diode D1, the one IGBT Q1-1 and the first output capacitance C11, wherein an end of a PFC inductance L 1 is connected with the negative electrode of the first rectification thyristor S1-1, the other end of the one PFC inductance L 1 is connected with the anode of a PFC diode D1 and the collector electrode of an IGBT Q1-1 respectively, the negative electrode of the one PFC diode D1 is connected with the end of the first output capacitance C11, and the other end of the first output capacitance C11 is connected with the emitter of an IGBT Q1-1 by the first input center line N; Wherein second branch is connected with the negative electrode of the 4th rectification thyristor S4-1, the anode of the 4th rectification thyristor S4-1 is connected with PFC negative half period circuit, described PFC negative half period circuit comprises: the 2nd PFC inductance L 2, the 2nd PFC diode D2, the 2nd IGBT Q1-2 and the second output capacitance C12, wherein an end of the 2nd PFC inductance L 2 is connected with the anode of the 4th rectification thyristor S4-1, the other end of the 2nd PFC inductance L 2 is connected with the negative electrode of the 2nd PFC diode D2 and the emitter of the 2nd IGBT Q1-2 respectively, the anode of the 2nd PFC diode D2 is connected with the end of the second output capacitance C12, and the other end of the second output capacitance C12 is connected with the collector electrode of the 2nd IGBT Q1-2 by the first input center line N; The collector electrode of the 2nd IGBT Q1-2 of the emitter of the one IGBT Q1-1 of the positive half cycle circuit of described PFC and PFC negative half period circuit connects and composes pfc circuit; The other end that first capacitor C 7 of wherein said filter circuit is connected with first inductance L 19 relatively is connected with the first input center line N;
The internal cell power supply circuits comprise: the internal cell that is composed in series by first Battery pack and second Battery pack, second capacitor C 21, first resistance R 1 and the 3rd capacitor C 22 and second resistance R 2, wherein, second capacitor C 21 and first resistance R 1 are connected in parallel, wherein a Bing Lian end is connected with internal cell is anodal, the other end is connected with the second input center line M, and the 3rd capacitor C 22 and second resistance R 2 be connected in parallel, wherein a Bing Lian end is connected with the internal cell negative pole, the other end is connected with the second input center line M, the end of the described second input center line M is connected first Battery pack of internal cell and the serial connection point X of second Battery pack, and the other end is connected with the first input center line N;
The internal cell positive pole is drawn out to the second current measuring element H7, and the second current measuring element H7 is connected with the anode of the first power supply thyristor S1-2, and the negative electrode of the first power supply thyristor S1-2 is connected with the negative electrode of the described first rectification thyristor S1-1; The negative pole of internal cell is drawn out to the 3rd current measuring element H8, and the 3rd current measuring element H8 is connected with the negative electrode of the 4th power supply thyristor S4-2, and the anode of the 4th power supply thyristor S4-2 is connected with the anode of the 4th rectification thyristor S4-1;
In described Vienna-class circuit, it is identical to be connected second rectification circuit between all the other two phase output terminals of internal cell power supply circuits and three phase mains and the 3rd rectification circuit and above-mentioned first rectification circuit, here repeat no more, and the shared first identical output capacitance C11 of described first rectification circuit, second rectification circuit and the 3rd rectification circuit and the second output capacitance C12;
From the above, rectification thyristor (SCR) S1-1～6-1 shown in Figure 1 is used for the main road rectification; Power supply thyristor S1-2～6-2 is used for powered battery; Q1-1, Q1-2, Q2-1, Q2-2, Q3-1, Q3-2 are the insulation gate pole bipolar transistor (IGBT) of main road and battery sharing power factor corrector (PFC) circuit; L1～L6 is the inductance of main road and battery sharing pfc circuit, because of inductance value is identical, is made as L; Inductance L 19, L20, L21 and capacitor C 7, C8, C9 form input filter circuit; Wherein, the electric current by the PFC inductance is made as i
L, current in middle wire is made as i
0, input voltage is U
S, the internal resistance of rectifier is R, the bus capacitor both end voltage is U
d, capacitance is C; The electric current that flows through bus capacitor is i
d, and the switch function of pfc circuit IGBT is made as S
A, S
B, S
CThe basic circuit equation of this rectifier is:
According to this circuit equation, static/rotation transformation through 3/2 conversion, can get its state equation:
Wherein, i
d, i
qFor input current through the current phasor of 3/2 conversion and static/rotation transformation gained component at d axle (active current component) and q axle (reactive current component); And U
Sd, U
SqFor input voltage through the voltage vector of 3/2 conversion and static/rotation transformation gained component at d axle and q axle; According to above state equation, with the busbar voltage is the rectifier outer shroud, with the d shaft current is to encircle in the rectifier, be 1 for pursuing the rectifier power factor simultaneously, on behalf of the set-point of the q shaft current ring of idle component, Ying Jiang be made as 0, and by to the decoupling zero of this state equation, thereby drawn the vector control strategy of VIENNA-like circuit.
Consult shown in Figure 2, UPS mainly comprise VIENNA-like main circuit, IGBT drive circuit, check-out console (or claiming testing circuit) and digital signal processor (Digital Signal Processor, DSP).Pi regulator is realized by executive program by DSP.The VIENNA-like main circuit is converted to direct current with the alternating current of importing and exports by dc bus under the power drive signal controlling of IGBT drive circuit output.The dc bus of check-out console from main circuit obtains voltage (Vbus+, Vbus-) and current signal and feeds back to DSP, the pi regulator computing and the output of being correlated with by DSP are used for pulse-width signal (this pulse-width signal is specially IGBT pulsewidth amount), produce the power drive signal with this pulse-width signal control IGBT drive circuit.
Consult shown in Figure 3ly, represented the vector control strategy that DSP implements by working procedure among the figure.Below in conjunction with Fig. 2, Fig. 3 and Fig. 4 the idiographic flow of implementing vector control is described:
Step 10: by check-out console sample respectively three-phase voltage Va, Vb, Vc, three-phase current Ia, Ib, Ic and outlet side DC bus-bar voltage Vbus+, the Vbus-of input side rectifier.
Step 20:DSP carries out busbar voltage control, regulates the set-point Id that computing (being the Vd_reg among Fig. 3) draws meritorious (D axle) electric current loop through Voltage loop PI
*
Step 30: three-phase input current is carried out 3/2 conversion and static/rotation transformation, draw the real component Id and the idle amount component Iq of space current vector, and respectively as the feedback quantity of meritorious (D axle) electric current loop and idle (Q axle) electric current loop.
Step 40: with real component Id as the feedback quantity of active current pi regulator and the set-point Id of described active current ring
*Carry out PI and regulate computing (being Id_reg and-1 link among Fig. 3), obtain active current and regulate output.
In order further to improve the control effect of active current ring, can introduce the feedforward component Vd of DC bus-bar voltage and the decoupling zero component L ω * Iq and the PI adjusting acting in conjunction as a result of reactive current and obtain active current adjusting output.
Step 50: idle component Iq is carried out PI adjusting computing (being Iq_reg and-1 link among Fig. 3) as the feedback quantity of reactive current pi regulator and the set-point Iq* of reactive current ring, obtain reactive current and regulate output.
In order further to improve the control effect of reactive current ring, decoupling zero component L ω * Id and the PI adjusting acting in conjunction as a result that can introduce active current obtain reactive current adjusting output.
As it is less to import filtering parameter, and engineering design is influenced when not obvious, can be with the set-point Iq of reactive current ring
*Be made as 0, have relatively high expectations, then can not carry out the control of 0 idle component as systematic function, can be by regulating the set-point Iq of reactive current ring
*Carry out corresponding reactive power compensation.
Step 60: 3/2 inverse transformation and static/rotation inverse transformation are carried out in active current adjusting output and reactive current adjusting output, draw pulse-width modulation (PWM) switching value of A, B, C three phase mains, and above-mentioned switching value is concentrated dead area compensation at each power frequency period.
Step 70: differentiate three-phase input voltage positive and negative (UP/DOWN) with the voltage phase discriminator, and drawing the IGBT pulsewidth amount of each road PFC jointly with the PWM switching value of A, B, C three phase mains, the power drive signal that is produced by this IGBT pulsewidth amount control is realized the vector control to the VIENNA-like circuit.
Claims (4)
1, the vector control method of rectifier in a kind of uninterrupted power supply, described uninterrupted power supply comprises with Vienna-class circuit being rectifier, IGBT drive circuit, testing circuit and the digital signal processor of rectification circuit, wherein, three phase mains is connected with the input side of rectifier, testing circuit is connected between rectifier and the digital signal processor, and the IGBT drive circuit is connected between rectifier and the digital signal processor;
Described Vienna-class circuit comprises the internal cell power supply circuits, be connected the rectification circuit between internal cell power supply circuits and the three phase mains, described rectification circuit comprises first rectification circuit, second rectification circuit and the 3rd rectification circuit, wherein at three phase mains wherein first rectification circuit of a phase comprise: first inductance (L19), first electric capacity (C7), first current measuring element (H1), the first rectification thyristor (S1-1), the 4th rectification thyristor (S4-1) and the pfc circuit of forming by positive half cycle circuit of PFC and PFC negative half period circuit
Wherein, wherein mutually an output of one end of first inductance (L19) and three phase mains connects, the other end of first inductance (L19) is connected with first electric capacity (C7), wherein first inductance (L19) and first electric capacity (C7) constitute filter circuit, the end that first inductance (L19) is connected with first electric capacity (C7) is told first branch and second branch by first current measuring element (H1), first branch is connected with the anode of the first rectification thyristor (S1-1), the negative electrode of the first rectification thyristor (S1-1) is connected with the positive half cycle circuit of PFC, the positive half cycle circuit of described PFC comprises: a PFC inductance (L1), the one PFC diode (D1), the one IGBT (Q1-1) and first output capacitance (C11), wherein an end of a PFC inductance (L1) is connected with the negative electrode of the first rectification thyristor (S1-1), the other end of the one PFC inductance (L1) is connected with the anode of a PFC diode (D1) and the collector electrode of an IGBT (Q1-1) respectively, the negative electrode of the one PFC diode (D1) is connected with an end of first output capacitance (C11), and the other end of first output capacitance (C11) is connected with the emitter of an IGBT (Q1-1) by the first input center line (N); Wherein second branch is connected with the negative electrode of the 4th rectification thyristor (S4-1), the anode of the 4th rectification thyristor (S4-1) is connected with PFC negative half period circuit, described PFC negative half period circuit comprises: the 2nd PFC inductance (L2), the 2nd PFC diode (D2), the 2nd IGBT (Q1-2) and second output capacitance (C12), wherein an end of the 2nd PFC inductance (L2) is connected with the anode of the 4th rectification thyristor (S4-1), the other end of the 2nd PFC inductance (L2) is connected with the negative electrode of the 2nd PFC diode (D2) and the emitter of the 2nd IGBT (Q1-2) respectively, the anode of the 2nd PFC diode (D2) is connected with an end of second output capacitance (C12), and the other end of second output capacitance (C12) is connected with the collector electrode of the 2nd IGBT (Q1-2) by the first input center line (N); The collector electrode of the emitter of the one IGBT (Q1-1) of the positive half cycle circuit of described PFC and the 2nd IGBT (Q1-2) of PFC negative half period circuit connects and composes pfc circuit; The other end that first electric capacity (C7) of wherein said filter circuit is connected with first inductance (L19) relatively is connected with the first input center line (N);
The internal cell power supply circuits comprise: the internal cell that is composed in series by first Battery pack and second Battery pack, second electric capacity (C21), first resistance (R1) and the 3rd electric capacity (C22) and second resistance (R2), wherein, second electric capacity (C21) and first resistance (R1) are connected in parallel, wherein a Bing Lian end is connected with internal cell is anodal, the other end is connected with the second input center line (M), and the 3rd electric capacity (C22) and second resistance (R2) be connected in parallel, wherein a Bing Lian end is connected with the internal cell negative pole, the other end is connected with the second input center line (M), one end of the described second input center line (M) is connected first Battery pack of internal cell and the serial connection point (X) of second Battery pack, and the other end is connected with the first input center line (N);
The internal cell positive pole is drawn out to second current measuring element (H7), second current measuring element (H7) is connected with the anode of the first power supply thyristor (S1-2), and the negative electrode of the first power supply thyristor (S1-2) is connected with the negative electrode of the described first rectification thyristor (S1-1); The negative pole of internal cell is drawn out to the 3rd current measuring element (H8), the 3rd current measuring element (H8) is connected with the negative electrode of the 4th power supply thyristor (S4-2), and the anode of the 4th power supply thyristor (S4-2) is connected with the anode of the 4th rectification thyristor (S4-1);
In described Vienna-class circuit, it is identical to be connected second rectification circuit between all the other two phase output terminals of internal cell power supply circuits and three phase mains and the 3rd rectification circuit and above-mentioned first rectification circuit, and shared identical first output capacitance (C11) of described first rectification circuit, second rectification circuit and the 3rd rectification circuit and second output capacitance (C12);
It is characterized in that described method comprises step:
The DC bus-bar voltage of A, testing circuit sampling rectifier outlet side, and utilize digital signal processor that described DC bus-bar voltage is carried out ratio-integration and regulate computing, the set-point of active current ring obtained;
The three-phase input current of B, testing circuit sampling input side rectifier, and described three-phase input current carried out 3/2 conversion and static/rotation transformation, obtain the real component and the idle component of space current vector;
C, described real component is carried out ratio-integration as the set-point of the feedback quantity of the active current proportional-integral controller of digital signal processor and described active current ring regulate computing, obtain active current and regulate output;
D, described idle component is carried out ratio-integration as the set-point of the feedback quantity of the reactive current proportional-integral controller of digital signal processor and reactive current ring regulate computing, obtain reactive current and regulate output;
E, described active current is regulated output and reactive current regulate output and carry out 3/2 inverse transformation and static/rotation inverse transformation, obtain the pwm switch amount of three phase mains;
The three-phase input voltage of F, the input side rectifier that obtains according to sampling is differentiated the positive and negative of input voltage, and with the common IGBT pulsewidth amount that produces each road power factor corrector in described Vienna-class circuit of the pwm switch amount of described three phase mains, the power drive signal that is produced by this IGBT pulsewidth amount control IGBT drive circuit is realized the vector control to Vienna-class circuit.
2, the method for claim 1, it is characterized in that, also introduce the feedforward component of DC bus-bar voltage and the decoupling zero component of reactive current and ratio-integration adjusting acting in conjunction as a result of described active current proportional-integral controller among the step C and obtain active current and regulate output.
3, method as claimed in claim 1 or 2 is characterized in that, ratio-integration adjusting acting in conjunction as a result of also introducing the decoupling zero component and the described reactive current proportional-integral controller of active current among the step D obtains reactive current and regulates output.
4, the method for claim 1 is characterized in that, according to the systematic function requirement, carries out corresponding reactive power compensation or the set-point of reactive current ring is made as 0 by the set-point of regulating the reactive current ring.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNB2003101166716A CN100433494C (en) | 2003-11-26 | 2003-11-26 | Vector control method for rectifier of UPS |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNB2003101166716A CN100433494C (en) | 2003-11-26 | 2003-11-26 | Vector control method for rectifier of UPS |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN1622420A CN1622420A (en) | 2005-06-01 |
| CN100433494C true CN100433494C (en) | 2008-11-12 |
Family
ID=34760726
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CNB2003101166716A Expired - Lifetime CN100433494C (en) | 2003-11-26 | 2003-11-26 | Vector control method for rectifier of UPS |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN100433494C (en) |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP2675052A1 (en) * | 2012-04-27 | 2013-12-18 | Huawei Technologies Co., Ltd. | Circuit and control method thereof |
| CN106515503A (en) * | 2016-12-30 | 2017-03-22 | 深圳市英威腾电气股份有限公司 | Charging and discharging method for electric automobile and charger |
Families Citing this family (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US7768805B2 (en) * | 2007-03-09 | 2010-08-03 | General Electric Company | Clean input UPS with fast rectifier control and improved battery life |
| CN107785972A (en) * | 2017-09-19 | 2018-03-09 | 南京航空航天大学 | A kind of control system and control method of uninterruptible power system rectifier |
| CN107769594B (en) * | 2017-11-07 | 2019-08-13 | 西南交通大学 | A kind of optimization method of Pulse rectifier current inner loop controller |
| CN113708479A (en) * | 2021-08-30 | 2021-11-26 | 漳州科华电气技术有限公司 | PFC control method and terminal equipment |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5140514A (en) * | 1990-05-03 | 1992-08-18 | Kone Elevator Gmbh | Regulation of d.c. voltage of a pulse-width modulated rectifier using spatial vectors in a stationary coodinate system |
| JP3192058B2 (en) * | 1995-02-01 | 2001-07-23 | 株式会社日立製作所 | Control device for PWM converter |
-
2003
- 2003-11-26 CN CNB2003101166716A patent/CN100433494C/en not_active Expired - Lifetime
Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5140514A (en) * | 1990-05-03 | 1992-08-18 | Kone Elevator Gmbh | Regulation of d.c. voltage of a pulse-width modulated rectifier using spatial vectors in a stationary coodinate system |
| JP3192058B2 (en) * | 1995-02-01 | 2001-07-23 | 株式会社日立製作所 | Control device for PWM converter |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP2675052A1 (en) * | 2012-04-27 | 2013-12-18 | Huawei Technologies Co., Ltd. | Circuit and control method thereof |
| EP2675052A4 (en) * | 2012-04-27 | 2014-04-23 | Huawei Tech Co Ltd | Circuit and control method thereof |
| CN106515503A (en) * | 2016-12-30 | 2017-03-22 | 深圳市英威腾电气股份有限公司 | Charging and discharging method for electric automobile and charger |
| CN106515503B (en) * | 2016-12-30 | 2018-09-18 | 深圳市英威腾电气股份有限公司 | A kind of charging/discharging thereof and charger of electric vehicle |
Also Published As
| Publication number | Publication date |
|---|---|
| CN1622420A (en) | 2005-06-01 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN103401463B (en) | The miniature photovoltaic grid-connected inverter that dc-link capacitance reduces and control method | |
| CN107230983B (en) | Power spring application system based on power control and control method thereof | |
| Liu et al. | Modeling and SVPWM control of quasi-Z-source inverter | |
| Gow et al. | Photovoltaic converter system suitable for use in small scale stand-alone or grid connected applications | |
| CN102856916B (en) | Reactive power control method and circuit of single-phase photovoltaic inverter | |
| CN107046375B (en) | A kind of MMC circular current control method of bridge arm single-sensor | |
| CN101414788B (en) | DC constant current power supply with low ripple implemented through mixing IGBT series and parallel connections | |
| CN108616132B (en) | Model prediction direct power control method based on three vectors | |
| CN106130381B (en) | The control method of power feedforward prediction Direct Power based on Virtual shipyard orientation | |
| CN203387430U (en) | Micro photovoltaic grid connected inverter for optimization of direct current bus capacitor | |
| CN204615631U (en) | A kind of busbar voltage ripple compensation control circuit of circuit of power factor correction | |
| CN103401267A (en) | Grid-connected circuit for small-sized wind-driven generator | |
| CN103166489A (en) | Control circuit for three-phase high power factor rectifier | |
| CN107017811A (en) | Permanent magnet motor controller and method for no electrolytic capacitor motor driven systems | |
| CN205195587U (en) | Grid -connected PV converter, photovoltaic power supply system and electrical apparatus | |
| CN105337520A (en) | Photovoltaic grid-connected converter, photovoltaic power supply system and electric appliance | |
| CN106655830A (en) | Decoupling control method and system | |
| CN102545264A (en) | Method for controlling grid-connected inverter based on feed-forward decoupling of state quantity | |
| CN100433494C (en) | Vector control method for rectifier of UPS | |
| CN104883083A (en) | Active power decoupling device without additional switching element and control method therefor | |
| CN111181420A (en) | Single-phase Vienna rectifier and control method thereof | |
| Barrado et al. | Standalone self-excited induction generator with a three-phase four-wire active filter and energy storage system | |
| CN107482930A (en) | A kind of double inductance twin voltage DC output circuits | |
| Slabbert et al. | Grid connected/solar water pump for rural areas | |
| CN108809130A (en) | The modulator approach of the sources Semi-Z single-phase inverter |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant | ||
| CP03 | Change of name, title or address |
Address after: Columbo Road, Ohio, Dearborn 1050 Patentee after: Dimension Corp. Address before: Ohio, USA Patentee before: LIEBERT Corp. |
|
| CP03 | Change of name, title or address | ||
| CX01 | Expiry of patent term |
Granted publication date: 20081112 |
|
| CX01 | Expiry of patent term |