CA1090466A - Tv sync pulse separator and noise gate - Google Patents
Tv sync pulse separator and noise gateInfo
- Publication number
- CA1090466A CA1090466A CA274,298A CA274298A CA1090466A CA 1090466 A CA1090466 A CA 1090466A CA 274298 A CA274298 A CA 274298A CA 1090466 A CA1090466 A CA 1090466A
- Authority
- CA
- Canada
- Prior art keywords
- coupled
- voltage
- reference voltage
- circuit according
- source
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
- H04N5/00—Details of television systems
- H04N5/04—Synchronising
- H04N5/08—Separation of synchronising signals from picture signals
Landscapes
- Engineering & Computer Science (AREA)
- Multimedia (AREA)
- Signal Processing (AREA)
- Synchronizing For Television (AREA)
- Picture Signal Circuits (AREA)
Abstract
IMPROVED TV SYNC PULSE SEPARATOR AND NOISE GATE
Abstract Of The Disclosure A constant current source supplies a bias current through a diode chain, establishing a first voltage at a terminal coupled to the string. A DC restorer circuit, responsive to a source of composite video signals, couples an additional current through the diode chain during the sync interval. This additional current establishes a second voltage level at the terminal. The second voltage is compared with a reference voltage for producing output signals synchronized with the sync pulses.
Abstract Of The Disclosure A constant current source supplies a bias current through a diode chain, establishing a first voltage at a terminal coupled to the string. A DC restorer circuit, responsive to a source of composite video signals, couples an additional current through the diode chain during the sync interval. This additional current establishes a second voltage level at the terminal. The second voltage is compared with a reference voltage for producing output signals synchronized with the sync pulses.
Description
1~466 RCA 70,7l7 This invention relates to sync separator circuits.
Composite video signals obtained from the IF
stages of a television receiver are composed of two parts, a video portion which contains picture information to ~e coupled to the electron guns of the cathode ray tube, and a sync portion having sync pulses superimposed upon a blanking level. A sync separator circuit clips the sync pulses from the video signal portion. The sync pulses are then used to synchronize horizontal and vertical scanning with the incoming video information.
Certain television transmitting systems, such as community antenna television systems (CATV) which include amplifiers and/or remodulators, place increasing demands on the sync separator. Because such amplifier systems tend to compress the sync pulses, the sync ~ .
separator must be able to operate properly with only a -~
fraction of the normal sync pulse amplitude.
If adequate composite video amplitude is available, typical conventional sync separators can operate ~ ;
properly with 25% of the normal sync amplitude. However, with modern integrated circuits, the composite video ;~
available is often only 2-3 volts. The sync separator must be able to operate with sync pulse amplitudes of 200 2S millivolts or less. It is, therefore, desirable to provide a sync separator that can be incorporated as part ~ -of an integrated circuit and can operate with relatively low relative and absolute sync pulse amplitudes.
In accordance with a preferred emkodiment of the invention,a first circuit provides a bias current through a
Composite video signals obtained from the IF
stages of a television receiver are composed of two parts, a video portion which contains picture information to ~e coupled to the electron guns of the cathode ray tube, and a sync portion having sync pulses superimposed upon a blanking level. A sync separator circuit clips the sync pulses from the video signal portion. The sync pulses are then used to synchronize horizontal and vertical scanning with the incoming video information.
Certain television transmitting systems, such as community antenna television systems (CATV) which include amplifiers and/or remodulators, place increasing demands on the sync separator. Because such amplifier systems tend to compress the sync pulses, the sync ~ .
separator must be able to operate properly with only a -~
fraction of the normal sync pulse amplitude.
If adequate composite video amplitude is available, typical conventional sync separators can operate ~ ;
properly with 25% of the normal sync amplitude. However, with modern integrated circuits, the composite video ;~
available is often only 2-3 volts. The sync separator must be able to operate with sync pulse amplitudes of 200 2S millivolts or less. It is, therefore, desirable to provide a sync separator that can be incorporated as part ~ -of an integrated circuit and can operate with relatively low relative and absolute sync pulse amplitudes.
In accordance with a preferred emkodiment of the invention,a first circuit provides a bias current through a
- 2 -~J~
:,~
1~90466 RCA 70,717 I plurality of series coupled diodes and establishes a first voltage at a terminal coupled to the diodes. A
second circuit, responsive to a source of video signals, the video signals including synchrohizing signals, introduces to the plurality of series coupled diodes during the occurrence of the synchronizing signals a current in addition to the bias current for establishing a second voltage at the terminal. A third circuit develops an output signal when the second voltage and a reference voltage differ by a predetermined value.
FIGURE 1 lS a schematlc clrcult of an embodiment of the invention;
FIGURE 2 is a schematic circuit of another embodiment of the invention;
FIGURE 3 is a schematic circuit of still another embodiment of the invention; and FIGIJRES 4a - 4c illustrate waveforms associated with the circuits of FIGURES 1 - 3.
In FIGURE 1, AC signals comprising composite video signals 20, obtained from conventional IF stages of a television receiver, are coupled to a terminal 10 of a sync separator circuit 50. The signals are then coupled through a capacitor 21 t~ a first input terminal 30 at the base of a transistor 22. A resistor 23 couples the base of transistor 22 to a source of B+ voltage. The collector of transistor 22 is coupled to a constant current source 24. The emitter is coupled to ground through a pair of diodes 31 and 32, forming a first diode - ~ . ' ' ': :
- RCA 70,717 10~0466 1 ^hain 25 comprising diodes 31 and 32 and the base-emitter junction of transistor 22.
Capacitor 21, resistor 23 and transistor 22 form a DC restorer circuit 40 to provide a DC restoration voltage to the video sync portion 20a of the AC composite video signals 20. During the sync interval, transistor 22 ~ ~-is forward biased into saturation by the sync pulses 20a of composite video signals 20, and a DC restoration voltage equal to the difference between the DC voltage at terminal 30 and the effective DC appearing at terminal 10 during the sync period is developed across the capacitor.
The resistor 23 provides current to charge capacitor 21 during the video picture interval to replace charge removed during the sync interval.
lS When transistor 22 conducts during the sync interval, current flows through diode chain 25. A major portion of this current comprises a biasing current -originating from constant current source 24. This biasing current establishes a reference potential at 2~ terminal 30. Capacitor 21 of the DC restorer circuit 40 then provides the remaining additional current through diode chain 40. The additional current increases the voltage at terminal 30 by an incremental amount, providing a voltage level Vb at terminal 30 during the sync interval.
Coupled between the B+ voltage source and ground are a constant current source 28, a transistor 27, and a pair of diodes 33 and 34. The collector and base of transistor 27 are coupled together forming a diode structure. A second diode chain 26 comprises diodes 33 and 34 and the base-emitter junction of transistor 27.
109046~ RCA 70,7l7 1 Diode chains 2S and 26 are illustratively constructed from identical npn transistors, and for identical constant current sources 24 and 28, the voltage at a second input terminal 29 coupled to the base of transistor 27 is equal to a reference voltage Va.
Input terminals 29 and 30 are coupled to a , , , voltage comparator 37. During the picture interval, the negative-going video signals 20b reverse bias transistor 22, and the voltage at input terminal 30 of comparator 37 is lower than the voltage at input terminal 29. The . .~
voltage at an output terminal 36 is at a first output -~
voltage level. During the sync interval, because of the `
.
additional current from capacitor 21, the voltage at terminal 30 is at a value Vb which is greater than the voltage Va at terminal 29. The voltage at output terminal 36 of comparator 37 then shifts to a second output voltage level, thereby providing repetitive output signals 35 ~-~
in synchronization with the incoming sync pulses 20a.
The output signals 35 are coupled to horizontal and vertical deflection circuits~ not shown, for obtaining synchronized deflection scanning. , Comparator 37, depending upon its gain, will require a certain voltage change to shift completely from one output voltage level to another. As illustrated in FIGURE 4a, at the start of the sync pulse, the voltage ~ `
increases from black level towards sync level at a rate limited by the system bandwidth and any noise filtering, not shown, included between the video section and the input to the sync separator. When the input voltage Vb at ~ -~
terminal 30 is equal to the lower threshold level VQ of ... . . . .
. :, RCA 70,717 10904~6i 1 comparator 37, the waveform 35 at output terminal 36 begins to move from the low state to the high state. When the input voltage Vb is equal to Va, comparator 37 is in the balanced state, and the output voltage at terminal 36 is half-way between the low and high levels. When the input voltage Vb exceeds the upper threshold level Vh of comparator 37, the voltage at output terminal 36 is in the high state. No further change now takes place in the voltage at terminal 36 until the negative-going edge of the sync pulse when the reverse of the above occurs.
The switching thresholds V0 and Vh of comparator 37 can be made to approach Va by increasing the gain of comparator 37. In practice, V~ and Vh will differ by less than five millivolts.
The circuit of FIGURE 1 can readily be fabricated -~
as an integrated circuit, and comparator reference level Va may be varied, as illustrated in FIGURE 4b, over a wide range ~V by such conventional techniques as geometrical device ratioing or by including a small resistor in diode chain 25. If the reference level Va is placed too close to the sync level then the circuit will be sensitive to noise pulses superimposed on the sync level. By setting the reference level Va closer to the black level, improved noise immunity results, but in the presence of small amplitude sync pulses, such as would result from weak signals or some remodulated cable distribution systems, the sync separator would actually be operating on video, as illustrated in FIGURE 4c. A compromise in the voltage level of Va with respect to DC restoring level Vb has to be established to provide correct operation of the RCA 70,717 1090466 ~:
I circuit in the presence of composite video waveforms with ~, compressed syncs and normal composite video waveforms having a high noise content.
The circuit of FIGURE 2 is another embodiment ;
of a sync separator circuit and includes a noise elimination circuit. Circuit elements of FIGURE 2 corresponding to those of FIGURE 1 are identically marked.
Capacitor 21 is now coupled to input terminal 30 at the ~ -base of transistor 22 through a resistor 39, and the collector of transistor 27 is coupled to constant current source 28 through a resistor 38. The junction of resistors 23 and 39 is coupled to a first differential amplifier input terminal 60 of a differential amplifying pair of transistors 41 and 42. A second input terminal 43 is coupled to resistor 38. Constant current sources 44 and 45 are coupled, respectively, to the collector of transistor 41 and the emitters of transistors 41 and 42. Constant .
current source 44 is coupled to ground through serially ~-coupled diodes 46-48 and a resistor 49. A transistor 51 has its collector coupled to the cathodes of diodes 32 and 34, its base coupled to resistor 49, and its emitter coupled to ground.
In the absence of noise, when sync pulses 20a bias transistor 22 into conduction, the voltage drop across resistor 39 establishes a certain reference voltage at differential amplifier input terminal 60. The voltage drop across resistor 38 is selected to be larger than that ~¦
across resistor 39. Transistor 42 will conduct, and transistor 41 will be cut off. Current from source 44 will flow through elements 46-49, causing transistor 51 _ 7 _ , ,, ,:
RCA 70,717 ~9046~;
I to saturate.
In the presence of noise which exceeds the normal sync pulse height, a higher than normal current flows through resistor 39, and the added voltage drop, due to the noise, turns transistor 41 on, thereby sinking the current from source 44 away from elements 46-49. In this condition, transistor 51 cuts off, cutting off transistor 22 and disabling operation of sync separator 50.
The current flow through resistor 39 from capacitor 21 is reduced to a value which will just maintain transistor 41 conducting. The discharge rate of capacitor 21 is greatly reduced, thus ensuring a rapid recovery time of sync separator circuit 50 after the noise interference has ceased.
A modification of the circuit of FIGURE 2 iS
illustrated in FIGURE 3. Comparator 37 comprises a pair of differentially coupled transistors 52 and 53 and a constant current source 54; output terminal 36 is coupled to the collector of transistor 53. Constant current sources 24 and 28 of FIGURE 2 are replaced, respectively, by resistors 55 and 56. The reference voltage at an input terminal 64 is obtained from a voltage divider across transistor 27 at the junction of a resistor 57 and a resistor 58.
The amplification capability of transistor 22 can be used to advantage by coupling an input terminal 63 to the collector of transistor 22. Because, in saturation, the collector voltage of transistor 22 approaches the emitter voltage~ the clipping point for sync pulses 20a can be accurately determined.
~; ,, RCA 70,717 ~090466 I ~he noise threshold level is determined by use of a voltage divider comprising resistors 61 and 62 coupled across a diode coupled transistor 59 in series with transistor 27. Such an arrangement results in the noise threshold level remaining virtually constant over a wide range of supply voltages.
With the component values of FIGURE 3, as indicated, and with a nominal 3 volt peak-to-peak composite video signal 20, correct sync separator operation was obtained with as little as 15~ relative sync pulse amplitude (approximately 150 millivolts), while maintaining full noise immunity performance.
~ ;
.: .
~ ~
.-- .
:
.. . . .. : ... . .. , . ' ., ~ . . '' : .
:,~
1~90466 RCA 70,717 I plurality of series coupled diodes and establishes a first voltage at a terminal coupled to the diodes. A
second circuit, responsive to a source of video signals, the video signals including synchrohizing signals, introduces to the plurality of series coupled diodes during the occurrence of the synchronizing signals a current in addition to the bias current for establishing a second voltage at the terminal. A third circuit develops an output signal when the second voltage and a reference voltage differ by a predetermined value.
FIGURE 1 lS a schematlc clrcult of an embodiment of the invention;
FIGURE 2 is a schematic circuit of another embodiment of the invention;
FIGURE 3 is a schematic circuit of still another embodiment of the invention; and FIGIJRES 4a - 4c illustrate waveforms associated with the circuits of FIGURES 1 - 3.
In FIGURE 1, AC signals comprising composite video signals 20, obtained from conventional IF stages of a television receiver, are coupled to a terminal 10 of a sync separator circuit 50. The signals are then coupled through a capacitor 21 t~ a first input terminal 30 at the base of a transistor 22. A resistor 23 couples the base of transistor 22 to a source of B+ voltage. The collector of transistor 22 is coupled to a constant current source 24. The emitter is coupled to ground through a pair of diodes 31 and 32, forming a first diode - ~ . ' ' ': :
- RCA 70,717 10~0466 1 ^hain 25 comprising diodes 31 and 32 and the base-emitter junction of transistor 22.
Capacitor 21, resistor 23 and transistor 22 form a DC restorer circuit 40 to provide a DC restoration voltage to the video sync portion 20a of the AC composite video signals 20. During the sync interval, transistor 22 ~ ~-is forward biased into saturation by the sync pulses 20a of composite video signals 20, and a DC restoration voltage equal to the difference between the DC voltage at terminal 30 and the effective DC appearing at terminal 10 during the sync period is developed across the capacitor.
The resistor 23 provides current to charge capacitor 21 during the video picture interval to replace charge removed during the sync interval.
lS When transistor 22 conducts during the sync interval, current flows through diode chain 25. A major portion of this current comprises a biasing current -originating from constant current source 24. This biasing current establishes a reference potential at 2~ terminal 30. Capacitor 21 of the DC restorer circuit 40 then provides the remaining additional current through diode chain 40. The additional current increases the voltage at terminal 30 by an incremental amount, providing a voltage level Vb at terminal 30 during the sync interval.
Coupled between the B+ voltage source and ground are a constant current source 28, a transistor 27, and a pair of diodes 33 and 34. The collector and base of transistor 27 are coupled together forming a diode structure. A second diode chain 26 comprises diodes 33 and 34 and the base-emitter junction of transistor 27.
109046~ RCA 70,7l7 1 Diode chains 2S and 26 are illustratively constructed from identical npn transistors, and for identical constant current sources 24 and 28, the voltage at a second input terminal 29 coupled to the base of transistor 27 is equal to a reference voltage Va.
Input terminals 29 and 30 are coupled to a , , , voltage comparator 37. During the picture interval, the negative-going video signals 20b reverse bias transistor 22, and the voltage at input terminal 30 of comparator 37 is lower than the voltage at input terminal 29. The . .~
voltage at an output terminal 36 is at a first output -~
voltage level. During the sync interval, because of the `
.
additional current from capacitor 21, the voltage at terminal 30 is at a value Vb which is greater than the voltage Va at terminal 29. The voltage at output terminal 36 of comparator 37 then shifts to a second output voltage level, thereby providing repetitive output signals 35 ~-~
in synchronization with the incoming sync pulses 20a.
The output signals 35 are coupled to horizontal and vertical deflection circuits~ not shown, for obtaining synchronized deflection scanning. , Comparator 37, depending upon its gain, will require a certain voltage change to shift completely from one output voltage level to another. As illustrated in FIGURE 4a, at the start of the sync pulse, the voltage ~ `
increases from black level towards sync level at a rate limited by the system bandwidth and any noise filtering, not shown, included between the video section and the input to the sync separator. When the input voltage Vb at ~ -~
terminal 30 is equal to the lower threshold level VQ of ... . . . .
. :, RCA 70,717 10904~6i 1 comparator 37, the waveform 35 at output terminal 36 begins to move from the low state to the high state. When the input voltage Vb is equal to Va, comparator 37 is in the balanced state, and the output voltage at terminal 36 is half-way between the low and high levels. When the input voltage Vb exceeds the upper threshold level Vh of comparator 37, the voltage at output terminal 36 is in the high state. No further change now takes place in the voltage at terminal 36 until the negative-going edge of the sync pulse when the reverse of the above occurs.
The switching thresholds V0 and Vh of comparator 37 can be made to approach Va by increasing the gain of comparator 37. In practice, V~ and Vh will differ by less than five millivolts.
The circuit of FIGURE 1 can readily be fabricated -~
as an integrated circuit, and comparator reference level Va may be varied, as illustrated in FIGURE 4b, over a wide range ~V by such conventional techniques as geometrical device ratioing or by including a small resistor in diode chain 25. If the reference level Va is placed too close to the sync level then the circuit will be sensitive to noise pulses superimposed on the sync level. By setting the reference level Va closer to the black level, improved noise immunity results, but in the presence of small amplitude sync pulses, such as would result from weak signals or some remodulated cable distribution systems, the sync separator would actually be operating on video, as illustrated in FIGURE 4c. A compromise in the voltage level of Va with respect to DC restoring level Vb has to be established to provide correct operation of the RCA 70,717 1090466 ~:
I circuit in the presence of composite video waveforms with ~, compressed syncs and normal composite video waveforms having a high noise content.
The circuit of FIGURE 2 is another embodiment ;
of a sync separator circuit and includes a noise elimination circuit. Circuit elements of FIGURE 2 corresponding to those of FIGURE 1 are identically marked.
Capacitor 21 is now coupled to input terminal 30 at the ~ -base of transistor 22 through a resistor 39, and the collector of transistor 27 is coupled to constant current source 28 through a resistor 38. The junction of resistors 23 and 39 is coupled to a first differential amplifier input terminal 60 of a differential amplifying pair of transistors 41 and 42. A second input terminal 43 is coupled to resistor 38. Constant current sources 44 and 45 are coupled, respectively, to the collector of transistor 41 and the emitters of transistors 41 and 42. Constant .
current source 44 is coupled to ground through serially ~-coupled diodes 46-48 and a resistor 49. A transistor 51 has its collector coupled to the cathodes of diodes 32 and 34, its base coupled to resistor 49, and its emitter coupled to ground.
In the absence of noise, when sync pulses 20a bias transistor 22 into conduction, the voltage drop across resistor 39 establishes a certain reference voltage at differential amplifier input terminal 60. The voltage drop across resistor 38 is selected to be larger than that ~¦
across resistor 39. Transistor 42 will conduct, and transistor 41 will be cut off. Current from source 44 will flow through elements 46-49, causing transistor 51 _ 7 _ , ,, ,:
RCA 70,717 ~9046~;
I to saturate.
In the presence of noise which exceeds the normal sync pulse height, a higher than normal current flows through resistor 39, and the added voltage drop, due to the noise, turns transistor 41 on, thereby sinking the current from source 44 away from elements 46-49. In this condition, transistor 51 cuts off, cutting off transistor 22 and disabling operation of sync separator 50.
The current flow through resistor 39 from capacitor 21 is reduced to a value which will just maintain transistor 41 conducting. The discharge rate of capacitor 21 is greatly reduced, thus ensuring a rapid recovery time of sync separator circuit 50 after the noise interference has ceased.
A modification of the circuit of FIGURE 2 iS
illustrated in FIGURE 3. Comparator 37 comprises a pair of differentially coupled transistors 52 and 53 and a constant current source 54; output terminal 36 is coupled to the collector of transistor 53. Constant current sources 24 and 28 of FIGURE 2 are replaced, respectively, by resistors 55 and 56. The reference voltage at an input terminal 64 is obtained from a voltage divider across transistor 27 at the junction of a resistor 57 and a resistor 58.
The amplification capability of transistor 22 can be used to advantage by coupling an input terminal 63 to the collector of transistor 22. Because, in saturation, the collector voltage of transistor 22 approaches the emitter voltage~ the clipping point for sync pulses 20a can be accurately determined.
~; ,, RCA 70,717 ~090466 I ~he noise threshold level is determined by use of a voltage divider comprising resistors 61 and 62 coupled across a diode coupled transistor 59 in series with transistor 27. Such an arrangement results in the noise threshold level remaining virtually constant over a wide range of supply voltages.
With the component values of FIGURE 3, as indicated, and with a nominal 3 volt peak-to-peak composite video signal 20, correct sync separator operation was obtained with as little as 15~ relative sync pulse amplitude (approximately 150 millivolts), while maintaining full noise immunity performance.
~ ;
.: .
~ ~
.-- .
:
.. . . .. : ... . .. , . ' ., ~ . . '' : .
Claims (12)
1. A sync separator circuit adapted to be driven by a source of video signals, said video signals including synchronizing signals, comprising: a first plurality of series coupled diodes; controllable switching means coupled to said first plurality; a source of first bias current coupled to a control terminal of said controllable switching means; first means coupled to one of said first plurality and said switching means for providing a first current through said first plurality of series coupled diodes, said first current establishing a first voltage at a first terminal coupled to said first plurality of series coupled diodes during the occurrence of said synchronizing signals; second means coupled to said control terminal and to the source of video signals for providing during the occurrence of said synchronizing signals an additional bias current to said controllable switching means for introducing to said first plurality of series coupled diodes during said occurrence a second current in addition to said first current for establishing a second voltage at said first terminal; a source of first reference voltage; and comparator means coupled to said source of first reference voltage and responsive to said first reference voltage and said second voltage for developing an output signal when said second voltage and said first reference voltage differ by a predetermined value.
2. A circuit according to Claim 1, wherein said source of first reference voltage comprises a second plurality of series coupled diodes through which a third current flows.
3. A circuit according to Claim 1 wherein said second means comprises a DC restorer circuit for providing said additional bias current.
4. A circuit according to Claim 3 wherein said DC
restorer circuit includes a capacitor coupled to said controllable switching means, said controllable switching means conducting in a saturated state during the occurrence of said synchronizing signals.
restorer circuit includes a capacitor coupled to said controllable switching means, said controllable switching means conducting in a saturated state during the occurrence of said synchronizing signals.
5. A circuit according to Claim 4, wherein said controllable switching means comprises a first transistor, said first bias current and said additional bias current coupled to a base-emitter junction of said first transistor.
6. A circuit according to Claim 5, wherein said first terminal is coupled to the collector of said first transistor.
7. A circuit according to Claim 5, including noise elimination means comprising third means coupled to said series coupled diodes for generating at a terminal coupled to said third means a third voltage during the occurrence of said synchronizing signals, means for generating a noise reference voltage and disabling means responsive to said third voltage and said noise reference voltage for disabling operation of said sync separator circuit when said third voltage and said noise reference voltage differ by a predetermined value.
8. A circuit according to Claim 7, wherein said third means comprises a resistor through which said additional bias current flows.
9. A circuit according to Claim 7 wherein said disabling means includes switching means coupled to said first plurality of series coupled diodes, and fourth means coupled to said switching means for changing the conduction of said switching means when said third voltage and said noise reference voltage differ by a predetermined value.
10. A circuit according to Claim 9, wherein said fourth means comprises a differential amplifier including second and third differentially coupled transistors, said third voltage and said noise reference voltage sources coupled, respectively, to first and second input terminals of said differential amplifier.
11. A circuit according to Claim 7, wherein said source of first reference voltage comprises a second plurality of series coupled diodes through which a third current flows.
12. A circuit according to Claim 11, wherein said means for generating a noise reference voltage comprises a first diode coupled in series with said second plurality of series coupled diodes and a voltage divider network coupled across said first diode, said noise reference voltage obtained at a junction point within said voltage divider network.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| GB1253576A GB1572823A (en) | 1976-03-29 | 1976-03-29 | Tv sync pulse separator and noise gate |
| GB12535/76 | 1976-03-29 |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CA1090466A true CA1090466A (en) | 1980-11-25 |
Family
ID=10006407
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CA274,298A Expired CA1090466A (en) | 1976-03-29 | 1977-03-18 | Tv sync pulse separator and noise gate |
Country Status (10)
| Country | Link |
|---|---|
| JP (1) | JPS52119115A (en) |
| AT (1) | AT368337B (en) |
| AU (1) | AU511857B2 (en) |
| CA (1) | CA1090466A (en) |
| DE (1) | DE2713952C3 (en) |
| FI (1) | FI61595C (en) |
| FR (1) | FR2346921A1 (en) |
| GB (1) | GB1572823A (en) |
| IT (1) | IT1076400B (en) |
| SE (1) | SE418351B (en) |
Families Citing this family (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE3309809A1 (en) * | 1983-03-18 | 1984-09-20 | Siemens AG, 1000 Berlin und 8000 München | METHOD FOR SEPARATING THE SYNCHRONOUS-PULSE MIXTURE FROM THE FBAS SIGNAL AND CIRCUIT FOR A DIGITAL AMPLITUDE SCREEN FOR IMPLEMENTING THE METHOD |
| JPS61120584A (en) * | 1984-11-15 | 1986-06-07 | Matsushita Electric Ind Co Ltd | Synchronizing separating and clamping device |
Family Cites Families (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US3746786A (en) * | 1971-04-30 | 1973-07-17 | Hitachi Ltd | Noise detecting circuit for television receivers and the like |
| DE2315808C3 (en) * | 1972-04-05 | 1982-01-21 | Sony Corp., Tokyo | Sync signal disconnection circuit |
| US3809808A (en) * | 1972-09-13 | 1974-05-07 | Bell Telephone Labor Inc | Video sync separator |
-
1976
- 1976-03-29 GB GB1253576A patent/GB1572823A/en not_active Expired
-
1977
- 1977-03-14 IT IT2121077A patent/IT1076400B/en active
- 1977-03-18 CA CA274,298A patent/CA1090466A/en not_active Expired
- 1977-03-21 SE SE7703229A patent/SE418351B/en not_active IP Right Cessation
- 1977-03-22 FI FI770891A patent/FI61595C/en not_active IP Right Cessation
- 1977-03-23 AU AU23530/77A patent/AU511857B2/en not_active Expired
- 1977-03-28 JP JP3517077A patent/JPS52119115A/en active Granted
- 1977-03-28 FR FR7709195A patent/FR2346921A1/en active Granted
- 1977-03-29 DE DE19772713952 patent/DE2713952C3/en not_active Expired
- 1977-03-29 AT AT218077A patent/AT368337B/en not_active IP Right Cessation
Also Published As
| Publication number | Publication date |
|---|---|
| GB1572823A (en) | 1980-08-06 |
| FI61595C (en) | 1982-08-10 |
| AU511857B2 (en) | 1980-09-11 |
| ATA218077A (en) | 1982-01-15 |
| JPS5528637B2 (en) | 1980-07-29 |
| FR2346921B1 (en) | 1982-03-19 |
| SE418351B (en) | 1981-05-18 |
| FR2346921A1 (en) | 1977-10-28 |
| AU2353077A (en) | 1978-09-28 |
| SE7703229L (en) | 1977-09-30 |
| IT1076400B (en) | 1985-04-27 |
| JPS52119115A (en) | 1977-10-06 |
| FI770891A (en) | 1977-09-30 |
| AT368337B (en) | 1982-10-11 |
| DE2713952A1 (en) | 1977-10-06 |
| FI61595B (en) | 1982-04-30 |
| DE2713952C3 (en) | 1982-01-28 |
| DE2713952B2 (en) | 1979-06-28 |
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