WO2014167727A1 - 電力変換装置 - Google Patents
電力変換装置 Download PDFInfo
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- WO2014167727A1 WO2014167727A1 PCT/JP2013/061113 JP2013061113W WO2014167727A1 WO 2014167727 A1 WO2014167727 A1 WO 2014167727A1 JP 2013061113 W JP2013061113 W JP 2013061113W WO 2014167727 A1 WO2014167727 A1 WO 2014167727A1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/06—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
- H02M1/322—Means for rapidly discharging a capacitor of the converter for protecting electrical components or for preventing electrical shock
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- the present invention relates to a power conversion device that converts AC power into DC and supplies it to a load.
- a power conversion device that converts AC power into DC and supplies it to a load
- a rectifier that full-wave rectifies the input from the AC power
- a chopper circuit having a switching element that is turned on and off by a PWM signal
- the power source is short-circuited through the reactor by opening and closing the switching element, thereby shaping the current waveform to improve the power factor, reducing the harmonics of the input current, and
- the output voltage is raised and lowered by charging and discharging the energy.
- Patent Document 1 discloses that “first and second input terminals to which an input voltage is supplied, first and second output terminals from which an output voltage is extracted, and one end connected to the first input terminal.
- the other end of the choke coil is connected to the first output terminal via a diode, and the other end of the choke coil and the connection point of the diode are connected to the second output terminal.
- a switching element a capacitor connected between the connection point of the diode and the first output terminal, and the second output terminal, and a threshold value that presets a current that flows when the switching element is turned on
- a comparator for comparing the output signal, an oscillator, a pulse width modulation circuit for controlling a duty ratio of a pulse signal formed from the output signal of the oscillator to stabilize the output voltage, and the pulse
- a frequency switching circuit that is supplied with an output signal from the width modulation circuit and switches the frequency of the output signal by the comparison signal from the comparison unit, and a PFC control that outputs a pulse signal for turning on and off the switching element from the frequency switching circuit
- the frequency switching circuit switches the frequency of the pulse signal to a higher frequency when the current flowing when the switching element is turned on is greater than or greater than the threshold.
- Power supply is disclosed.
- Patent Document 1 an oscillator that charges and discharges a capacitor using a current source is used, and there is a problem that the configuration as hardware becomes complicated and the cost increases.
- the present invention has been made in view of the above, and using a general-purpose function mounted on a general-purpose microcomputer generally used as a control unit for controlling a switching element of a power conversion device, without increasing the cost,
- An object of the present invention is to provide a power converter that can easily switch (increase or change) the switching frequency.
- a power converter is a power converter arranged between an AC power supply and a load, and rectifies a voltage of the AC power supply.
- a smoothing unit that smoothes the DC voltage on the load side from the rectifier circuit unit, a short circuit unit that is disposed on the AC power supply side from the smoothing unit, and short-circuits the AC power source, and the short circuit unit At least one of a reactor disposed on the AC power supply side, a reactor current detection unit that detects the current of the reactor, and a bus voltage detection unit that detects an output voltage of the smoothing unit, and the AC power supply side from the smoothing unit
- a drive pulse is generated from a backflow prevention element for preventing a backflow of current to the current and an output signal of the reactor current detection unit or the bus voltage detection unit, and a control signal for opening and closing the short-circuit unit is output by the drive pulse.
- the switching frequency can be easily switched (increased or decreased) without increasing the cost by using a general-purpose function mounted on a general-purpose microcomputer generally used as a control unit for controlling the switching element of the power conversion device. It is possible to provide a changeable power converter.
- FIG. 1 is a diagram illustrating a configuration example of a power conversion device according to the first embodiment.
- FIG. 2 is a diagram illustrating the switching control unit according to the first embodiment.
- FIG. 3 is a diagram showing a current waveform during operation of the boost converter unit according to the first embodiment.
- FIG. 4 is a diagram showing a current waveform when the amount of change in current during the period when the switching element according to the first embodiment is on is larger than the amount of change in current during the off period.
- FIG. 5 is a diagram illustrating a current waveform when the amount of change in current during the period in which the switching element according to Embodiment 1 is on is smaller than the amount of change in current during the period during which off.
- FIG. 1 is a diagram illustrating a configuration example of a power conversion device according to the first embodiment.
- FIG. 2 is a diagram illustrating the switching control unit according to the first embodiment.
- FIG. 3 is a diagram showing a current waveform during operation of the boost converter unit according to the first
- FIG. 6 is a diagram for explaining a current mode of the reactor current according to the first embodiment.
- FIG. 7 is a diagram showing waveforms in the discontinuous mode according to the first embodiment.
- FIG. 8 is a diagram showing waveforms in the continuous mode according to the first embodiment.
- FIG. 9 is a diagram illustrating a case where the switching frequency is changed to twice the frequency of the carrier signal in the drive pulse generation unit using the switching frequency changing unit.
- FIG. 10 is a diagram illustrating a case where the switching frequency is changed to three times the frequency of the carrier signal in the drive pulse generation unit using the switching frequency changing unit.
- FIG. 11 is a diagram illustrating a configuration example of the power conversion device according to the second embodiment.
- FIG. 12 is a diagram illustrating a configuration example of the power conversion device according to the second embodiment.
- FIG. 13 is a diagram illustrating a configuration example of the power conversion device according to the second embodiment.
- FIG. 14 is a diagram illustrating a configuration example of the power conversion device according to the
- FIG. 1 is a diagram illustrating a configuration example of a power conversion device according to an embodiment of the present invention. 1 is disposed between a three-phase AC power source 1 (AC power source) and a load 12, and includes a three-phase rectifier 2 (rectifier circuit unit), a boost converter unit 3, a smoothing capacitor 7, A reactor current detection unit 8, a bus voltage detection unit 9, a switching control unit 10, and a switching frequency change unit 11 are provided.
- AC power source AC power source
- a load 12 includes a three-phase AC power source 1 (AC power source) and a load 12, and includes a three-phase rectifier 2 (rectifier circuit unit), a boost converter unit 3, a smoothing capacitor 7, A reactor current detection unit 8, a bus voltage detection unit 9, a switching control unit 10, and a switching frequency change unit 11 are provided.
- the three-phase AC power source 1 is short-circuited by the short-circuit portion 24 via the boost reactor 4.
- the three-phase rectifier 2 has a configuration in which six diode elements 14a to 14f are bridge-connected, and rectifies the AC voltage of the three-phase AC power source 1.
- the step-up converter unit 3 includes a step-up reactor 4, a switching element 5, and a backflow prevention element 6.
- a smoothing unit 25 is arranged on the load 12 side from the boost converter unit 3.
- the smoothing unit 25 has a smoothing capacitor 7, and the smoothing capacitor 7 smoothes the output of the boost converter unit 3 (DC voltage on the load 12 side).
- the boost reactor 4 is arranged on the three-phase AC power source 1 side with respect to the short-circuit unit 24, and the backflow prevention element 6 is connected from the smoothing unit 25 to the three-phase AC power source 1 side. It arrange
- the short-circuit unit 24 is disposed closer to the three-phase AC power source 1 than the smoothing unit 25 and shorts the three-phase AC power source 1 side.
- the short-circuit part 24 has the switching element 5, and the opening and closing of the short-circuit part 24 is controlled by the switching element 5.
- the switching element 5 for example, an IGBT (Insulated Gate Bipolar Transistor) can be used.
- the backflow prevention element 6 prevents backflow of current from the smoothing unit 25 to the three-phase AC power supply 1 side.
- a diode element may be used as illustrated in FIG.
- a diode element used for the backflow prevention element 6 a fast recovery diode can be illustrated.
- Smoothing capacitor 7 smoothes the output of boost converter unit 3.
- the reactor current detector 8 detects the reactor current flowing through the boost reactor 4.
- the bus voltage detector 9 detects and outputs the bus voltage that is the smoothed output voltage of the boost converter 3.
- the switching control unit 10 generates a drive signal for operating the switching element 5, controls the opening and closing of the switching element 5, and controls whether or not the short circuit unit 24 opens and closes.
- the switching control part 10 should just be comprised by the calculator. Examples of the arithmetic unit include a microcomputer (DSP) or a DSP (Digital Signal Processor).
- FIG. 2 is a diagram illustrating a configuration example of the switching control unit 10 according to the first embodiment of the present invention.
- the switching control unit 10 illustrated in FIG. 2 includes a bus voltage control unit 21, a reactor current control unit 22, and a drive pulse generation unit 23.
- the bus voltage controller 21 calculates a reactor current command value I dc * from the bus voltage value V o and the bus voltage command value V o * , which are output signals of the bus voltage detector 9.
- the calculation of the reactor current command value I dc * is performed by, for example, proportional-integral control (PI control) of a deviation between the bus voltage value V o and the bus voltage command value V o * , which is an output signal of the bus voltage detection unit 9. And do it.
- PI control proportional-integral control
- the reactor current control unit 22 determines the on-duty of the switching element 5 from the reactor current value I dc that is an output signal of the reactor current detection unit 8 and the reactor current command value I dc * that is an output signal of the bus voltage control unit 21. Is calculated.
- the calculation of the on-duty is, for example, proportional to the deviation between the reactor current value I dc that is the output signal of the reactor current detection unit 8 and the reactor current command value I dc * that is the output signal of the bus voltage control unit 21.
- Perform integration control The on-duty calculation may be performed by proportional-integral control (PI control) of the deviation between the bus voltage value V o that is the output signal of the bus voltage detector 9 and the bus voltage command value V o * . That is, the on-duty calculation may be performed without using the reactor current value I dc . Therefore, the on-duty calculation may include either the reactor current detection unit 8 or the bus voltage detection unit 9.
- PI control proportional-integral control
- the drive pulse generator 23 generates a drive pulse for operating the switching element 5 based on the on-duty calculated by the reactor current controller 22 or the bus voltage controller 21. For example, the drive pulse generator 23 calculates a timer value based on the on-duty, compares the timer value with a carrier signal such as a triangular wave or sawtooth wave, and performs switching only in a section where the timer value is larger than the carrier signal. A pulse signal is output so that the element 5 is turned on.
- a carrier signal such as a triangular wave or sawtooth wave
- the calculation method of the bus voltage controller 21 and the reactor current controller 22 is not limited to proportional-integral control (PI control), and proportional control may be used or integral control may be used. Alternatively, proportional integral derivative control (PID control) may be used.
- PI control proportional-integral control
- PID control proportional integral derivative control
- the input voltage of the boost converter unit 3 is an output voltage rectified by the three-phase rectifier 2 and is expressed as V ds .
- the output voltage of the boost converter unit 3 is smoothed by the smoothing unit 25.
- the smoothed voltage smoothing unit 25 is expressed as V o.
- V ds and V o V ds / (1 ⁇ D on ) using on-duty D on. expressed.
- V ds can be controlled, and the output voltage of the boost converter unit 3 can be controlled.
- D on (V o ⁇ V ds ) / V o .
- FIG. 3 is a diagram showing a current waveform during the operation of the boost converter unit 3.
- 3A shows a current waveform when the switching element 5 is turned on
- FIG. 3B shows a current waveform when the switching element 5 is turned off.
- V ds is applied to the boost reactor 4.
- V ds ⁇ V o is applied to the boost reactor 4 in the opposite direction to that when it is on.
- the on-duty D on is larger than the relationship of the above equation, the amount of change in current during the period when the switching element 5 is turned on becomes larger than the amount of change in current during the period during which the switching element 5 is turned off.
- FIG. 4 is a diagram showing a current waveform when the amount of change in current during the period in which the switching element 5 is turned on is greater than the amount of change in current during the period in which the switching element 5 is turned off. As shown in FIG. 4, the current gradually increases by repeatedly opening and closing the switching element 5.
- the on-duty D on is smaller than the relationship of the above formula, the amount of change in current during the period when the switching element 5 is turned on becomes smaller than the amount of change in current during the period when it is turned off.
- FIG. 5 is a diagram showing a current waveform when the amount of change in current during the period when the switching element 5 is turned on is smaller than the amount of change in current during the period during which the switching element 5 is turned off. As shown in FIG. 5, the current gradually decreases by repeatedly opening and closing the switching element 5.
- the waveform of the current flowing through the boost reactor 4 from the three-phase AC power source 1 side to the load 12 side can be controlled by the on-duty.
- FIGS. 6A to 6C are diagrams for explaining the current mode of the reactor current.
- a current mode in which the reactor current becomes zero each time the switching element 5 is switched (turned on and off) is called a discontinuous mode.
- a current mode in which the reactor current does not become zero every time the switching element 5 is switched (turned on and off) is called a continuous mode.
- the continuous mode the next time the switching element 5 is turned on, the behavior is such that the final value of the current in the previous off period of the switching element 5 is the initial value.
- the current mode in which the reactor current becomes zero in the OFF section of the switching element 5 and at the same time the ON section of the next switching element 5 starts is defined as the discontinuous mode and the continuous mode. In the sense of a boundary, it is called a critical mode.
- the current in this energization section is equal to the current flowing through the boost reactor 4 from the three-phase AC power source 1 side to the load 12 side in the energization section.
- the boost converter unit 3 not only boosts the bus voltage, but also improves the power factor and reduces the harmonic components included in the input current.
- FIG. 7A and 7B show waveforms in the discontinuous mode.
- FIG. 7A shows a waveform when the on-duty is large in the discontinuous mode
- FIG. 7B shows a waveform when the on-duty is small in the discontinuous mode.
- FIG. 8A and 8B are waveforms in the continuous mode.
- FIG. 8A shows a waveform when the on-duty is large in the continuous mode
- FIG. 8B shows a waveform when the on-duty is small in the continuous mode.
- the switching control unit 10 calculates the on-duty and opens and closes the switching element 5 based on this on-duty.
- the switching frequency which is the frequency at which the switching element 5 repeats opening and closing, is generally a drive pulse. It is determined by the frequency of the carrier signal in the generation unit 23.
- This carrier signal is set by a microcomputer or the like used for the switching control unit 10, but the timing for performing the control calculation of the bus voltage control unit 21 and the reactor current control unit 22 is also usually the peak or valley of the same carrier signal.
- the carrier signal is generally set to a predetermined value.
- the time that can be used for the control calculation is also shortened. That is, there is a problem that it is difficult to change the switching frequency according to the load of the device (particularly to increase the frequency).
- the switching frequency changing unit 11 between the gate of the switching element 5 included in the short circuit unit 24 and the switching control unit 10
- the switching frequency is changed without changing the frequency.
- the switching frequency can be changed without affecting the load of the control calculation.
- FIG. 9 is a diagram illustrating a case where the switching frequency is set to twice the frequency of the carrier signal in the drive pulse generation unit 23 as an example of the operation using the switching frequency changing unit 11.
- the drive pulse generator 23 outputs at least two drive pulses (S1, S2).
- the drive pulse generator 23 desirably has a 6-phase PWM function mounted on a microcomputer having a motor control function.
- the 6-phase PWM function is often installed in microcomputers that are supposed to be used for controlling three-phase inverters that control motors.
- a timer value for one phase Two-phase drive pulses (S1p and S1n, S2p and S2n) suitable for one-phase upper and lower switching elements, that is, ON and OFF are inverted are generated.
- S1p and S1n, S2p and S2n Two-phase drive pulses
- the switching frequency can be easily changed by using this 6-phase drive pulse generation.
- the first timer value t1 to be compared with the carrier signal is 1 ⁇ 2 of the on-duty D on
- the second timer value t2 is 1 (on)
- a pulse having a phase difference of 180 degrees from the pulse generated at t1 when compared with the same carrier signal is generated.
- the ratio of the on-time of both pulses is equal.
- S1p and S2n are input to the OR circuit included in the switching frequency changing unit 11 (S1p OR S2n).
- S1p is a pulse signal for an element on the upper arm side of the inverter among pulse signals generated using the first timer value t1
- S1n is a pulse signal generated using the first timer value t1.
- it is a pulse signal for the element on the lower arm side of the inverter.
- S2p is a pulse signal for the element on the upper arm side of the inverter among pulse signals generated using the second timer value t2
- S2n is a pulse signal generated using the second timer value t2. It is a pulse signal for the element on the lower arm side of the inverter.
- the output pulse signal is one period of the carrier signal. Both the ON section and the OFF section appear twice in the signal, and the signal has a frequency twice that of the carrier signal.
- the above-described first timer value t1 is set to 1 ⁇ 2 of the desired on-duty D on , so that the ratio of the on-time to the switching cycle becomes a value equivalent to the desired on-duty D on . In this manner, a pulse signal having a switching frequency exceeding the upper limit of the carrier frequency of the microcomputer can be generated.
- the switching element 5 and the backflow prevention element 6 are formed of a wide gap semiconductor (for example, SiC or GaN), the switching element 5 and the backflow prevention element 6 are generally used at a switching frequency higher than that of an element formed of Si.
- a wide gap semiconductor for example, SiC or GaN
- the switching frequency is increased, the required inductance value of the reactor can be reduced, so that the reactor can be reduced in size. Further, since a reactor having a low inductance value can be used, the cost can be reduced.
- a signal with a desired on-duty can be obtained at the same frequency as the carrier signal. That is, by providing the switching frequency changing unit 11, it is possible to switch between 1 and 2 times the frequency of the carrier signal only by changing (switching) the arithmetic expression of the timer value.
- FIG. 10 is a diagram illustrating a case where the switching frequency is set to three times the frequency of the carrier signal in the drive pulse generator 23 as an example of the operation using the switching frequency changer 11.
- the drive pulse generator 23 outputs at least three drive pulses (S1, S2, S3).
- S1n, S2p, and S3n are input to a logic circuit (here, an AND circuit and an OR circuit) included in the switching frequency changing unit 11 ((S1n AND S2p) OR S3n).
- a logic circuit here, an AND circuit and an OR circuit included in the switching frequency changing unit 11 ((S1n AND S2p) OR S3n).
- S1p, S1n, S2p, and S2n are the same as those in FIG.
- S3p is a pulse signal for the element on the upper arm side of the inverter among the pulse signals generated using the third timer value t3
- S3n is a pulse signal generated using the third timer value t3. Of these, it is a pulse signal for the element on the lower arm side of the inverter.
- the ratio of the on-time to the switching cycle becomes a value equivalent to the desired on-duty. In this manner, a pulse signal having a switching frequency exceeding the upper limit of the carrier frequency of the microcomputer can be generated.
- the switching element 5 and the backflow prevention element 6 are formed of a wide gap semiconductor (for example, SiC or GaN), the switching element 5 and the backflow prevention element 6 are generally used at a switching frequency higher than that of an element formed of Si.
- a wide gap semiconductor for example, SiC or GaN
- the switching frequency is increased, the required inductance value of the reactor can be lowered, so that the reactor can be downsized and the cost can be reduced.
- a signal with a desired on-duty can be obtained at a frequency equal to that of the carrier signal without changing the logic operation unit.
- the signal is set to a desired on-duty signal at a frequency twice that of the carrier signal without changing the logical operation unit.
- the switching frequency changing unit 11 it is possible to switch between 1 time, 2 times and 3 times the frequency of the carrier signal only by changing (switching) the timer value arithmetic expression.
- the logic circuit used in this embodiment may be configured using only the same type of logic circuit (for example, only a NOR circuit or a NAND circuit). If only the same type of logic circuit is used, a plurality of logic circuits having the same operator can be used in the same package, and the occupied area and cost of the logic circuit can be suppressed.
- the logic circuit used in this embodiment may be used as a protection circuit that blocks a switching signal. For example, when a circuit abnormal signal is detected, the circuit can be protected in the event of abnormality if the switching signal can be cut off.
- the method for obtaining the on-duty D on of the switching element 5 is not limited to the one that performs both the bus voltage control and the reactor current control as described above. Either one of the controls may be performed, or open loop control in which feedback such as the bus voltage and the reactor current is not performed may be used.
- a signal having a double frequency is output using two signals output from the switching control unit, and a signal having a triple frequency is output using three signals output from the switching control unit.
- the present invention is not limited to this, and by appropriately combining logic circuits, a signal having a higher frequency than the input signal can be output.
- FIG. 1 to 14 are diagrams showing a configuration example of the power conversion device according to the present embodiment.
- FIG. 11 shows a power converter in which the three-phase AC power source 1 in FIG. 1 is replaced with a single-phase AC power source 1a. As shown in FIG. 11, the present invention can also be applied to a single-phase AC power source.
- FIG. 12 shows a three-phase AC power source 1 as a single-phase AC power source 1a, a short-circuit unit 24a that is a bidirectional switch that short-circuits the single-phase AC power source 1a via the boost reactor 4, and two smoothing units connected in series. It is a figure which shows a power converter device provided with the smoothing part 25a comprised by the capacitors 7a and 7b, and the single phase rectifier 2a.
- the short-circuiting portion 24a is opened and closed to repeatedly short-circuit the power source via the boost reactor 4, thereby shaping the input current from the single-phase AC power source 1a.
- the smoothing unit 25 shown in FIG. 12 includes two smoothing capacitors 7a and 7b.
- the short-circuit switch is turned off. Then, the capacitor of the smoothing capacitor 7a is charged.
- the smoothing capacitor 7b is charged, and the voltage applied to the load 12 is double that of full-wave rectification. And when the switch for short circuit provided in the short circuit part 24a turns on, an electric current will flow into the short circuit part 24a.
- FIG. 12 shows a general configuration in the case where, for example, one IGBT (Insulated Gate Bipolar Transistor) is used as the shorting switch.
- IGBT Insulated Gate Bipolar Transistor
- FIG. 13 is a diagram showing a power conversion device in which a switch 26 is provided in the configuration of FIG. A portion where the diode elements in the single-phase rectifier 2 a of FIG. 13 are connected in series and a portion where the two smoothing capacitors 7 a and 7 b are connected are connected via a switch 26. With the configuration shown in FIG. 13, the smoothing capacitors 7a and 7b are alternately charged to obtain a doubled rectified voltage, which can be switched between a double and a double.
- FIG. 14 is a diagram showing a power conversion device in which the boost reactor 4 is arranged between the single-phase AC power source 1a and the single-phase rectifier 2a with respect to the configuration of FIG.
- the present invention can also be applied to the configuration shown in FIG.
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Abstract
Description
図1は、本発明の実施の形態に係る電力変換装置の一構成例を示す図である。図1に示す電力変換装置13は、三相交流電源1(交流電源)と負荷12の間に配置され、三相整流器2(整流回路部)と、昇圧コンバータ部3と、平滑コンデンサ7と、リアクタ電流検出部8と、母線電圧検出部9と、スイッチング制御部10と、スイッチング周波数変更部11と、を備える。
本発明の電力変換装置は、実施の形態1にて説明したものに限定されない。図11~14は、本実施の形態の電力変換装置の構成例を示す図である。
Claims (6)
- 交流電源と負荷の間に配される電力変換装置であって、
前記交流電源の電圧を整流する整流回路部と、
前記整流回路部より前記負荷側の直流電圧を平滑化する平滑化部と、
前記平滑化部より前記交流電源側に配置され、前記交流電源を短絡する短絡部と、
前記短絡部より前記交流電源側に配置されたリアクタと、
前記リアクタの電流を検出するリアクタ電流検出部及び前記平滑化部の出力電圧を検出する母線電圧検出部の少なくとも一方と、
前記平滑化部から前記交流電源側への電流の逆流を防止する逆流防止素子と、
前記リアクタ電流検出部または前記母線電圧検出部の出力信号から駆動パルスを生成し、該駆動パルスによって前記短絡部の開閉の制御信号を出力するスイッチング制御部と、
前記スイッチング制御部と前記短絡部の間に配され、論理演算により前記制御信号の周波数を変更可能なスイッチング周波数変更部と、を備える電力変換装置。 - 前記スイッチング周波数変更部の論理演算は、前記スイッチング制御部の出力する制御信号の2つ以上を用いて行い、
前記スイッチング周波数変更部の出力信号の周波数は、入力信号の周波数よりも高いことを特徴とする請求項1に記載の電力変換装置。 - 前記スイッチング周波数変更部の論理演算は、前記スイッチング制御部の2つの出力信号を用いて行い、
前記スイッチング周波数変更部の出力信号の周波数は、入力信号の周波数の略2倍とすることを特徴とする請求項1に記載の電力変換装置。 - 前記スイッチング周波数変更部の論理演算は、前記スイッチング制御部の3つの出力信号を用いて行い、
前記スイッチング周波数変更部の出力信号の周波数は、入力信号の周波数よりも高いことを特徴とする請求項1に記載の電力変換装置。 - 前記スイッチング周波数変更部の論理演算は、前記スイッチング制御部の3つの出力信号を用いて行い、
前記スイッチング周波数変更部の出力信号の周波数は、入力信号の周波数の略3倍とすることを特徴とする請求項1に記載の電力変換装置。 - 前記短絡部と前記逆流防止素子の少なくともいずれか一方にワイドギャップ半導体を用いることを特徴とする請求項1乃至請求項5のいずれか一項に記載の電力変換装置。
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CN201380075559.4A CN105122620B (zh) | 2013-04-12 | 2013-04-12 | 电力转换装置 |
JP2015511059A JP6038293B2 (ja) | 2013-04-12 | 2013-04-12 | 電力変換装置 |
PCT/JP2013/061113 WO2014167727A1 (ja) | 2013-04-12 | 2013-04-12 | 電力変換装置 |
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