CN106487308A - The input of series electric motor drive system lacks a phase error-tolerance type Direct Torque Control - Google Patents
The input of series electric motor drive system lacks a phase error-tolerance type Direct Torque Control Download PDFInfo
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- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
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Abstract
The present invention relates to a kind of series electric motor drive system input lacks a phase error-tolerance type Direct Torque Control, be applied particularly to single inverter power six phase permanent-magnet synchronous motor series connection three-phase permanent magnet synchronous motor drive system, purpose is to realize two motor transient electromagnetic torque decouplers in the case of the scarce phase of input side in this kind of bi-motor tandem drive system using remaining 5 phase inverter bridge to control, to improve the reliability of this kind of tandem drive system.
Description
Technical field
The six phase permanent-magnet synchronous motor series connection three-phase permanent magnet synchronous motor drivetrain the present invention relates to a kind of single inverter is powered
System input lacks a phase error-tolerance type Direct Torque Control.
Background technology
Close with aerospace propulsion system, full warship electric power promotion, electric locomotive traction, electronic/fuel combination Automobile drive etc.
The high speed development in key field, it has harsher requirement to the weight and volume of drive system, and lightweight, high power are close
Degree, the power-driven system of low cost will be important developing direction.Single inverter power multiple electric motors composition series connection
Drive system is an important research direction, compared with the three-phase drive system of the one-to-one power supply of inverter-motor, advantage
It is:The quantity of inverter leg decreases;All series electric motors just can be carried out by uneoupled control by a set of DSP control platform.
Single inverter power six phase permanent-magnet synchronous motor series connection three-phase permanent magnet synchronous motor drive system be multiple electric motors tandem drive system
Typical case in system, this drive system utilizes two winding current opposite in phase characteristics of six-phase motor electricity space mutual deviation 180 degree, by six
Connect with a phase winding in three phase electric machine again, thus realizing three after two winding tail end parallel connections of phase motor electricity space mutual deviation 180 degree
Electromagnetic torque decoupling between phase motor control and six-phase motor control.Power due to employing single inverter, improve and be
The reliability of system, reduces the cost of system;Further, since adopting permanent magnet excitation, two motor operation efficiency highs.
In order to improve further above-mentioned tandem drive system reliability it is desirable to six-phase motor one phase winding open circuit or inversion
Under one brachium pontis failure condition of bridge, remain able to realize the electromagnetic torque between two motors using remaining 5 inverter bridge legs
Uneoupled control.The no matter open circuit of six-phase motor one phase winding or one brachium pontis fault of inverter bridge, six-phase motor only has five phase winding works
Make, flow in the winding being connected with fault brachium pontis or breaking winding disappearance, with the phase winding of disappearance phase winding electricity space symmetr
The electric current crossed is identical with corresponding three-phase windings electric current.For lacking the six-phase motor of a phase, with disappearance phase winding electricity
The phase winding of space symmetr is uncontrollable;And, other electric currents in two windings of electric space symmetr no longer keep inverted relationship,
So destroy the electromagnetic torque decoupling between two motors.How to realize the synchronous electricity of six-phase permanent-magnet that single inverter lacks a phase
The electromagnetic torque uneoupled control that machine is connected between three-phase permanent magnet synchronous motor drive system is the problem in science that must solve.For
This, patent of the present invention proposes single inverter six phase permanent-magnet synchronous motor series connection three-phase permanent magnet synchronous motor drive system of powering and lacks one
Phase error-tolerance type Direct Torque Control.
Content of the invention
Present invention aims to the deficiencies in the prior art, a kind of single inverter is provided to power the synchronous electricity of six-phase permanent-magnet
Machine series connection three-phase permanent magnet synchronous motor drive system input lacks a phase error-tolerance type Direct Torque Control it is therefore an objective to utilize remaining
5 phase inverter bridge realize this kind of bi-motor tandem drive system occur input side lack a phase in the case of two motor transient electromagnetics turn
Square uneoupled control, to improve the reliability of this kind of tandem drive system.
For achieving the above object, the technical scheme is that:It is mutually fault-tolerant that a kind of series electric motor drive system input lacks one
Type Direct Torque Control, be applied particularly to single inverter power six phase permanent-magnet synchronous motor series connection three-phase permanent magnet synchronous motor
Drive system, the method comprises the steps,
S1:Using T6Orthogonal transform matrix, will include six input current i of disappearance phasesA~isFIt is transformed in α β coordinate
iαiβAnd i in xy coordinate systemxiy:
Wherein, io1、io2For two zero-sequence currents;Because six-phase motor lacks a phase, and three-phase windings have central point,
Two motor driven systems of all series connection only have 4 degree of freedom can control, due to needing the stator magnetic linkage to two motors, electricity
Magnetic torque carries out closed loop control, occupies 4 degree of freedom, so variable is uncontrolled in two zero sequence shaftings;
S2:Using formula (2), iαiβ, six-phase motor rotor flux ψf1And six-phase motor rotor position angle θr1Calculate α β
Plane six-phase motor stator magnetic linkage ψsαψsβ;
Lsm1=0.5 (Ldm1+Lqm1), Lrs1=0.5 (Ldm1-Lqm1), Ldm1、Lqm1It is respectively six-phase motor phase winding main magnetic circuit
Straight, quadrature axis inductance, Lsσ1For six-phase motor phase winding leakage inductance;
Using formula (3), ixiy, three phase electric machine rotor flux ψf2And three phase electric machine rotor position angle θr2Calculate x/y plane
Three-phase motor stator magnetic linkage ψsxψsy:
Lsm2=0.5 (Ldm2+Lqm2), Lrs2=0.5 (Ldm2-Lqm2), Ldm2、Lqm2It is respectively three phase electric machine phase winding main magnetic circuit
Straight, quadrature axis inductance, Lsσ2For three phase electric machine phase winding leakage inductance;
S3:Judge α β plane six-phase motor stator magnetic linkage ψsαψsβα β plane sector number θ residing for vector1si;Judge that xy puts down
Face three-phase motor stator magnetic linkage ψsxψsyX/y plane sector number θ residing for vector2si;
S4:According to α β plane six-phase motor stator magnetic linkage ψsαψsβAnd stator magnetic linkage amplitude givesThrough six-phase motor magnetic
Chain hysteresis comparator, the variable φ of output control α β plane six-phase motor stator magnetic linkage amplitudee1:
According to x/y plane three-phase motor stator magnetic linkage ψsxψsyAnd stator magnetic linkage amplitude givesThrough three phase electric machine magnetic linkage
Hysteresis comparator, the variable φ of output control x/y plane three-phase motor stator magnetic linkage amplitudee2:
S5:Using formula (4), iαiβAnd ψsαψsβCalculate six-phase motor electromagnetic torque Te1;
Te1=p1(ψsαiβ-ψsβiα) (4)
Wherein, p1For six-phase motor magnetic pole logarithm;
Using formula (5), ixiyAnd ψsxψsyCalculate three phase electric machine electromagnetic torque Te2;
Te2=p2(ψsxiy-ψsyix) (5)
Wherein, p2For three phase electric machine magnetic pole logarithm;
S6:By six-phase motor electromagnetic torque Te1And its set-pointGive six-phase motor torque hysteresis comparator, output
Control six-phase motor electromagnetic torque variable τe1,
Wherein, εm1For six-phase motor torque stagnant ring ring width, its value can be according to actual six-phase motor direct torque error need
Arrange;
By three phase electric machine electromagnetic torque Te2And its set-pointGive three phase electric machine torque hysteresis comparator, output control
Three phase electric machine electromagnetic torque variable τe2,
Wherein, εm2For three phase electric machine torque stagnant ring ring width, its value can be according to actual three phase electric machine direct torque error need
Arrange;
S7:By τe1、φe1、θ1si、τe2、φe2、θ2siIt is simultaneously sent to optimized switching vector table, obtain one group of remaining healthy 5 phase
Inverter bridge optimized switching combine, by inverter act on disappearance one mutually input six be in series three-phase permanent magnet synchronous motor drive
System, realizing two stator flux of motor amplitude errors and electromagnetic torque error is 0 control targe.
In an embodiment of the present invention, in described step S6, six-phase motor electromagnetic torque set-pointDynamo-electric with three-phase electricity
Magnetic torque set-pointDepending on concrete two motor control variables, specifically:If control is electromagnetic torque, system is straight
Connect given;If control is rotating speed, two electric motor speed controller difference output torques giveWithIf control is
Rotor position angle, then two motor position controller outputs are torque referenceWith
In an embodiment of the present invention, in described step S2, α β plane six-phase motor stator magnetic linkage ψsαψsβWith x/y plane three
Phase stator flux of motor ψsxψsyAlso can be calculated using the voltage model of stator magnetic linkage, using the stator magnet of voltage model
Chain typical calculation is as follows:
Step S21:Using T6Orthogonal transform matrix, will include six input voltage u of disappearance phaseAO~uFOIt is transformed to α β to sit
U in marksαusβAnd u in xy coordinate systemsxusy:
Wherein, uso1、uso2For two residual voltages;
Step S22:According to formula (6), iαiβCalculate α β plane six-phase motor stator magnetic linkage ψsαψsβ;
α β plane six-phase motor stator magnetic linkage ψsαψsβ:
Wherein, Rs1For six-phase motor phase winding resistance;
According to formula (7), ixiyCalculate x/y plane three-phase motor stator magnetic linkage ψsxψsy;
X/y plane three-phase motor stator magnetic linkage ψsxψsy:
Wherein, Rs2For three phase electric machine phase winding resistance.
Compared to prior art, the invention has the advantages that:The single inverter of the present invention is powered and six is in series three
Phase permagnetic synchronous motor lacks a phase error-tolerance type Direct Torque Control, solves the symmetrical winding permanent magnet of 60 degree six of biasing synchronous
Motor series connection three-phase permanent magnet synchronous motor drive system two motors in the case of input disappearance one phase continue to decouple uninterrupted fortune
A difficult problem for row, this control method has the advantage that:
1) consider the disappearance contribution to two motor mathematical models for the phase winding, two motor stator magnetic of disappearance phase will be included
Chain control is circular, achieves the uneoupled control of two motor electromagnetic torques well;
2) permagnetic synchronous motor can produce reluctance torque using saliency, thus strengthening the load capacity of motor, and
Control strategy of the present invention considers motor salient pole phenomenon, so when control object of the present invention is salient-pole permanent-magnet synchronous motor,
Drive system output torque ability can effectively be strengthened;
3), after adopting the present invention, tandem drive system can be compatible to lacking one by winding normal non-fault situation fast transition
Wrong running status, improves uninterrupted when series-connected double motors driving direct Torque Control winding open circuit or inverter bridge leg fault
Reliability of operation.
Brief description
Fig. 1 single inverter power six phase permanent-magnet synchronous motor series connection three-phase permanent magnet synchronous motor input lack a phase error-tolerance type straight
Connect torque-controlling structures figure.
Fig. 2 embodiments of the invention drive system hardware structure diagram.
Fig. 3 six phase permanent-magnet synchronous motor and three-phase permanent magnet synchronous motor series system.
Fig. 4 six phase permanent-magnet synchronous motor coordinate system defines.
Fig. 5 three-phase permanent magnet synchronous motor coordinate system defines.
The switching vector selector figure of α β plane, x/y plane after Fig. 6 phase shortage.
Synthesized voltage vector u in Fig. 7 alpha-beta planesα+jusβ.
Synthesized voltage vector u in Fig. 8 x-y planesx+jusy.
Specific embodiment
Below in conjunction with the accompanying drawings, technical scheme is specifically described.
When six symmetrical winding permanent magnet synchronous motor series connection three-phase permanent magnet synchronous motor drive system input sides lack a phase
Afterwards, if not considering six in bi-motor tandem drive system mathematic model is set up and its error-tolerance type Strategy of Direct Torque Control builds
In phase motor, the contribution of disappearance phase winding, so leads to the symmetry characteristic of original six-phase motor stator winding to go to pot, thus no
Method searches out a set of effective coordinate transform and the six-phase motor lacking a phase is carried out decoupling modeling with three phase electric machine, finally cannot
Realized using remaining 5 healthy inverter bridge leg output voltage vector between six-phase motor and the three phase electric machine of disappearance one phase
Electromagnetic torque uneoupled control.In place of the deficiencies in the prior art, the present invention proposes a kind of consideration disappearance phase winding to fixed
The six phase permanent-magnet synchronous motor series connection three-phase permanent magnet synchronous motor that the single inverter of sub- magnetic linkage modeling and control contribution is powered drives
System lacks a phase error-tolerance type Direct Torque Control it is therefore an objective to realize this kind of bi-motor series connection using remaining 5 phase inverter bridge
Two motor transient electromagnetic torque decouplers in the case of input side lacks a phase and controls, to improve this kind of tandem drive in drive system
The reliability of system.
The structured flowchart of the inventive method is as shown in Figure 1.Using T6Orthogonal transform matrix mutually inputs include disappearance phase 6
Electric current isA~isFIt is transformed to i in α β coordinate planeαiβAnd i in xy coordinate planexiy(formula (1)), thus two motors of control
The current component of energy converting between mechanical projects respectively to α β coordinate plane and xy coordinate plane;Using formula (2), iαiβAnd six phases
Permagnetic synchronous motor (this motor is abbreviated as PMSM6) rotor position angle θr1Calculate the six-phase permanent-magnet comprising to lack phase in α β plane
Synchronous motor stator magnetic linkage ψsαψsβ;Using formula (3), ixiyAnd three-phase permanent magnet synchronous motor (this motor is abbreviated as PMSM3) turns
Sub- angular position thetar2Calculate three-phase permanent magnet synchronous motor stator magnetic linkage ψ in x/y planesxψsy;Using formula (4), iαiβAnd ψsαψsβ
Calculate the six-phase motor electromagnetic torque T of disappearance one phasee1;Using formula (5), ixiyAnd ψsxψsyCalculate three phase electric machine electromagnetism to turn
Square Te2;Six-phase motor electromagnetic torque is givenAnd electromagnetic torque Te1, give the output control of six-phase motor torque hysteresis comparator
The τ of six-phase motor electromagnetic torque processede1Variable;Three phase electric machine electromagnetic torque is givenAnd electromagnetic torque Te2, give three-phase electricity
The τ of dynamo-electric magnetic torque hysteresis comparator output control three phase electric machine electromagnetic torquee2Variable;In six-phase motor α β coordinate plane
Stator magnetic linkage amplitude gives | ψs1|*And stator magnetic linkage amplitude | ψs1|, give six-phase motor flux linkage hysteresis comparator device output control six
The φ of the stator magnetic linkage amplitude in phase motor α β coordinate planee1Variable;Three phase electric machine xy coordinate plane inner stator magnetic linkage amplitude
Given | ψs2|*And stator magnetic linkage amplitude | ψs2|, give three phase electric machine flux linkage hysteresis comparator device output control three phase electric machine xy coordinate
The φ of plane inner stator magnetic linkage amplitudee2Variable;The stator magnetic linkage vector ψ in six-phase motor α β coordinate planes1Argument ∠ θψs1
With the stator magnetic linkage vector ψ in three phase electric machine xy coordinate planes2Argument ∠ θψs2Give respective Stator flux linkage sectors respectively and judge ring
Section, exports sector number θ residing for two stator flux of motor vectors respectively1si、θ2si;The controlling electromagnetic torque of two motors is become
Amount τe1τe2, stator magnetic linkage amplitude control variable φe1φe2And sector number θ1siθ2si, give optimized switching vector table and export one group
Optimum five inverter bridge leg switch combinations of residue, thus adding an optimal voltage vector in remaining 5 phase inputs, to realize
Two stator flux of motor amplitude errors and electromagnetic torque error are 0 control.Default due to calculating six-phase motor α β coordinate plane
Sub- magnetic linkage formula 2 includes the contribution of disappearance phase winding so that obtaining decoupling between the electromagnetic torque of two motors, is so profit
With remaining 5 inverter bridge legs, uneoupled control is carried out to two motor electromagnetic torques by stator magnetic linkage and creates precondition.?
Using in the drive system of all-digitized demodulator, do not need in addition to add hardware using the present invention, you can realize two motors of series connection
Lack any one input phase error-tolerance type Direct Torque Control, reduce the hardware cost of drive system.The method is implemented as follows,
S1:Using T6Orthogonal transform matrix, will include six input current i of disappearance phasesA~isFIt is transformed in α β coordinate
iαiβAnd i in xy coordinate systemxiy:
Wherein, io1、io2For two zero-sequence currents;Because six-phase motor lacks a phase, and three-phase windings have central point,
Two motor driven systems of all series connection only have 4 degree of freedom can control, due to needing the stator magnetic linkage to two motors, electricity
Magnetic torque carries out closed loop control, occupies 4 degree of freedom, so variable is uncontrolled in two zero sequence shaftings;
S2:Using formula (2), iαiβ, six-phase motor rotor flux ψf1And six-phase motor rotor position angle θr1Calculate α β
Plane six-phase motor stator magnetic linkage ψsαψsβ;
Lsm1=0.5 (Ldm1+Lqm1), Lrs1=0.5 (Ldm1-Lqm1), Ldm1、Lqm1It is respectively six-phase motor phase winding main magnetic circuit
Straight, quadrature axis inductance, Lsσ1For six-phase motor phase winding leakage inductance, these inductance value can obtain from six-phase motor nameplate;
Using formula (3), ixiy, three phase electric machine rotor flux ψf2And three phase electric machine rotor position angle θr2Calculate x/y plane
Three-phase motor stator magnetic linkage ψsxψsy:
Lsm2=0.5 (Ldm2+Lqm2), Lrs2=0.5 (Ldm2-Lqm2), Ldm2、Lqm2It is respectively three phase electric machine phase winding main magnetic circuit
Straight, quadrature axis inductance, Lsσ2For three phase electric machine phase winding leakage inductance, these inductance value can obtain from six-phase motor nameplate;
S3:Judge α β plane six-phase motor stator magnetic linkage ψsαψsβα β plane sector number θ residing for vector1si;Judge that xy puts down
Face three-phase motor stator magnetic linkage ψsxψsyX/y plane sector number θ residing for vector2si;
S4:According to α β plane six-phase motor stator magnetic linkage ψsαψsβAnd stator magnetic linkage amplitude givesThrough six-phase motor magnetic
Chain hysteresis comparator, the variable φ of output control α β plane six-phase motor stator magnetic linkage amplitudee1:
According to x/y plane three-phase motor stator magnetic linkage ψsxψsyAnd stator magnetic linkage amplitude givesThrough three phase electric machine magnetic linkage
Hysteresis comparator, the variable φ of output control x/y plane three-phase motor stator magnetic linkage amplitudee2:
S5:Using formula (4), iαiβAnd ψsαψsβCalculate six-phase motor electromagnetic torque Te1;
Te1=p1(ψsαiβ-ψsβiα) (4)
Wherein, p1For six-phase motor magnetic pole logarithm, can obtain from six-phase motor nameplate;
Using formula (5), ixiyAnd ψsxψsyCalculate three phase electric machine electromagnetic torque Te2;
Te2=p2(ψsxiy-ψsyix) (5)
Wherein, p2For three phase electric machine magnetic pole logarithm, can obtain from six-phase motor nameplate;
S6:By six-phase motor electromagnetic torque Te1And its set-pointGive six-phase motor torque hysteresis comparator, output
Control six-phase motor electromagnetic torque variable τe1,
Wherein, εm1For six-phase motor torque stagnant ring ring width, its value can be according to actual six-phase motor direct torque error need
Arrange;
By three phase electric machine electromagnetic torque Te2And its set-pointGive three phase electric machine torque hysteresis comparator, output control
Three phase electric machine electromagnetic torque variable τe2,
Wherein, εm2For three phase electric machine torque stagnant ring ring width, its value can be according to actual three phase electric machine direct torque error need
Arrange;
S7:By τe1、φe1、θ1si、τe2、φe2、θ2siIt is simultaneously sent to optimized switching vector table, obtain one group of remaining healthy 5 phase
Inverter bridge optimized switching combine, by inverter act on disappearance one mutually input six be in series three-phase permanent magnet synchronous motor drive
System, realizing two stator flux of motor amplitude errors and electromagnetic torque error is 0 control targe.
In described step S6, six-phase motor electromagnetic torque set-pointWith three phase electric machine electromagnetic torque set-pointDepending on tool
Depending on two motor control variables of body, specifically:If control is electromagnetic torque, system directly gives;If control is to turn
Speed, then two electric motor speed controller difference output torques are givenWithIf control is rotor position angle, two electricity
The output of machine positioner is torque referenceWith
In described step S2, α β plane six-phase motor stator magnetic linkage ψsαψsβWith x/y plane three-phase motor stator magnetic linkage ψsxψsy
Also can be calculated using the voltage model of stator magnetic linkage, the stator magnetic linkage typical calculation using voltage model is as follows:
Step S21:Using T6Orthogonal transform matrix, will include six input voltage u of disappearance phaseAO~uFOIt is transformed to α β to sit
U in marksαusβAnd u in xy coordinate systemsxusy:
Wherein, uso1、uso2For two residual voltages;
Step S22:According to formula (6), iαiβCalculate α β plane six-phase motor stator magnetic linkage ψsαψsβ;
α β plane six-phase motor stator magnetic linkage ψsαψsβ:
Wherein, Rs1For six-phase motor phase winding resistance;
According to formula (7), ixiyCalculate x/y plane three-phase motor stator magnetic linkage ψsxψsy;
X/y plane three-phase motor stator magnetic linkage ψsxψsy:
Wherein, Rs2For three phase electric machine phase winding resistance.
It is below the specific embodiment of the present invention.
Embodiments of the invention drive system hardware configuration is as shown in Figure 2.Including:Rectification circuit, filter capacitor, six contraries
Become device, 60 degree of six symmetrical winding permanent magnet synchronous motor of biasing, three-phase permanent magnet synchronous motor, six phase winding current collection circuits,
Two motor rotor position angle Acquisition Circuit, isolation drive, central controller, man-machine interfaces etc..Can also adopt suitably straight
Stream power supply provides six phase inverter DC bus-bar voltages.In inverter, power tube adopts IGBT or MOFET, and central controller adopts
DSP or single-chip microcomputer.Winding current Acquisition Circuit is constituted with the operational amplifier mode of combining using Hall current sensor, also may be used
Constituted so that the differential operational amplifier mode of combining is followed by using winding string power resistor.Can effectively be realized using Hall scheme
Control loop and the electrical isolation of major loop, can reduce drive system cost using winding string power resistor scheme.Rotor position
Angle setting Acquisition Circuit can be followed by level shifting circuit using rotary encoder and constitute, it would however also be possible to employ rotary transformer is followed by solving
Code circuit is constituted, and wherein the former cost is relatively low, but position angle sampling precision is limited by encoder line number, and the latter is relatively costly,
But position angle sampling precision is higher.Winding current Acquisition Circuit and the weak voltage signal of rotor position angle Acquisition Circuit deliver to central authorities' control
Device A/D modular converter processed.Calculate and should send according to the error-tolerance type Strategy of Direct Torque Control of the signal obtaining and the present invention
Control signal, goes to control the switch motion of the power switch pipe in inverter via isolation drive.
This system ultimate principle is described below:
Fig. 3 gives the connected mode of the six phase permanent-magnet synchronous motor series connection three-phase permanent magnet synchronous motor of the present invention.
ABCDEF is six phase windings of six phase permanent-magnet synchronous motor, and UVW is three phase windings of three-phase permanent magnet synchronous motor.Normal six
A phase current i in phase motorsAWith D phase current isDAnti-phase, so being in series with three phase electric machine U again after A phase and the parallel connection of D phase tail end,
To realize the decoupling in two motor controls, the connection of other phases is in the same manner.
Fig. 4 and Fig. 5 is the coordinate system that six phase permanent-magnet synchronous motor and three-phase permanent magnet synchronous motor realize energy converting between mechanical
Definition.α β and xy is rest frame, d1q1 and d2q2 is rotor synchronous rotating frame.In the diagram, between d1 axle and α axle
Angle be six-phase motor rotor position angle θr1, us1、is1、ψs1、ψr1It is respectively stator voltage vector, the electric current arrow of six-phase motor
Amount, α β plane stator magnetic linkage vector and rotor flux linkage vector, projection on d1 axle, q1 axle, α axle, β axle for these vectors is used respectively
Subscript " d1 ", " q1 ", " α ", " β " indicate.A~F is respectively six phase winding axis.ωr1Electric angle for the rotation of six-phase motor rotor
Speed.δ1For the angle between six-phase motor α β plane stator magnetic linkage and rotor flux.In Figure 5, the folder between d2 axle and x-axis
Angle is three phase electric machine rotor position angle θr2, us2、is2、ψs2、ψr2Be respectively the stator voltage vector of three phase electric machine, current phasor,
X/y plane stator magnetic linkage vector and rotor flux linkage vector, these vectors are under the projection in d2 axle, q2 axle, x-axis, y-axis is used respectively
Mark " d2 ", " q2 ", " x ", " y " indicate.U~W is respectively three-phase windings axis.ωr2Electric angle speed for the rotation of three phase electric machine rotor
Degree.δ2Angle between x/y plane stator magnetic linkage for three phase electric machine and rotor flux.Except for controlling two in six-phase motor
Freely it is outside one's consideration for 4 of platform motor energy converting between mechanical, also there are 2 degree of freedom, this two degree of freedom variables project to o respectively1
And o2Zero sequence shafting.
Using following T6Matrix can be Transformation of Mathematical Model in natural system of coordinates to α β, xy, o1o2In rest frame:
Six-phase motor α β plane stator magnetic linkage ψsαψsβWith three phase electric machine x/y plane stator magnetic linkage ψsxψsyAs follows respectively:
The electromagnetic torque of six phases and three phase electric machine is as follows respectively:
Te1=p1(ψsαiβ-ψsβiα) formula 4
Te2=p2(ψsxiy-ψsyix) formula 5
αβ、xy、o1o2In rest frame, voltage balance equation is as follows respectively:
Contrast (formula 4~formula 8) can be seen that related to six-phase motor energy converting between mechanical in train
Variable is only present on α β plane;In x/y plane, six-phase motor will produce leakage inductance pressure drop (L on three phase electric machinesσ1*dix/
dt、Lsσ1*diy/ dt) and resistance drop (Rs1*ix、Rs1*iy), but leakage inductance and resistance very little, it is negligible, therefore should
Only related to the three phase electric machine energy converting between mechanical variable of plane;o1o2Plane and the energy converting between mechanical variable of two motors
All it doesn't matter, only relevant with the resistance of the stator winding of two motors and leakage inductance.Therefore, six-phase motor and three phase electric machine can
So that decoupling independent control to be realized respectively on α β plane and x/y plane.
According to the definition of d1q1 in Fig. 4 and α β coordinate system, six-phase motor stator magnetic linkage and electromagnetic torque rotation transformation are arrived
In d1q1 coordinate system:
Te1=p1(ψsd1iq1-ψsq1id1) formula 10
Wherein, Ld1=Lsσ1+3Lsm1+3Lrs1, Lq1=Lsσ1+3Lsm1-3Lrs1It is respectively the straight of six-phase motor d1q1 coordinate system
Quadrature axis inductance.
Obtained by Fig. 4:
ψsd1=| ψs1|cosδ1Formula 11
ψsq1=| ψs1|sinδ1Formula 12
Can be obtained according to formula (formula 9), (formula 11), (formula 12)
(formula 11)~(formula 14) is substituted into (formula 10) can derive:
Understood according to formula (formula 15), as stator magnetic linkage ψs1When amplitude is controlled to constant, want to control torque Te1, only need
Control angle δ1.
In the same manner, three phase electric machine torque is it is also theorized that the expression formula similar to formula (formula 15) is as follows:
Wherein, Ld2=2Lsσ2+3Lsm2+3Lrs2, Lq2=2Lsσ2+3Lsm2-3Lrs2It is respectively three phase electric machine d2q2 coordinate system
D-axis and q-axis inductance.Understood according to formula (formula 16), as stator magnetic linkage ψs2When amplitude is controlled to constant, want to control torque Te2, only
Angle δ need to be controlled2.
Either six phase, or three phase electric machine, to by quick control δ1Or δ2, to realize quick to electromagnetic torque
Control it is only necessary to the rotation of quick control stator magnetic linkage vector.So, realize uneoupled control between two motors it is important to
How to utilize inverter output voltage vector to two stator flux of motor ψs1、ψs2Carry out uneoupled control.
From Fig. 3 connection figure, voltage u after six phase winding A phases are disconnected with inverter bridgeAo~uFoDerivation result is as follows:
Using T6Premultiplication (formula 17) both sides obtain
According to (formula 18) visible, uso1Naturally after being the open circuit of 0, A phase, and three-phase windings adopt star-like connection, so entirely
Drive system only has 4 free variables controlled.Control six-phase motor and three phase electric machine electromechanics energy using α β plane, x/y plane respectively
After total 4 free variables after amount conversion, on o2 axle, variable is uncontrollable.
Visible according to voltage, magnetic linkage relation, using suitable switch combination can control simultaneously six-phase motor α β plane, three
Phase motor x/y plane inner stator magnetic linkage, thus realize to six phases and three phase electric machine electromagnetic torque uneoupled control.
Ignore uAoAfter contribution to voltage vector in formula (formula 18), formula (formula 18) simplifies further
According to formula (formula 19), take different switch combination (Sb~Sf) one group of α β plane, the switch of x/y plane can be obtained
Vector usα+jusβ、usx+jusy, draw α β plane, x/y plane switching vector selector figure as shown in Figure 6.
Can be according to the Direct Torque Control exporting a voltage vector in traditional one digital controlling cycle, directly
It is connected on sectorization in α β plane and x/y plane, build optimized switching vector table.But this method can make optimized switching vector
Table becomes very huge, reduces the real-time of Direct Torque Control.For this reason, the present invention adopts univoltage vector partial synthesis
Voltage vector combines method, to build optimized switching vector table;α β plane and x/y plane are each divided into 90 degree of 4 spans
Sector, respectively as shown in FIG. 7 and 8, the univoltage vector being adopted or synthesized voltage vector are on the border of sector.By following
Mode resultant vector:81 (16,30), 82 (30,25), 83 (12,25), 84 (16,12), 85 (6,26), 87 (12,11), 89 (6,
19), 90 (15,19), 91 (15,1), 92 (6,1), 93 (19,20), 95 (9,13).Each resultant vector is by original two
Nonzero voltage space vector respectively acts on half controlling cycle and produces, and such as resultant vector 85 is by original 6 vector 26 vector respectively
Controlling cycle T of effect halfs/ 2 formation, its position, size and PWM sequential such as Fig. 7 and Fig. 8 institute on α β plane and x/y plane
Show.Continuous for arrow number, in figures 7 and 8 original vector 10,4,27,21 again arrow number is 86,88,
94,96.Vector respective scattergram such as Fig. 7 and Fig. 8 on α β plane and x/y plane.Based on 81~96 vectors, build the present invention
Optimized switching vector table method be elaborated as follows:
1) the synthesized voltage vector figure shown in Fig. 7, Fig. 8 is respectively divided into 4 sectors by figure mark, sector number is remembered respectively
For θ1siAnd θ2si(i=1,2,3,4).90 ° of electrical angles of each sector span.
2) judge six-phase motor stator magnetic linkage ψ respectivelys1With three-phase motor stator magnetic linkage ψs2Residing sector, according to two
Motor state in which, to select suitable voltage vector.For example, when the magnetic linkage of six-phase motor be in the first sector (as Fig. 7),
Torque and magnetic linkage are required to increase;The sector of three phase electric machine is also at the first sector (as Fig. 8), torque and magnetic linkage and is also required to simultaneously
Increase, then should select voltage vector 81.
3) combine 1) and 2) combined selection as a result, it is possible to obtain optimized switching vector table as shown in table 1, according to this table institute
The inverter output voltage vector obtaining, can realize lacking simultaneously the six-phase motor of a phase and three phase electric machine electromagnetic torque and
Stator magnetic linkage amplitude follows the tracks of set-point all the time, and two motors achieve uneoupled control.
Table 1 optimized switching vector table
In Table 1, τe1=1 and τe2=1 represents two motor torques all increases, τe1=-1 and τe2=-1 represents two electricity
Machine torque all reduces.Фe1=1 and Фe2=1 represents two motor magnetic linkages all increases, Фe1=0 and Фe2=0 represents two motors
Magnetic linkage all reduces
Work process comprises the steps:
(1) utilize T in formula 16Orthogonal transform matrix, will include six input current i of disappearance phasesA~isFIt is transformed to α β
I in coordinateαiβAnd i in xy coordinate systemxiy;
(2) formula 2, i are utilizedαiβ, six-phase motor rotor flux ψf1And six-phase motor rotor position angle θr1Calculate α β to put down
Face six-phase motor stator magnetic linkage ψsαψsβ;Using formula 3, ixix, three phase electric machine rotor flux ψf2And three phase electric machine rotor position angle
θr2Calculate x/y plane three-phase motor stator magnetic linkage ψsxψsy;
(3) judge α β plane six-phase motor stator magnetic linkage ψsαψsβα β plane sector number θ residing for vector1si;Judge that xy puts down
Face three-phase motor stator magnetic linkage ψsxψsyX/y plane sector number θ residing for vector2si;
(4) according to α β plane six-phase motor stator magnetic linkage ψsαψsβAnd stator magnetic linkage amplitude givesThrough six-phase motor magnetic
Chain hysteresis comparator, the variable φ of output control α β plane six-phase motor stator magnetic linkage amplitudee1;Fixed according to x/y plane three phase electric machine
Sub- magnetic linkage ψsxψsyAnd stator magnetic linkage amplitude givesThrough three phase electric machine flux linkage hysteresis comparator device, output control x/y plane three-phase
The variable φ of stator flux of motor amplitudee2;
(5) formula 4, i are utilizedαiβAnd ψsαψsβCalculate six-phase motor electromagnetic torque Te1;Using formula 5, ixiyAnd ψsxψsyMeter
Calculate three phase electric machine electromagnetic torque Te2;
(6) by six-phase motor electromagnetic torque Te1And its set-pointGive six-phase motor torque hysteresis comparator, output
Control six-phase motor electromagnetic torque variable τe1;By three phase electric machine electromagnetic torque Te2And its set-pointGive three phase electric machine to turn
Square hysteresis comparator, output control three phase electric machine electromagnetic torque variable τe2;
(7) by τe1、φe1、θ1si、τe2、φe2、θ2siIt is simultaneously sent to optimized switching vector table, obtain one group of remaining healthy 5 phase
Inverter bridge optimized switching combine, by inverter act on disappearance one mutually input six be in series three-phase permanent magnet synchronous motor drive
System, realizing two stator flux of motor amplitude errors and electromagnetic torque error is 0 control targe.
Wherein in step (6), electromagnetic torque givesWithDepending on concrete two motor control variables.If controlling
It is electromagnetic torque, then system directly gives this value;If control is rotating speed, (such as PI controls two electric motor speed controllers
Device) respectively output torque giveWithIf control is rotor position angle, two motor position controller outputs are
Torque referenceWith
α β plane six-phase motor stator magnetic linkage ψ wherein in step (2)sαψsβWith x/y plane three-phase motor stator magnetic linkage ψsxψsy
Can also be calculated using the voltage model of stator magnetic linkage.
It is more than presently preferred embodiments of the present invention, all changes made according to technical solution of the present invention, produced function is made
With without departing from technical solution of the present invention scope when, belong to protection scope of the present invention.
Claims (3)
1. a kind of input of series electric motor drive system lack a phase error-tolerance type Direct Torque Control it is characterised in that:Specifically should
Power six phase permanent-magnet synchronous motor series connection three-phase permanent magnet synchronous motor drive system for single inverter, the method includes walking as follows
Suddenly,
S1:Using T6Orthogonal transform matrix, will include six input current i of disappearance phasesA~isFIt is transformed to i in α β coordinateαiβAnd
I in xy coordinate systemxiy:
Wherein, io1、io2For two zero-sequence currents;Because six-phase motor lacks a phase, and three-phase windings have central point, all strings
Two motor driven systems of connection only have 4 degree of freedom can control, due to needing the stator magnetic linkage to two motors, electromagnetic torque
Carry out closed loop control, occupy 4 degree of freedom, so variable is uncontrolled in two zero sequence shaftings;
S2:Using formula (2), iαiβ, six-phase motor rotor flux ψf1And six-phase motor rotor position angle θr1Calculate α β plane
Six-phase motor stator magnetic linkage ψsαψsβ;
Lsm1=0.5 (Ldm1+Lqm1), Lrs1=0.5 (Ldm1-Lqm1), Ldm1、Lqm1It is respectively six-phase motor phase winding main magnetic circuit
Directly, quadrature axis inductance, Lsσ1For six-phase motor phase winding leakage inductance;
Using formula (3), ixiy, three phase electric machine rotor flux ψf2And three phase electric machine rotor position angle θr2Calculate x/y plane three-phase
Stator flux of motor ψsxψsy:
Lsm2=0.5 (Ldm2+Lqm2), Lrs2=0.5 (Ldm2-Lqm2), Ldm2、Lqm2It is respectively three phase electric machine phase winding main magnetic circuit
Directly, quadrature axis inductance, Lsσ2For three phase electric machine phase winding leakage inductance;
S3:Judge α β plane six-phase motor stator magnetic linkage ψsαψsβα β plane sector number θ residing for vector1si;Judge x/y plane three-phase
Stator flux of motor ψsxψsyX/y plane sector number θ residing for vector2si;
S4:According to α β plane six-phase motor stator magnetic linkage ψsαψsβAnd stator magnetic linkage amplitude givesStagnant through six-phase motor magnetic linkage
Ring comparator, the variable φ of output control α β plane six-phase motor stator magnetic linkage amplitudee1:
According to x/y plane three-phase motor stator magnetic linkage ψsxψsyAnd stator magnetic linkage amplitude givesThrough the stagnant chain rate of three phase electric machine magnetic linkage
Compared with device, the variable φ of output control x/y plane three-phase motor stator magnetic linkage amplitudee2:
S5:Using formula (4), iαiβAnd ψsαψsβCalculate six-phase motor electromagnetic torque Te1;
Te1=p1(ψsαiβ-ψsβiα) (4)
Wherein, p1For six-phase motor magnetic pole logarithm;
Using formula (5), ixiyAnd ψsxψsyCalculate three phase electric machine electromagnetic torque Te2;
Te2=p2 (ψsxiy-ψsyix) (5)
Wherein, p2For three phase electric machine magnetic pole logarithm;
S6:By six-phase motor electromagnetic torque Te1And its set-pointGive six-phase motor torque hysteresis comparator, output control six
Phase motor electromagnetic torque variable τe1,
Wherein, εm1For six-phase motor torque stagnant ring ring width, its value can need set according to actual six-phase motor direct torque error
Put;
By three phase electric machine electromagnetic torque Te2And its set-pointGive three phase electric machine torque hysteresis comparator, output control three-phase
Motor electromagnetic torque variable τe2,
Wherein, εm2For three phase electric machine torque stagnant ring ring width, its value can need set according to actual three phase electric machine direct torque error
Put;
S7:By τe1、φe1、θ1si、τe2、φe2、θ2siIt is simultaneously sent to optimized switching vector table, obtain one group of remaining healthy 5 phase inversion
Bridge optimized switching combines, and is in series three-phase permanent magnet synchronous motor drivetrain by inverter acts on that disappearance one mutually inputs six
System, realizing two stator flux of motor amplitude errors and electromagnetic torque error is 0 control targe.
2. series electric motor drive system input according to claim 1 lacks a phase error-tolerance type Direct Torque Control, its
It is characterised by:In described step S6, six-phase motor electromagnetic torque set-pointWith three phase electric machine electromagnetic torque set-pointDepending on
Depending on concrete two motor control variables, specifically:If control is electromagnetic torque, system directly gives;If control is
Rotating speed, then two electric motor speed controller difference output torques are givenWithIf control is rotor position angle, two
Motor position controller output is torque referenceWith
3. series electric motor drive system input according to claim 1 lacks a phase error-tolerance type Direct Torque Control, its
It is characterised by:In described step S2, α β plane six-phase motor stator magnetic linkage ψsαψsβWith x/y plane three-phase motor stator magnetic linkage ψsxψsy
Also can be calculated using the voltage model of stator magnetic linkage, the stator magnetic linkage typical calculation using voltage model is as follows:
Step S21:Using T6Orthogonal transform matrix, will include six input voltage u of disappearance phaseAO~uFOIt is transformed in α β coordinate
usαusβAnd u in xy coordinate systemsxusy:
Wherein, uso1、uso2For two residual voltages;
Step S22:According to formula (6), iαiβCalculate α β plane six-phase motor stator magnetic linkage ψsαψsβ;
α β plane six-phase motor stator magnetic linkage ψsαψsβ:
Wherein, Rs1For six-phase motor phase winding resistance;
According to formula (7), ixiyCalculate x/y plane three-phase motor stator magnetic linkage ψsxψsy;
X/y plane three-phase motor stator magnetic linkage ψsxψsy:
Wherein, Rs2For three phase electric machine phase winding resistance.
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Citations (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4463414A (en) * | 1982-09-13 | 1984-07-31 | Pillar Corporation | Alternating current power supply for highly inductive loads |
CN101662256A (en) * | 2009-09-21 | 2010-03-03 | 南京航空航天大学 | Control method of six-phase ten-pole permanent magnet fault-tolerant motor with strong fault-tolerant capability |
CN104270063A (en) * | 2014-09-30 | 2015-01-07 | 福州大学 | Fault-tolerant direct torque control method for six-phase permanent magnet synchronous motor lacking any two phases of windings |
CN105119546A (en) * | 2015-08-27 | 2015-12-02 | 浙江大学 | Fault tolerance control method based on asymmetric double three-phase permanent magnet synchronous motor |
-
2016
- 2016-11-04 CN CN201610958949.1A patent/CN106487308B/en active Active
Patent Citations (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4463414A (en) * | 1982-09-13 | 1984-07-31 | Pillar Corporation | Alternating current power supply for highly inductive loads |
CN101662256A (en) * | 2009-09-21 | 2010-03-03 | 南京航空航天大学 | Control method of six-phase ten-pole permanent magnet fault-tolerant motor with strong fault-tolerant capability |
CN104270063A (en) * | 2014-09-30 | 2015-01-07 | 福州大学 | Fault-tolerant direct torque control method for six-phase permanent magnet synchronous motor lacking any two phases of windings |
CN105119546A (en) * | 2015-08-27 | 2015-12-02 | 浙江大学 | Fault tolerance control method based on asymmetric double three-phase permanent magnet synchronous motor |
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